WO2013167002A1 - 一种串联谐振变换器的控制方法 - Google Patents

一种串联谐振变换器的控制方法 Download PDF

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Publication number
WO2013167002A1
WO2013167002A1 PCT/CN2013/077716 CN2013077716W WO2013167002A1 WO 2013167002 A1 WO2013167002 A1 WO 2013167002A1 CN 2013077716 W CN2013077716 W CN 2013077716W WO 2013167002 A1 WO2013167002 A1 WO 2013167002A1
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Prior art keywords
frequency
series resonant
resonant converter
control mode
load
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English (en)
French (fr)
Inventor
刘溪川
鲍胜华
陈洲
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ZTE Corp
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ZTE Corp
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Priority to EP13788628.9A priority Critical patent/EP2916444B1/en
Priority to US14/438,751 priority patent/US9425676B2/en
Publication of WO2013167002A1 publication Critical patent/WO2013167002A1/zh
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33571—Half-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/505—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/515—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H02M7/523—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with LC-resonance circuit in the main circuit
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • the present invention relates to a resonant power conversion technique, and in particular to a control method for a series resonant converter. Background technique
  • Figure 1 shows the main circuit topology of a half-bridge LLC series resonant converter.
  • the duty cycles of the power transistors Q1 and Q2 are both 0.5, and the complementary frequency modulation method of the fixed dead zone is used for control.
  • the resonant network equivalent circuit of the main circuit of the LLC series resonant converter is shown in Figure 2. From the equivalent circuit diagram, the DC voltage gain expression of the main circuit of the LLC series resonant converter is:
  • V in is the input voltage
  • f s is the operating frequency (ie, the switch tube
  • the conduction frequency) is the resonant frequency of the first working area
  • L r is the resonant inductance
  • L m is the magnetizing inductance
  • Q is the quality factor
  • the expression of the quality factor is:
  • the gain characteristic curve of the LLC series resonant converter can be drawn by the expression (1).
  • the LLC series resonant converter can be divided into three regions according to the operating characteristics.
  • the operating frequency f s >f r it is in the first working area; when f m ⁇ f s ⁇ , it works in the second working area; when f s ⁇ f m , it works in the third working area.
  • C r is the resonant capacitor and f m is the resonant frequency of the second working region, f 1
  • the first method is to add a small dummy load to achieve the output voltage under no-load or light-load conditions. Adjustment
  • the second method is to adjust the duty cycle (or phase shift angle) of the switch tube by adding a widening (or phase shifting) control under no-load or light-load conditions;
  • the third method is to add the widening (or phase shifting) and frequency-modulated mixing control under no-load or light-load conditions to adjust the duty cycle (or phase shift angle) and operating frequency of the switching tube at the same time.
  • the first method can realize the voltage regulation under no-load or light-load conditions, but sacrifices the converter at no load or light load. Conversion efficiency
  • the second method greatly improves the stability under no-load or light-load conditions, and achieves voltage regulation under no-load or light-load conditions.
  • due to the nonlinearity of the gain characteristic curve during widening As the duty cycle increases, the output voltage decreases, which makes the loop design difficult. It is difficult to ensure that the feedback loop of the widening range is always stable and does not oscillate.
  • the third method is based on the second method, adding simultaneous frequency modulation and widening control, the purpose is to ensure the linear relationship of the output gain characteristic curve, and solve the problem of loop design difficulty to some extent.
  • the method also has difficulty in controlling the loop.
  • the frequency adjustment curve is difficult to optimize and other practical engineering problems.
  • the converter works near the switching load point there are also two control strategies to switch back, making the loop unstable and affecting the overall output characteristics of the converter.
  • the object of the present invention is to provide a control method for a series resonant converter, which solves the problem of voltage instability of a series resonant converter under low voltage light load or no load condition, effectively expands the output range, and solves the problem at the same time.
  • the output voltage gain is not monotonous when the duty cycle is adjusted, and the loop is difficult to control.
  • the technical solution of the present invention is: obtaining a feedback signal by collecting an analog output signal of the series resonant converter, and changing an operating frequency of the series resonant converter according to the feedback signal; selecting a series resonant converter according to a state of the load
  • the series resonant converter adopts a hybrid control mode combining frequency modulation and fixed frequency modulation.
  • the series resonant converter adopts frequency modulation control.
  • Mode and the hybrid control mode and the FM control mode are switched by hysteresis control.
  • the operating frequency of the series resonant converter is obtained by integrating the absolute value of the difference between the feedback signal and the given value and multiplying by the set ratio.
  • the frequency modulation control mode is a control mode in which the frequency and the duty ratio are simultaneously adjusted and controlled.
  • the frequency modulation state flag bit and the cut-in frequency corresponding to the frequency modulation state flag bit are set, the calculated operating frequency is compared with the preset hand-cut frequency, and the control mode of the series resonant converter is determined according to the comparison result.
  • the frequency modulation state flag is 0 or 1.
  • the preset puncturing frequency is the first plunging frequency, and when the operating frequency is greater than the first plunging frequency, the series resonant converter adopts mixing. Control mode, otherwise the FM state flag is set to 1, the series resonant converter enters the FM control mode; when the FM status flag is 1, the preset cut-in frequency is the second cut-in frequency, when the series resonant converter is less than the second cut-in frequency
  • the series resonant converter adopts the frequency modulation control mode, otherwise the frequency modulation state flag is set to 0, and the series resonant converter enters the hybrid control mode.
  • the operating frequency is set to a frequency value between the first puncturing frequency and the second puncturing frequency.
  • the duty cycle of the series resonant converter operation is set to 0, and when the operating frequency is between the first cut-in frequency and the second cut-in frequency,
  • the series resonant converter adopts a fixed-width modulation control mode, and when the operating frequency is between the second plunging frequency and a predetermined value, the series resonant converter adopts an FM widening control mode.
  • FIG. 1 is a top view of a main circuit of a half-bridge LLC series resonant converter
  • Figure 2 is an equivalent circuit diagram of the resonant network of Figure 1;
  • Figure 3 is a schematic diagram of the LLC gain characteristic curve
  • Figure 4 is a simulation diagram of the output characteristics of the FM control in Figure 1;
  • Figure 5 is a simulation diagram of the output control characteristic of the adjustment control in Figure 1;
  • Figure 6 is a simulation diagram of the output characteristics of the simultaneous frequency modulation control in Figure 1;
  • FIG. 7 is a preferred flowchart of a method for controlling a resonant converter according to an embodiment of the present invention
  • FIG. 8 is a diagram showing a relationship between duty ratio and frequency in a specific control according to an embodiment of the present invention. detailed description
  • the control method of the present invention is applicable to a series resonant converter circuit, and specifically includes: an LC series resonant converter circuit (SRC), a series-parallel resonant converter circuit (SPRC), and a LLC series resonant converter circuit; the circuit topology may be a half bridge, a full bridge, or the like.
  • SRC LC series resonant converter circuit
  • SPRC series-parallel resonant converter circuit
  • LLC series resonant converter circuit the circuit topology may be a half bridge, a full bridge, or the like.
  • control method of the present invention is as follows:
  • the feedback signal is obtained by collecting the analog output signal of the series resonant converter, and the operating frequency of the series resonant converter is changed according to the feedback signal; the control mode of the series resonant converter is selected according to the state of the load, when the load is in a light load or no load state
  • the series resonant converter adopts a hybrid control mode combining frequency modulation and fixed frequency modulation.
  • the series resonant converter adopts a frequency modulation control mode, and the hybrid control mode and the frequency modulation control mode pass the hysteresis loop. Control to switch.
  • the switching between the hybrid control mode and the FM control mode of the series resonant converter load is determined by presetting the two states (the state of the FM flag) and the cut-in frequency corresponding to each state (as will be described later).
  • the load is light or heavy, which is set according to the actual application. Different series of resonant converters and different application scenarios have different light load or heavy load division.
  • the embodiment of the present invention is still described by taking the half bridge LLC series resonant converter shown in FIG. 1 as an example.
  • the half-bridge LLC series resonant converter further includes a processor, a storage unit, a unit for controlling the switch tubes Q1, Q2, etc., which are well known to those skilled in the art, and thus are not shown in the drawings, and are not for convenience of explanation.
  • a processor for controlling the switch tubes Q1, Q2, etc.
  • FIG. 4 discloses that the half-bridge LLC series resonant converter adopts an FM control mode, has a duty ratio of 45%, and operates at the same light load open-loop condition, and the operating frequencies are 100K, 150 ⁇ , respectively. 200K, 250K, 300 ,, corresponding output voltage characteristics.
  • the half-bridge LLC series resonant converter has a duty ratio of 15%, 20%, 30% when operating in the same light load open-loop condition when the control mode is used, the operating frequency is 300K. , 40%, 45%, corresponding output voltage characteristics.
  • FIG. 6 discloses that the half-bridge LLC series resonant converter adopts the frequency modulation and widening control mode, and the frequency corresponding duty cycle is 300K/15%, 280 ⁇ /20%, respectively, when operating under the same light load open-loop condition.
  • FIG. 7 is a flowchart of a control method according to an embodiment, which performs corresponding control by determining a frequency modulation flag bit, and the frequency modulation flag bit is preset in a half bridge LLC series resonant converter software, and the setting is performed. Is 0 or 1.
  • the preset plunging frequency is assigned to the first plunging frequency.
  • the first plunging frequency is set to 110K, and when the operating frequency of the switching tubes Q1 and Q2 is determined to be smaller than the first cutting
  • the input frequency ie less than 110K
  • the load of the half-bridge LLC series resonant converter is determined to be a heavy load
  • the operating frequency of the switching tubes Q1 and Q2 is set to 150K (the duty ratio is 50%)
  • the analog output signal of the series resonant converter circuit is sampled to obtain a feedback signal, and the absolute value of the difference between the feedback signal and the given value is integrated, and then multiplied by the set ratio to obtain the operating frequency of the switching transistors Q1 and Q2 of the next cycle.
  • the FM flag is set to 1, and enters the FM control mode; otherwise, the load of the half-bridge LLC series resonant converter is determined to be light load or no load. At this time, the half-bridge LLC series resonant converter operates in the hybrid control mode.
  • the preset cut-in frequency is assigned to the second cut-in frequency.
  • the second cut-in frequency is set to 250K, and when the operating frequency is greater than the second cut-in frequency (ie, greater than 250 ⁇ ), the determination is performed.
  • the load of the half-bridge LLC series resonant converter is light load or no load.
  • the operating frequency of the switching transistors Q1 and Q2 is set to 150K (duty cycle is 30%), and the analog output signal of the series resonant converter circuit is sampled.
  • the feedback signal is integrated with the absolute value of the difference between the feedback signal and the given value, and multiplied by the set ratio to obtain the operating frequency and duty ratio of the switching transistors Q1 and Q2 of the next cycle, and the FM flag is set to 0. , enter the hybrid control mode; otherwise, determine that the load of the half-bridge LLC series resonant converter is heavy, so that the half-bridge LLC series resonant converter operates in the FM control mode.
  • the control mode of adjusting the frequency with a fixed duty ratio is adopted, that is, the duty ratio of the switching tubes Q1 and Q2 is fixed to 30%.
  • the control mode in which the frequency and the duty ratio are simultaneously adjusted is adopted, that is, the duty ratios of the switching tubes Q1 and Q2 are linearly changed from 30% to 15%.
  • FIG. 8 reflects the correspondence between duty cycle and frequency in the specific control of the embodiment.
  • the main control ideas of the control method of the present invention can be visually seen from the figure.
  • a hybrid control mode combining frequency modulation and fixed-width frequency modulation is used to control the operating frequency and duty ratio of the series resonant converter switch. It realizes the voltage regulation function under low voltage and light load or no load condition, effectively expands the output range, and solves the problem that the output voltage gain is not monotonous and the loop is difficult to control under low voltage and light load conditions; and the hybrid control mode and frequency modulation Control mode Two working modes adopt hysteresis control when switching, which solves the problem that when the series resonant converter works near the switching load point, the two control modes switch back and forth, resulting in unstable output, effectively improving the loop during switching. Stability and overall output performance specifications of the series resonant converter.
  • the invention solves the problem that the series resonant converter is under low voltage light load or no load state by adopting a hybrid control mode when the load is light load or no load and a hybrid control mode and a frequency modulation control mode switching by hysteresis control.
  • the problem of unstable voltage effectively expands the output range, and solves the problem that the output voltage gain is not monotonous and the loop is difficult to control due to the adjustment of the duty ratio, thereby effectively improving the loop stability and the series resonant converter during switching.
  • Overall output performance metrics are provided.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

一种串联谐振变换器的控制方法，该方法通过采集串联谐振变换器的模拟输出信号获得反馈信号，并根据反馈信号改变串联谐振变换器的工作频率；且当串联谐振变换器的负载为轻载或空载状态时，其采用调频调宽、定宽调频两种相结合的混合控制模式，当负载重载时，其采用调频控制模式，且混合控制模式和调频控制模式通过滞环控制进行切换。通过在负载轻载或者空载时采用混合控制模式和通过滞环控制实现混合控制模式和调频控制模式切换的方式，从而解决了串联谐振变换器在低压轻载或空载状态下的电压不稳定的问题、有效地扩展了输出范围，同时解决了因调整占空比时输出电压增益不单调、环路难以控制的问题。

Description

一种串联谐振变换器的控制方法 技术领域
本发明涉及谐振电源变换技术， 具体涉及一种串联谐振变换器的控制 方法。 背景技术
随着电源变换技术的发展， 高效率高功率密度成为一个重要的发展趋 势。 谐振变换器以其软开关， 效率高， 工作频率高， 体积小等优点在开关 电源技术应用中得到广泛的应用和关注。 串联谐振变换器作为其中的一种 简单电路拓朴， 既能够满足高频化要求， 又能够达到较高的转换效率， 已 被业界广泛采用。
以 LLC ( Lr， Lm， Cr 的缩写， 它们分别代表谐振参数中的谐振电感、 励磁电感和谐振电容） 串联谐振变换器为例， 变换器上的谐振元件工作在 正弦谐振状态的时候， 开关管上的电压自然过零， 在变频的范围内都能够 实现原边开关管的零电压开通与关断， 所以电源损耗很小。 因此这种拓朴 通常采用变频调制 （ Pulse frequency modulation, 简称 PFM )控制模式。
图 1为半桥 LLC串联谐振变换器主电路拓朴。电路在进行 PFM控制时， 功率管 Q1、 Q2占空比均为 0.5，采用固定死区的互补调频方式来进行控制。 LLC 串联谐振变换器主电路的谐振网络等效电路如图 2所示， 由等效电路 图可得出 LLC串联谐振变换器主电路直流电压增益表达式为：
Figure imgf000003_0001
其中， V。为输出电压， Vin为输入电压， fs为工作频率 （亦即开关管的 导通频率）， 为第一个工作区的谐振频率， fr ^ ^， Lr为谐振电感，
Lm为励磁电感， Q为品质因数， 品质因数的表达式为：
Figure imgf000004_0001
由表达式 ( 1 )可绘出 LLC串联谐振变换器增益特性曲线示意图如图 3 所示， LLC 串联谐振变换器按工作特性可分为三个区域。 当工作频率 fs>fr 时， 处于第一个工作区； fm<fs< 时工作于第二个工作区； fs<fm时， 工作于 第三个工作区。 其中， Cr为谐振电容， fm为第二个工作区的谐振频率， f 1
m 2 ^Cr(Lr + Lm) 当工作频率 fs大于谐振频率 时， 励磁电感 Lm作为负载未参与谐振， 此时的工作模式类似于一般的串联谐振变换器（SRC )。 当变换器输出空载 或轻载时， Rac接近为无穷大， Q近似为 0， 因此表达式（1 )可简化为
Figure imgf000004_0002
由表达式（3 )可以看出，当 LLC串联谐振变换器工作在空载或轻载时， 工作频率升高或者谐振频率降低， 会使电压增益变小， 当 fs> 时， 增益的 微小变化会引起很大的频率变化， 因此 LLC串联谐振变换器在空载或轻载 条件下输出电压难以稳定。 由图 3 可以看出， 当工作在低压轻载状态时， 增益特性曲线趋于平坦， 如果要稳压就需要很高的工作频率， 但工作频率 很高会带来一系列问题， 如磁性器件难以优化， 开关损耗增加， 可靠性降 低等； 另外当负载接近空载时， 输出电压会随着频率或占空比的升高反而 上升， 导致无法进行负反馈环路控制。
目前业界中通常采用如下方法来克服上述问题：
第一种方法是， 在空载或轻载状态下， 加个小的假负载实现输出电压 调节；
第二种方法是， 在空载或轻载状态下， 加入调宽 （或者移相）控制即 调整开关管的占空比 （或者移相角）；
第三种方法是， 在空载或轻载状态下， 加入调宽 （或者移相）和调频 调宽混合控制即同时调整开关管的占空比 （或者移相角 )和工作频率。
上述三种方法， 虽然可以克月良上述问题， 然而亦分别存在如下问题： 第一种方法虽然可以实现空载或轻载状态下的稳压， 但是牺牲了空载 或轻载时的变换器转换效率；
第二种方法虽然极大的改善了空载或轻载状态下的稳定度， 实现了空 载或轻载状态下的稳压， 但由于调宽时增益特性曲线的非线性， 即可能出 现随着占空比的增加输出电压反而下降， 这样导致环路设计困难， 难以保 证调宽范围反馈环路始终稳定不振荡， 另外当变换器工作在切换负载点附 近时， 会存在两种控制策略来回切换， 使环路不稳定， 影响变换器整体输 出特性；
第三种方法是在第二种方法的基础上， 加入了同时调频调宽控制， 目 的是保证输出增益特性曲线的线性关系， 一定程度上解决了环路设计困难 的问题。 但是在实际工程中对于输出范围很宽的变换器而言， 很难保证在 输出极限低压时， 输出增益特性曲线随占空比的变化仍然呈线性关系， 因 此该方法同样会存在环路难以控制， 调频调宽曲线难以优化等实际工程问 题。 另外当变换器工作在切换负载点附近时， 同样会存在两种控制策略来 回切换， 使环路不稳定， 影响变换器整体输出特性。
上面以半桥 LLC串联谐振为例说明了变换器工作在低压轻载或空载时 存在问题和缺陷， 全桥串联谐振也存在相同的现象。 理论上， 所有采用调 频控制的串联谐振电路均存在上述问题。 发明内容
本发明的目的在于提供一种串联谐振变换器的控制方法， 该方法解决 了串联谐振变换器在低压轻载或空载状态下的电压不稳定的问题、 有效的 扩展了输出范围， 同时解决了因调整占空比时输出电压增益不单调、 环路 难以控制的问题。
为实现上述发明目的， 本发明的技术方案为： 通过采集串联谐振变换 器的模拟输出信号获得反馈信号， 并根据反馈信号改变串联谐振变换器的 工作频率； 根据负载的状态选择串联谐振变换器的控制模式， 当负载为轻 载或空载状态时， 串联谐振变换器采用调频调宽、 定宽调频两种相结合的 混合控制模式， 当负载为重载状态时， 串联谐振变换器采用调频控制模式， 且混合控制模式和调频控制模式通过滞环控制进行切换。
优选地， 所述串联谐振变换器的工作频率是通过反馈信号与给定值的 差的绝对值进行积分运算后乘以设定的比例获得。
优选地， 当串联谐振变换器采用混合控制模式时， 其中的调频调宽控 制模式是频率和占空比同时进行调整控制的控制模式。
优选地， 设置调频状态标志位及预设与调频状态标志位对应的切入频 率， 将计算出的工作频率与预设切入频率进行比较， 根据比较结果来确定 串联谐振变换器的控制模式。
优选地， 调频状态标志位为 0或 1， 当调频状态标志位为 0时， 预设的 切入频率为第一切入频率， 当工作频率大于第一切入频率时， 串联谐振变 换器采用混合控制模式， 否则将调频状态标志位置 1， 串联谐振变换器进入 调频控制模式； 调频状态标志位为 1时， 预设的切入频率为第二切入频率， 当串联谐振变换器小于第二切入频率时， 串联谐振变换器采用调频控制模 式， 否则将调频状态标志位置 0， 串联谐振变换器进入混合控制模式。
优选地， 在调频状态标志位为 0且工作频率小于第一切入频率时或调 频状态标志位为 1 且工作频率大于第二切入频率时， 将工作频率设置为第 一切入频率和第二切入频率之间的一个频率值。
优选地， 在混合控制模式下， 当工作频率大于一预定值时， 将串联谐 振变换器工作的占空比设为 0，当工作频率在第一切入频率和第二切入频率 之间时， 使串联谐振变换器采用定宽调频控制模式， 工作频率在第二切入 频率和预定值之间时， 使串联谐振变换器采用调频调宽控制模式。
采用本发明控制方法的有益效果有如下几点：
( 1 ) 由于当串联谐振变换器工作在低压轻载或空载状态下， 采用调频 调宽和定宽调频两种相结合的混合控制模式， 对串联谐振变换器的工作频 率和占空比进行控制， 实现了低压轻载或空载状态下的稳压功能， 有效扩 展了输出范围， 同时解决了低压轻载条件下因输出电压增益不单调， 环路 难以控制的问题；
( 2 )混合控制模式和调频控制模式两种工作模式在切换时， 采用滞环 制， 解决了当串联谐振变换器工作在切换负载点附近时两种控制模式来回 切换导致输出不稳定的问题， 有效提高了切换时环路稳定性和串联谐振变 换器的整体输出性能指标。 附图说明
图 1是半桥 LLC串联谐振变换器主电路拓朴结构图；
图 2是图 1中谐振网络等效电路图；
图 3是 LLC增益特性曲线示意图；
图 4是图 1中采用调频控制输出特性仿真图；
图 5是图 1中采用调宽控制输出特性仿真图；
图 6是图 1中采用同时调频调宽控制输出特性仿真图；
图 7根据本发明实施例的谐振变换器控制方法的一种优选流程图； 图 8才艮据本发明实施例具体控制中占空比与频率对应关系图。 具体实施方式
为了详细说明本发明的技术内容、 构造特征、 所达成的目的及效果， 以下结合实施方式并配合附图作进一步说明。
本发明控制方法适用于串联谐振变换电路， 具体包括： LC串联谐振变 换电路（ SRC )， 串并联谐振变换电路（ SPRC ) 以及 LLC 串联谐振变换电 路； 电路拓朴可以是半桥， 全桥等。
本发明控制方法如下：
通过采集串联谐振变换器的模拟输出信号获得反馈信号， 并根据反馈 信号改变串联谐振变换器的工作频率； 根据负载的状态选择串联谐振变换 器的控制模式， 当负载为轻载或空载状态时， 串联谐振变换器采用调频调 宽、 定宽调频两种相结合的混合控制模式， 当负载为重载状态时， 串联谐 振变换器采用调频控制模式， 且混合控制模式和调频控制模式通过滞环控 制进行切换。
串联谐振变换器负载的混合控制模式和调频控制模式的切换， 是通过 预设两个状态 （调频标志位的状态）和每一状态对应的切入频率共同来确 定（如后详述）。 负载为轻载或重载， 是根据实际应用而设定的， 不同的串 联谐振变换器、 不用的应用场景， 其轻载或重载的划分并不相同。
本发明具体实施例仍以图 1所示的半桥 LLC串联谐振变换器为例进行 说明。半桥 LLC串联谐振变换器还包括处理器、存储单元、控制开关管 Q1 、 Q2的单元等， 此为本领域技术人员所熟知， 因此并未在图中示出， 在此不 为便于说明， 首先对半桥 LLC串联谐振变换器在采用调频控制模式、 调宽控制模式和调频调宽控制模式时的输出电压特性进行说明。
请参阅图 4，其揭示了半桥 LLC串联谐振变换器在采用调频控制模式、 占空比为 45%、工作在同样轻载开环条件时，工作频率分别为 100K、 150Κ、 200K、 250K、 300Κ时， 对应的输出电压特性。
由图 4可以看出， 当随着工作频率的升高输出电压变化范围已经很小， 这限制了半桥 LLC串联谐振变换器的输出调节能力。
请参阅图 5，其揭示了半桥 LLC串联谐振变换器在采用调宽控制模式、 工作频率为 300K、 工作在同样轻载开环条件时， 占空比分别为 15%、 20%、 30%、 40%、 45%, 对应的输出电压特性。
由图 5 可以看出， 引入调宽控制可极大的改善变换器输出调节能力， 但是同时也可以看出， 随着占空比的降低输出电压反而上升， 这样会导致 半桥 LLC串联谐振变换器输出电压增益不单调， 环路难以控制。
请参阅图 6， 其揭示了半桥 LLC 串联谐振变换器在采用调频调宽控制 模式， 工作在同样轻载开环条件时， 频率对应占空比分别为 300K/15%、 280Κ/20%、 260Κ/25%、 240Κ/30%、 220Κ/35%、 200Κ/40%对应的输出电压 特性。
由图 6可以看出， 引入调频调宽控制后输出电压基本上随着设定的频 率占空比控制曲线呈线性变化， 但半桥 LLC串联谐振变换器仍然存在输出 电压增益不单调的情况同时还存在严重的非线性， 导致增益突变。 因此也 会存在环路难以控制的问题。
以下为本发明控制方法的具体说明。
请参阅图 7， 其为本实施例的控制方法流程图， 其通过对调频标志位进 行判断， 进行相应的控制， 调频标志位是在半桥 LLC串联谐振变换器软件 中预设的， 其设置为 0或 1。
在调频标志位为 0 时， 将预设切入频率赋值为第一切入频率， 在本实 施例中第一切入频率设定为 110K， 当判断开关管 Ql 、 Q2的工作频率小于 第一切入频率 (即小于 110K )时， 判定半桥 LLC串联谐振变换器的负载为 重载， 将开关管 Ql 、 Q2的工作频率设置为 150K (占空比为 50% )， 并对 串联谐振变换电路的模拟输出信号进行采样得到反馈信号， 将该反馈信号 与给定值的差的绝对值进行积分运算后乘以设定的比例得到下一周期开关 管 Ql 、 Q2的工作频率， 同时将调频标志位设置为 1， 进入调频控制模式； 否则，判定半桥 LLC串联谐振变换器的负载为轻载或空载，此时使半桥 LLC 串联谐振变换器工作在混合控制模式。
上述的给定值和设定的比例是根据半桥 LLC串联谐振变换器器件参数 和实际工作要求而定的。
在调频标志位为 1 时， 将预设切入频率赋值为第二切入频率， 在本实 施例中第二切入频率设定为 250K， 当工作频率大于第二切入频率（即大于 250Κ )时， 判定半桥 LLC串联谐振变换器的负载为轻载或者空载， 将开关 管 Ql 、 Q2的工作频率设置为 150K (占空比为 30% )， 并对串联谐振变换 电路的模拟输出信号进行采样得到反馈信号， 将该反馈信号与给定值的差 的绝对值进行积分运算后乘以设定的比例得到下一周期开关管 Ql 、 Q2的 工作频率和占空比， 同时将调频标志位设置 0， 进入混合控制模式； 否则判 定半桥 LLC串联谐振变换器的负载为重载，使半桥 LLC串联谐振变换器工 作在调频控制模式。
本实施例中混合控制模式采用的控制方法具体如下：
在混合控制模式下， 工作频率在第一切入频率和第二切入频率之间时， 采用固定占空比调整频率的控制模式， 即开关管 Ql 、 Q2 占空比固定为 30%。
在混合控制模式下， 工作频率在第二切入频率〜 300K之间时， 采用频 率和占空比同时进行调整的控制模式， 即开关管 Ql 、 Q2 占空比在 30%~15%线性变化。
在混合控制模式下， 频率在 300K以上时， 开关管 Ql 、 Q2占空比为
0。 请参阅图 8， 其反映了本实施例具体控制中占空比与频率对应关系，从 图中可以很直观的看出本发明控制方法主要的控制思路。
由于当串联谐振变换器工作在低压轻载或空载状态下， 采用调频调宽 和定宽调频两种相结合的混合控制模式， 对串联谐振变换器开关管工作频 率和占空比进行控制， 实现了低压轻载或空载状态下的稳压功能， 有效的 扩展了输出范围， 同时解决了低压轻载条件下因输出电压增益不单调、 环 路难以控制的问题； 且混合控制模式和调频控制模式两种工作模式在切换 时， 采用滞环控制， 解决了当串联谐振变换器工作在切换负载点附近时两 种控制模式来回切换导致输出不稳定的问题， 有效的提高了切换时环路稳 定性和串联谐振变换器的整体输出性能指标。
需要说明的是， 上述实施例中所有的具体数据只是作为一个实例来进 行说明的， 本发明不仅限于此， 实际工程中可根据需要进行设定。
以上所揭露的仅为本发明的较佳实例而已， 当然不能以此来限定本发 明之权利范围， 因此依本发明权利要求所作的等同变化， 仍属于本发明所 涵盖的范围。
工业实用性
本发明通过在负载为轻载或者空载时采用混合控制模式和通过滞环控 制实现混合控制模式和调频控制模式切换的方式， 从而解决了串联谐振变 换器在低压轻载或空载状态下的电压不稳定的问题、 有效地扩展了输出范 围， 同时解决了因调整占空比时输出电压增益不单调、 环路难以控制的问 题， 从而有效提高了切换时环路稳定性和串联谐振变换器的整体输出性能 指标。

Claims

权利要求书
1、 一种串联谐振变换器的控制方法， 包括： 通过采集串联谐振变换器 的模拟输出信号获得反馈信号， 并根据反馈信号改变串联谐振变换器的工 作频率； 根据负载的状态选择串联谐振变换器的控制模式， 当负载为轻载 或空载状态时， 串联谐振变换器采用调频调宽、 定宽调频两种相结合的混 合控制模式， 当负载为重载时， 串联谐振变换器采用调频控制模式， 且混 合控制模式和调频控制模式通过滞环控制进行切换。
2、 根据权利要求 1所述串联谐振变换器的控制方法， 其中： 所述串联 谐振变换器的工作频率是通过反馈信号与给定值的差的绝对值进行积分运 算后乘以设定的比例获得。
3、 根据权利要求 1所述串联谐振变换器的控制方法， 其中： 当串联谐 振变换器采用混合控制模式时， 其中的调频调宽控制模式是频率和占空比 同时进行调整控制的控制模式。
4、 根据权利要求 1所述串联谐振变换器的控制方法， 其中： 设置调频 状态标志位及预设与调频状态标志位对应的切入频率， 将计算出的工作频 率与预设切入频率进行比较， 根据比较结果来确定变换器串联谐振变换器 的控制模式。
5、 根据权利要求 4所述串联谐振变换器的控制方法， 其中： 调频状态 标志位为 0或 1， 当调频状态标志位为 0时，预设的切入频率为第一切入频 率， 当工作频率大于第一切入频率时， 串联谐振变换器采用混合控制模式， 否则将调频状态标志位置 1， 串联谐振变换器进入调频控制模式； 调频状态 标志位为 1 时， 预设的切入频率为第二切入频率， 当串联谐振变换器小于 第二切入频率时， 串联谐振变换器采用调频控制模式， 否则将调频状态标 志位置 0， 串联谐振变换器进入混合控制模式。
6、 根据权利要求 5所述串联谐振变换器的控制方法， 其中： 在调频状 态标志位为 0且工作频率小于第一切入频率时或调频状态标志位为 1且工 作频率大于第二切入频率时， 将工作频率设置为第一切入频率和第二切入 频率之间的一个频率值。
7、 根据权利要求 5所述串联谐振变换器的控制方法， 其中： 在混合控 制模式下， 当工作频率大于一预定值时， 将串联谐振变换器工作的占空比 设为 0， 当工作频率在第一切入频率和第二切入频率之间时，使串联谐振变 换器采用定宽调频控制模式， 工作频率在第二切入频率和预定值之间时， 使串联谐振变换器采用调频调宽控制模式。
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