WO2017118337A1 - 无线通信方法和无线通信设备 - Google Patents

无线通信方法和无线通信设备 Download PDF

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Publication number
WO2017118337A1
WO2017118337A1 PCT/CN2016/112967 CN2016112967W WO2017118337A1 WO 2017118337 A1 WO2017118337 A1 WO 2017118337A1 CN 2016112967 W CN2016112967 W CN 2016112967W WO 2017118337 A1 WO2017118337 A1 WO 2017118337A1
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Prior art keywords
side device
receiving
receiving side
transmitting
predetermined pilot
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Ceased
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PCT/CN2016/112967
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English (en)
French (fr)
Inventor
赵培尧
王昭诚
竺旭东
陈晋辉
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Sony Corp
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Sony Corp
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Priority to AU2016384951A priority Critical patent/AU2016384951B2/en
Priority to BR112018010935-5A priority patent/BR112018010935A2/zh
Priority to CN202210673489.3A priority patent/CN115085786B/zh
Priority to EP20169869.3A priority patent/EP3709532A1/en
Priority to US15/766,967 priority patent/US10530434B2/en
Priority to CN201680074945.5A priority patent/CN108476056B/zh
Priority to JP2018517175A priority patent/JP7070407B2/ja
Priority to EP16883462.0A priority patent/EP3402090A4/en
Application filed by Sony Corp filed Critical Sony Corp
Publication of WO2017118337A1 publication Critical patent/WO2017118337A1/zh
Anticipated expiration legal-status Critical
Priority to US16/693,371 priority patent/US11070260B2/en
Priority to US17/234,834 priority patent/US11711121B2/en
Priority to US18/207,137 priority patent/US20230318668A1/en
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/0862—Weighted combining receiver computing weights based on information from the transmitter
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0621—Feedback content
    • H04B7/0626—Channel coefficients, e.g. channel state information [CSI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0868—Hybrid systems, i.e. switching and combining
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0868—Hybrid systems, i.e. switching and combining
    • H04B7/088—Hybrid systems, i.e. switching and combining using beam selection
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0891—Space-time diversity
    • H04B7/0897—Space-time diversity using beamforming per multi-path, e.g. to cope with different directions of arrival [DOA] at different multi-paths
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0404—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas the mobile station comprising multiple antennas, e.g. to provide uplink diversity
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • the present invention relates to a wireless communication method and a wireless communication device, and in particular to a beamforming training method suitable for a multi-user large-scale antenna system and an apparatus using the same.
  • millimeter wave technology and Massive Multi-Input Multi-Output (MIMO) technology are considered to be the key technologies of the fifth generation of mobile communication (5G) in the future, and thus have attracted widespread attention.
  • the millimeter-wave band has a large amount of available spectrum resources to meet the growing demand for traffic.
  • due to the short wavelength of the millimeter wave it is possible to set hundreds or even thousands of antennas in a small space, which is more advantageous for the application of large-scale antenna technology in real systems.
  • Fig. 1 schematically shows a single base station multi-user millimeter wave large-scale antenna system.
  • the base station 100 is equipped with M antennas and serves K user equipments UE1-UE K, each of which is equipped with N antennas.
  • data for K users by the device is a fully digital precoding matrix W ⁇ C M ⁇ K mapped to M radio frequency link
  • optimal precoding performance can be obtained.
  • this all-digital precoding architecture requires M radio frequency links, resulting in high hardware complexity and high power consumption. Therefore, the system shown in FIG.
  • each RF link corresponds to multiple phase shifters and antenna units, a single RF link can form one beam, so that a plurality of RF links can form a beam compared to the all-digital precoding architecture, which is greatly reduced.
  • the hardware cost The values of the phase shifters in the analog phase shifting network 120 constitute an analog precoding matrix F.
  • the analog precoding matrix F ⁇ C M ⁇ K satisfies the constraint
  • 2 M -1 .
  • the signals received on the respective antennas of the user equipments UE 1-UE K are connected via a phase-shifting network 140 to the respective one or more radio frequency links.
  • the downlink signal transmission model can be expressed as
  • y k is the received signal of the kth user equipment
  • H k is the downlink channel matrix between the kth user equipment and the base station 100
  • F and B are respectively an analog precoding matrix and a digital precoding matrix, wherein the analog precoding
  • the kth column f k of the matrix F represents an analog transmission weight vector for the kth user equipment (eg, phase settings for a plurality of phase shifters to which the kth radio frequency link is connected)
  • w k represents the kth user
  • the receiving weight vector of the device n k represents Gaussian white noise
  • x represents data transmitted to K user equipments UE 1-UE K.
  • the weight vector f k and the reception weights analog transmit weight vector w k is typically selected from the codebooks defined in advance, and more specifically, are selected from a code having a code the base station 100 of the present Fc and a user equipment UE according Wc of of.
  • the analog transmit and receive weight vectors are typically designed separately from the digital precoding matrix B to reduce computational complexity.
  • the process of selecting the optimal analog transmission weight vector/receiving weight vector for each user equipment from the codebook is called beamforming training. Beamforming training can be performed using criteria that maximize user received power, which is expressed as follows:
  • ⁇ w k, opt , f k, opt ⁇ represents the downlink receiving weight vector/downlink transmission weight vector optimal for the kth user equipment.
  • H eq ⁇ C K ⁇ K the downlink equivalent channel H eq ⁇ C K ⁇ K.
  • [H eq ] i,j w i,opt T H i f j, opt .
  • ZF The algorithm (ZF) is used to design the digital precoding matrix B, which is expressed as follows:
  • ⁇ is a diagonal matrix for transmission power allocation between user equipments.
  • the traditional beamforming training mechanism mainly includes physical channel estimation, exhaustive search, multi-layer feedback and single feedback.
  • the physical channel estimation mechanism directly estimates the downlink physical channel H k ⁇ C N ⁇ M through the pilot, and then the user equipment calculates an optimal transmit/receive weight vector according to the estimated physical channel, and feeds the transmission weight vector to the base station.
  • both the base station and the user equipment are equipped with a large number of antennas, so the channel estimation complexity is extremely high, and since the pilot is not beamformed, the received signal and noise are relatively low, and the channel estimation accuracy is higher. low.
  • the exhaustive search mechanism searches for all possible transmit/receive weight vector pairs, and the user equipment measures the channel quality for each pair of transmit/receive weight vectors, thereby selecting the optimal weight vector pair and feeding back the transmit weight vector to the base station.
  • An exhaustive search mechanism can achieve optimal performance, but the complexity is extremely high.
  • the multi-layer feedback mechanism divides the training process into multiple layers through pre-designed multi-layer codebooks, using exhaustive search in each layer. Since the number of candidate codewords in each layer is small, the complexity is reduced. However, the multi-layer feedback mechanism needs to feed back the weight vector to the base station multiple times, resulting in additional resources. In addition, since the training process of each user equipment is different, all user equipments must be trained individually, so that the overall complexity is high.
  • the single feedback mechanism divides the beamforming training into two processes. First, the base station searches for all possible transmission weight vectors, and the user equipment uses the omnidirectional beam to receive signals and estimate the channel quality, thereby selecting the optimal transmission weight vector and Feedback to the base station. Subsequently, the base station fixedly transmits the weight vector, and the user searches for the optimal reception weight vector. Compared with the exhaustive search mechanism, the complexity of the single feedback mechanism is reduced, but it also causes a certain performance loss, and its complexity increases with the increase of the number of user equipment.
  • the traditional beamforming training mechanism is mainly faced with the problem of excessive complexity.
  • the complexity of beamforming training affects the communication establishment time, which is a Important indicators. Therefore, there is a need for a fast beamforming training mechanism suitable for multi-user millimeter wave large-scale antenna systems.
  • the present invention provides a receiving side device in a communication system, comprising one or more processors, the one or more processors being configured to: according to the receiving side device pair from the transmitting side Determining, by a receiving sequence of a common sequence, an analog weight parameter of the plurality of antennas of the receiving side device; determining, according to the analog weight parameter, an antenna configuration for transmitting a predetermined pilot signal corresponding to the receiving side device, to The predetermined pilot signal is transmitted to the transmitting side.
  • the present invention also proposes a transmitting side device for a communication network, comprising one or more processors, the one or more processors being configured to generate a common sequence for transmission to multiple receptions a side device; for each of the plurality of receiving side devices, determining, according to a reception condition of a predetermined pilot signal from the receiving side device, a plurality of the transmitting side devices for the receiving side device An analog weight parameter of the antenna, wherein the predetermined pilot signal is sent by the receiving side device based on a multi-antenna transmission weight parameter of the receiving side device, wherein the multi-antenna transmission weight parameter is by the receiving side The device is determined based on the reception of the common sequence.
  • the present invention also provides a training method in a communication system, comprising: generating a common sequence by a transmitting side device to transmit to a plurality of receiving side devices; each of the plurality of receiving side devices according to receiving the common sequence Determining a first analog weight parameter, and determining an antenna configuration for transmitting a predetermined pilot signal corresponding to the receiving side device according to the determined first analog weight parameter to transmit the predetermined pilot signal to the a transmitting side device; and the transmitting side device determining a second analog weighting parameter for the receiving side device according to a reception condition of the predetermined pilot signal, and determining, according to the determined second analog weight parameter, An antenna configuration for transmitting data of the receiving side device to transmit the data to the receiving side device.
  • FIG. 1 is a schematic structural block diagram of a single base station multi-user millimeter wave large-scale antenna communication system to which the present invention is applied.
  • Fig. 2 schematically shows the structure of a fully connected phase shifting network of a base station.
  • Fig. 3 schematically shows the structure of a sub-connection phase shifting network of a base station.
  • Fig. 4 schematically shows the structure of a user equipment equipped with a plurality of radio frequency links.
  • Fig. 5 schematically shows the structure of a user equipment equipped with a single radio frequency link.
  • Figure 6 is a flow diagram of one example of beamforming training in accordance with the present invention.
  • Fig. 7 is a view for explaining the down training according to the present invention.
  • 8A and 8B are views for explaining the up training according to the present invention.
  • FIG. 9 is a flow chart of another example of beamforming training in accordance with the present invention.
  • FIGS 10A and 10B show performance comparisons of beamforming training in accordance with the present invention with the prior art.
  • 11 is a block diagram showing an example configuration of computer hardware.
  • Fig. 1 is a block diagram showing the structure of a communication system to which the present invention is applied.
  • K user data streams are input to a baseband digital precoder 110, and the digital precoder 110 digitally precodes K data streams using a digital precoding matrix B to Map to K RF links with different weighting factors.
  • Digital precoding is mainly used to eliminate interference between different data streams when multiple data streams multiplex the same physical transmission resources. It should be noted that digital precoding is not a necessary processing in the present invention since analog precoding can achieve different beam transmissions that are spatially separated, thereby reducing interference between different transport streams to some extent. In order to reduce system complexity or reduce cost, a digital precoder may not be provided in some embodiments.
  • digital precoding is done at the baseband portion, so the digital precoder can be implemented, for example, by a baseband processor, and is therefore sometimes referred to as a baseband precoder.
  • analog precoding is implemented by the processing circuitry in the RF section and is therefore sometimes referred to as analog beamforming.
  • the concept of beamforming has been known in the prior art, but most of them are discussed under the framework of one-to-one correspondence between the RF link and the antenna unit, and there is no device constraint. From the perspective, it is not necessary to perform repeated training to select a codeword from a fixed codebook for actual transmission.
  • beamforming transmission is usually performed only on the base station side, and the user equipment side only passively receives signals without adjustment of an antenna configuration (for example, a radio frequency device).
  • the radio frequency link of the user equipment corresponds to multiple phase shifters and antenna units, and a specific antenna configuration scheme is adopted when receiving or transmitting signals to cooperate with the base station to achieve high quality signal transmission.
  • the baseband signal is upconverted, amplified, and filtered to form a radio frequency signal.
  • the K radio frequency links are connected to the analog phase shifting network 120, and the M outputs of the phase shifting network 120 are respectively connected to the M antennas.
  • the values of the phase shifters in the phase shifting network 120 constitute an analog precoding matrix (or analog beamforming matrix) F.
  • analog beamforming is mainly used to improve the receiving signal-to-noise ratio of user equipment and overcome channel path fading. Generate different beams for different user equipments.
  • the processor 130 is configured to generate or determine a digital precoding matrix B and an analog precoding matrix F, that is, the processor 130 is configured to control digital precoding processing and configuration of phase shifters in the phase shifting network 120. It can be understood that the processor 130 herein can be implemented as one or more high-level controllers, baseband processors, and the like, and the digital pre-coding matrix B and the analog pre-coding matrix F can be separately generated by different processors.
  • phase shifting network 120 includes both a fully connected phase shifting network and a sub-connected phase shifting network.
  • Figure 2 shows schematically the structure of a fully connected phase shifting network. As shown in FIG. 2, each RF link is connected to M phase shifters, and the output signals of each K (K ⁇ M) phase shifters are added by an adder and connected to one antenna unit.
  • Fig. 3 schematically shows the structure of a sub-join phase shifting network. As shown in FIG. 3, each RF link is connected to M/K phase shifters, and each phase shifter is connected to one antenna unit.
  • each user equipment UE is equipped with N receiving antennas.
  • each user equipment UE can be equipped with a different number of antennas, and the invention is not limited thereto.
  • Figure 4 shows the structure of the user equipment UE in more detail.
  • the signals received by the N antenna units are connected to a plurality of radio frequency links via the phase shifting network 410 (the number of radio frequency links is less than the number of antenna units), and then filtered, amplified, and down-converted to obtain a baseband received signal. (not shown).
  • the structure of the phase shifting network 410 is similar to the phase shifting network 120 on the base station side.
  • the value of the phase shifter in the phase shifting network 410 constitutes the analog receive weight matrix W of the user equipment UE. Further, similar to the base station side, the reception weight matrix W is configured by the processor 420, that is, the value of the phase shifter in the phase shift network 410 is configured.
  • FIG. 5 shows another structure of the user equipment UE, which is more simplified than that of FIG.
  • the user equipment UE has only one radio frequency link, so signals received through the N antennas are added and output to the radio frequency link, and the phase shifting network is no longer needed.
  • the values of the N phase shifters connected to the N antennas constitute the analog reception weight vector w of the user equipment UE.
  • the values of the N phase shifters are configured by the processor 510, ie, the receive weight vector w is configured.
  • a weight vector corresponds to a value pattern of a plurality of phase shifters, the elements of the weight vector representing phase values of a set of phase shifters, and the weight matrix comprising respective RF chains Multiple weight vectors for the road. Furthermore, all available weight vectors constitute a beamforming codebook, in other words each weight vector corresponds to one of the beamforming codebooks.
  • the received signal corresponding to the kth data stream on the base station side (it is noted that the user equipment equipped with multiple radio frequency links can receive multiple data streams) can be expressed as:
  • H k is a downlink channel matrix between the user equipment and the base station corresponding to the kth data stream.
  • B ⁇ C K ⁇ K is a digital precoding matrix.
  • the digital precoding matrix B is a diagonally dominant matrix, that is, the value of the diagonal element is large, so after the digital precoding, the signal on the kth radio link Will mainly come from the kth data stream.
  • F ⁇ C M ⁇ K is an analog precoding matrix, and the kth column f k of the analog precoding matrix F represents an analog transmission weight vector for the kth radio frequency link (mainly carrying the kth data stream).
  • Full phase shifting network connection as shown in FIG.
  • w k represents the simulated reception weight vector of the user equipment for the kth data stream.
  • the vector w k is similar to the above f k .
  • x represents a signal transmitted by a base station corresponding to K data streams
  • n k represents Gaussian white noise
  • the analog transmission weight vector f k and the analog reception weight vector w k can only be selected from a predefined codebook due to device constraints, that is, only one of the predetermined codebooks can be employed.
  • the codebook on the base station side is defined as Fc
  • the codebook on the user equipment side is defined as Wc.
  • the codebook refers to all possible sets of values of non-zero elements in the weight vector.
  • the base station 100 notifies the downlink training information to all the user equipment UEs it serves by, for example, a broadcast channel, and the downlink training information may include, for example, the time for transmitting a downlink training sequence (for example, a pilot signal). The number of segments, the number of times the downlink training sequence is sent, and so on.
  • the downlink training sequence is generated by the base station 100 (for example, the processor 130), and is transmitted by the base station 100 to all user equipment UEs in step S602.
  • the downlink training sequence may be a Channel State Information Reference Signal (CSI-RS), a Common Reference Signal (CRS), a Demodulation Reference Signal (DMRS), etc., in addition to a broadcast channel such as It can be a Broadcast Control Channel (BCCH).
  • CSI-RS Channel State Information Reference Signal
  • CRS Common Reference Signal
  • DMRS Demodulation Reference Signal
  • BCCH Broadcast Control Channel
  • the downlink training information includes a time period in which the CSI-RS is transmitted, and includes information indicating that the CSI-RS is transmitted only on the specific subframe, since the certain number of the specific subframes are included in the time period, Therefore, the downlink training information does not have to include the number of times the CSI-RS is transmitted.
  • step S602 the base station 100 broadcasts a downlink training sequence (CSI-RS) to all user equipment UEs multiple times using the omnidirectional beam f omni .
  • CSI-RS downlink training sequence
  • Omnidirectional beam f omni is defined to satisfy Analog transmission weight vector, where Represents the base station transmit antenna response vector, ⁇ and Respectively indicate the horizontal direction of arrival angle and the vertical direction of arrival angle, and C represents a constant.
  • the user equipment UE can estimate the equivalent channel coefficient in the case where a certain codeword in the codebook Wc is used as the analog reception weight vector.
  • the user equipment UE may estimate an equivalent channel in the case where another codeword is used as the analog reception weight vector.
  • the number of times the base station transmits the downlink training sequence (for example, P times) is equal to the number of codewords in the codebook Wc of the user equipment UE (that is, the codebook size)
  • the user is received by receiving the downlink training sequence of P times.
  • the device UE can estimate the equivalent channel in the case of using all codewords in the codebook Wc.
  • the base station 100 is shown to broadcast the downlink training sequence to the user equipment UE 1-K P times using the omnidirectional beam f omni .
  • the user equipments UE 1-UE K respectively estimate the equivalent channel coefficients in the case where the codeword w 1 is used as the reception weight vector, and then the user for the downlink training sequence of the second broadcast,
  • the devices UE 1-UE K respectively estimate the equivalent channel coefficients in the case where the codeword w 2 is employed as the reception weight vector, and so on, until the estimation is completed for the P codewords in the codebook Wc.
  • the base station 100 determines the number of times of repeating the broadcast training sequence, for example, according to the codebook size of the user equipment having the largest codebook, to ensure each user.
  • the device is capable of making a full estimate.
  • a user equipment having multiple radio frequency links can utilize each radio frequency link to estimate one codeword, and thus can simultaneously target multiple codewords when receiving the downlink training sequence broadcasted by the base station 100 at one time. Make an estimate.
  • the base station 100 can reduce the number of times the downlink training sequence is repeatedly transmitted.
  • the user equipment can perform a complete estimation, and the base station 100 still needs to repeatedly broadcast the downlink training sequence according to the codebook size P of the user equipment.
  • the downlink reception weight vector that causes the reception quality of the downlink training sequence to satisfy the predetermined condition may be selected according to the estimation result, or preferably, the reception with the best reception quality is selected.
  • the weight vector, as the downlink reception weight vector that itself will be used in communication, is as shown in step S603 of FIG.
  • the criteria for selection may include: 1) maximizing the received signal power criteria, and 2) maximizing the signal to interference ratio criteria, which are respectively applicable to the case where the user equipment UE is equipped with a single radio frequency link and a plurality of radio frequency links.
  • the maximum received signal power criterion can be expressed as follows:
  • w represents the downlink receive weight vector used for a single radio link.
  • Wc represents a predetermined analog beamform codebook in the user equipment.
  • H ⁇ C N ⁇ M denotes a downlink channel matrix between the base station and the user equipment (N and M denote the number of antennas with the base station and user equipment), f omni represents a base station using the omni-directional beam.
  • the value of the phase shifter connected to the single radio frequency link of the user equipment UE may be configured according to the above determined opt to send the uplink training sequence to the base station (will be described later) description).
  • the maximum signal to interference ratio criterion can be expressed as follows:
  • N RF represents the number of radio frequency links provided by the user equipment
  • w j represents the analog reception weight vector adopted for the jth radio frequency link.
  • Wc represents the user.
  • H ⁇ C N ⁇ M represents the downlink channel matrix between the base station and the user equipment
  • f omni represents the omnidirectional beam used by the base station.
  • the value of a set of phase shifters connected to the jth radio link of the user equipment UE may be configured according to w j,opt as determined above to transmit an uplink training sequence to the base station (described later).
  • the w j,opt can be utilized to configure the values of the sets of phase shifters connected to the respective radio frequency links of the user equipment UE, that is, to perform the same configuration for each group of phase shifters.
  • a user equipment UE having multiple radio frequency links can simultaneously train with two base stations (eg, one macro base station and one small base station) by, for example, the Dual Connectivity technology specified in the LTE-A communication protocol.
  • the user equipment UE can obtain the analog reception weight vectors w1 and w2 for the two base stations, respectively, and then the user equipment UE configures a set of phase shifts connected to the radio frequency link 1 for the base station 1 by using the determined weight vector w1.
  • the value of the device, and for the base station 2 uses the determined weight vector w2 to configure the values of a set of phase shifters connected to the radio frequency link 2, thereby enabling simultaneous beamforming transmissions with the two base stations.
  • the downlink training process ends.
  • the user equipment UE calculates an uplink transmission weight vector according to the determined downlink reception weight vector in step S604, so that the uplink training sequence is transmitted by using the calculated uplink transmission weight vector, and the uplink training process is started.
  • the determined reception weight vector can be directly used as the uplink transmission weight vector of the user equipment UE.
  • the received weight vector can be corrected to obtain a more accurate line transmission weight vector, which will be described in detail below.
  • the base station 100 broadcasts uplink training information to all user equipments, for example, the uplink training information may include a time period for transmitting an uplink training sequence, a number of times for transmitting an uplink training sequence, and the like.
  • the uplink training information may not necessarily include the number of times the uplink training sequence is transmitted.
  • the base station has notified the user equipment about the information about the radio frequency link, the beamform codebook, and the like in the system information when the user equipment accesses the network.
  • the uplink training information may also be It is not necessary to include the number of times the uplink training sequence is sent.
  • the uplink training may be set in advance after a predetermined time elapses after the end of the downlink training, so the base station 100 may not need to specifically send the uplink training information.
  • the base station 100 notifies the user equipment UE of the uplink training sequence allocated to the user equipment UE by using dedicated signaling such as RRC signaling.
  • the user equipment UE transmits an uplink training sequence to the base station 100 according to the uplink transmission weight vector obtained in step S604, and the uplink training sequence and the uplink training information learned in step S605, as shown in step S606.
  • the uplink training sequences used by the respective user equipments UE are orthogonal to each other, including at least one of the training sequences themselves being orthogonal to each other and the physical transmission resources being orthogonal to each other.
  • the uplink training sequence may for example be an orthogonal pilot signal, such as a sounding reference signal (SRS).
  • SRS sounding reference signal
  • the uplink training sequence is SRS
  • the user equipment since the user equipment performs beamforming and transmitting the SRS based on the downlink training result, the downlink channel information can be implicitly and implicitly fed back while providing the resource scheduling reference to the base station. No special feedback signaling overhead is required.
  • the base station 100 estimates the equivalent channel coefficient in the case where each codeword in the codebook Fc is used as the uplink reception weight vector, and determines the reception of the uplink training sequence according to the estimation result.
  • the uplink reception weight vector whose quality satisfies the predetermined condition (or the reception quality is optimal) is as shown in step S607.
  • the base station 100 since the base station 100 typically has multiple radio frequency links, multiple codewords can be estimated simultaneously, ie, one for each radio link.
  • the codeword is used as the received weight vector to estimate the equivalent channel. Therefore, for an uplink training sequence transmitted by one user equipment UE at a time, the base station 100 can complete an equivalent channel estimation for K RF codewords, where KRF is the number of radio frequency links provided by the base station 100.
  • KRF is the number of radio frequency links provided by the base station 100.
  • the user equipment UE 1-UE K is used to transmit the uplink training sequence multiple times using its corresponding uplink transmission weight vector w 1 -w K , respectively.
  • the base station 100 has K RF radio frequency links, so it can be used for K RF code words f 1 , f 2 ... To estimate the equivalent channel coefficient.
  • the base station 100 targets the other K RF code words. To estimate the equivalent channel coefficients, and so on, until the estimation of all Q codewords in the codebook Fc is completed.
  • the processing of the base station 100 is the same as that for the user equipment UE 1.
  • the uplink training sequences sent by the multiple user equipments UE 1-UE K are mutually overlapping on the antennas of the base station 100.
  • the base station 100 can parse each user equipment UE. The sequence is sent, and the uplink training is performed separately for each user equipment UE. In this case, the capital consumed in the uplink training process
  • the source is independent of the number of users. Therefore, as long as the number of available orthogonal pilot signals (uplink training sequences) is allowed, as many user equipment UEs as possible can simultaneously transmit the uplink training sequence, thereby saving the total training overhead.
  • each radio-frequency link is connected to all antennas, so that the reception of signals on all transmission paths can be experienced.
  • all user equipment UEs served by the base station 100 can simultaneously transmit an uplink training sequence, so that the base station 100 can perform uplink training for all user equipment UEs at the same time and select a reception weight vector for each user equipment UE.
  • each radio frequency link of the base station 100 can be set to receive all users using the same receiving weight vector.
  • the K RF radio frequency links of the base station 100 use the code word f 2 to receive and estimate the equivalent channel coefficient, and so on, until The estimation is done for all Q codewords in the codebook Fc.
  • the training overhead is slightly larger than the case where the base station 100 is equipped with a fully connected phase shifting network, it still has significant advantages over existing methods such as an exhaustive search mechanism.
  • the base station 100 selects uplink reception that satisfies the predetermined condition that the reception quality of the uplink training sequence meets the predetermined condition according to the estimation result.
  • the criteria selected include: 1) maximizing the received signal power criteria, and 2) maximizing the signal to interference ratio criteria, which are respectively applicable to scenarios in which the user equipment UE is equipped with a single radio link and multiple radio links.
  • the maximum received signal power criterion can be expressed as follows:
  • f denotes a base station side reception weight vector used for the uplink training sequence transmitted by the user equipment 100.
  • f is selected from each codeword in the codebook Fc, and Fc represents a predetermined analog beamforming in the base station 100.
  • Codebook. H ⁇ C M ⁇ N denotes an uplink channel matrix between the base station and the user equipment UE 100 (N and M denote the number of antennas with the base station and user equipment), w represents a weight of the user equipment UE an uplink transmission using the weight vector.
  • the value of a set of phase shifters connected to the RF link of the user equipment UE in the base station 100 may be configured according to f opt as determined above to transmit data for the user equipment UE (described later).
  • the maximum signal to interference ratio criterion can be expressed as follows:
  • N RF denotes the number of radio frequency links provided by the user equipment 100
  • f j denotes a base station side reception weight vector adopted for the jth radio frequency link of the user equipment 100, as described above
  • f j is selected from the codebook Fc
  • Each codeword, Fc represents a predetermined analog beamform codebook in base station 100.
  • H ⁇ C M ⁇ N represents an uplink channel matrix between the user equipment and the base station 100
  • w j represents a transmission weight vector adopted by the j-th radio link of the user equipment 100.
  • the value of a set of phase shifters connected to the radio frequency link of the jth radio link of the user equipment UE in the base station 100 may be configured according to f j,opt determined as above to send data for the user equipment (will Described later).
  • the base station 100 calculates a downlink transmission weight vector for communication based on the determined uplink reception weight vector in step S608.
  • the determined reception weight vector can be directly used as the transmission weight vector.
  • the uplink reception weight vector needs to be corrected to obtain a downlink transmission weight vector.
  • both the user equipment UE and the base station 100 need to correct the determined reception weight vector to obtain a transmission weight vector, which will be specifically described below.
  • the method of correcting the received weight vector is related to antenna configuration and codebook design.
  • a correction method under the common linear equidistant antenna array and Fast Fourier Transform (FFT) codebook design is given below.
  • Codebook matrix For each column of the matrix is a reception / transmission weight vectors, where N a is the number of antennas, N c is the codebook size. The value of the element in the mth row and the mth column of the matrix C is
  • the uplink reception weight vector base station 100 in step S607 determined is the k-th up column codebook matrix in which S608 Selection k codebook matrix in the step down the column as a weight vector transmission weights for downlink transmission , where k down is given by:
  • step S608 After the base station 100 obtains the downlink transmission weight vector in step S608, the uplink training process ends. Thereafter, the base station 100 performs digital precoding processing in step S609.
  • the base station 100 first estimates an equivalent channel matrix whose least squares (LS) estimates of the (i, j)th elements of the equivalent channel matrix are as follows:
  • f j, opt is an uplink receiving weight vector used by the base station 100
  • y j is a signal sequence received by the base station 100 when f j, opt is used.
  • w i,opt is the optimal uplink transmission vector obtained by the i-th user equipment (assuming that the user equipment has a single radio link) in the downlink training phase
  • H i is the downlink channel matrix between the base station and the i-th user equipment.
  • ⁇ i is the orthogonal pilot used by the ith user equipment.
  • the base station 100 then calculates the digital precoding matrix B using a zero forcing (ZF) algorithm.
  • the digital precoding matrix B can be expressed as follows:
  • ⁇ is a diagonal matrix representing the transmission power allocation between user equipments.
  • the base station 100 has obtained the digital precoding matrix B, so that K data streams can be digitally precoded.
  • the base station 100 has obtained a downlink transmission weight vector for each user equipment UE (or its respective radio frequency link), that is, an analog precoding matrix F is obtained, so that the phase shifter in the analog phase shift network 120 can be configured. value.
  • the base station 100 can transmit the actual data (different from the training sequence) to the user equipment UE in step S610. Accordingly, the user equipment UE can also receive the actual data using the reception weight vector determined in step S603.
  • the beamforming training process shown in FIG. 6 can be applied to a periodic training mode between the base station 100 and the user equipment UE. That is, the base station 100 periodically notifies the user equipment UE of the downlink training information (as shown in step S601), thereby starting the training process.
  • Figure 9 shows the beamforming training process in the aperiodic training mode.
  • the user equipment 100 performs channel quality measurement in step S901.
  • the user equipment 100 actively sends a training request to the base station 100, as shown in step S902.
  • the base station 100 broadcasts the downlink training information to the user equipment UE in step S903, thereby starting the training process.
  • the subsequent steps S904-S912 are the same as steps S602-S610 in FIG. 6, and therefore will not be described herein.
  • the downlink training sequence is broadcast by the base station, and all user equipments can participate in the training at the same time.
  • the number of the required number of probe pairs (NPP) is P, where P is in the user equipment.
  • the beam is shaped by the codebook size.
  • all user equipments with orthogonal uplink training sequences can participate in training at the same time, and the K RF radio links provided by the base station can simultaneously perform equivalent channel estimation for different codewords, so the required detection
  • the number of beam pairs is Q/K RF , where Q is the beamform codebook size of the base station.
  • the overall complexity of the beamforming training mechanism according to the present invention is Q/K RF + P, and its complexity does not increase as the number of users increases, and thus is very suitable for a multi-user millimeter wave communication system. Furthermore, the beamforming training mechanism according to the present invention does not require feedback operation of the user equipment to the base station.
  • 10A and 10B respectively show the average downlink reachable rate of the user that can be achieved by the fast multi-user beamforming training mechanism and the existing exhaustive search mechanism and the single feedback mechanism, respectively, under different channel conditions.
  • the abscissa represents the signal-to-noise ratio
  • the ordinate represents the average downlink reachable rate
  • N cl represents the number of channel scattering clusters
  • N ray represents the number of sub-paths contained in each scattering cluster
  • ⁇ represents the length of the training sequence.
  • the performance of the beamforming training mechanism of the present invention is still superior to that of the single feedback mechanism. Furthermore, as the signal-to-noise ratio increases, the performance of the beamforming training mechanism of the present invention quickly converges to performance in a noise-free environment in a noisy environment, ie, the performance upper bound of the mechanism.
  • the base station in the above embodiments may be implemented as any type of evolved Node B (eNB), such as a macro eNB and a small eNB.
  • the small eNB may be an eNB covering a cell smaller than the macro cell, such as a pico eNB, a micro eNB, and a home (femto) eNB.
  • the base station can be implemented as any other type of base station, such as a NodeB and a base transceiver station (BTS).
  • the base station can include: a body (also referred to as a base station device) configured to control wireless communication; and one or more remote wireless headends (RRHs) disposed at a different location than the body.
  • RRHs remote wireless headends
  • various types of terminals can also operate as base stations by performing base station functions temporarily or semi-persistently.
  • the user equipment in the above embodiment can be implemented, for example, as a communication terminal (such as a smart phone, a tablet personal computer (PC), a notebook PC, a portable game terminal, a portable/encrypted dog type mobile router, and a digital camera). , or an in-vehicle terminal (such as a car navigation device).
  • the user equipment may also be implemented as a terminal that performs machine-to-machine (M2M) communication, also referred to as a machine type communication (MTC) terminal.
  • M2M machine-to-machine
  • MTC machine type communication
  • the user equipment may also be a wireless communication module (such as an integrated circuit module including a single wafer) installed on each of the above terminals.
  • the processor in the present invention may be implemented as a baseband processor or a combination of a baseband processor and a general purpose processor, for example implemented as a central processing unit (CPU) or a digital signal processor. (DSP).
  • CPU central processing unit
  • DSP digital signal processor
  • each device or module in the above embodiments may be implemented by software, hardware, or a combination of software and hardware.
  • the program included in the software can be stored in advance in a storage medium set inside or outside each device. As an example, during execution, these programs are written to random access memory (RAM) and executed by a processor (eg, a CPU).
  • FIG. 11 is a block diagram showing an example configuration of computer hardware that executes the above-described processing in accordance with a program.
  • a central processing unit (CPU) 1101, a read only memory (ROM) 1102, and a random access memory (RAM) 1103 are connected to each other through a bus 1104.
  • the input/output interface 1105 is further connected to the bus 1104.
  • the input/output interface 1105 is connected to an input unit 1106 formed by a keyboard, a mouse, a microphone, or the like; an output unit 1107 formed of a display, a speaker, or the like; a storage unit 1108 formed of a hard disk, a nonvolatile memory, or the like; A communication unit 1109 formed of a network interface card (such as a local area network (LAN) card, a modem, etc.); and a drive 1110 that drives the removable medium 1111 such as a magnetic disk, an optical disk, a magneto-optical disk, or a semiconductor memory.
  • LAN local area network
  • the CPU 1101 loads the program stored in the storage unit 1108 into the RAM 1103 via the input/output interface 1105 and the bus 1104, and executes the program to execute the above processing.
  • a program to be executed by a computer may be recorded on a removable medium 1111 as a package medium, such as a magnetic disk (including a floppy disk), an optical disk (including a compact disk-read only memory (CD-ROM)), A digital versatile disc (DVD) or the like, a magneto-optical disc, or a semiconductor memory is formed.
  • a program to be executed by a computer can also be provided via a wired or wireless transmission medium such as a local area network, the Internet, or digital satellite broadcasting.
  • the program can be input/output via The interface 1105 is installed in the storage unit 1108.
  • the program can be received by the communication unit 1109 via a wired or wireless transmission medium, and the program is installed in the storage unit 1108.
  • the program may be pre-installed in the ROM 1102 or the storage unit 1108.
  • the program to be executed by the computer may be a program that performs processing in accordance with the order described in this specification, or may be a program that executes processing in parallel or performs processing when needed, such as when called.
  • the present invention can also be configured as follows.
  • a receiving side device in a communication system comprising one or more processors, the one or more processors configured to: determine the receiving condition according to a receiving situation of a common sequence from a transmitting side by the receiving side device And receiving, by the analog weight parameter, an antenna configuration for transmitting a predetermined pilot signal corresponding to the receiving side device, to send the predetermined pilot signal to the Said the sending side.
  • the communication system includes a plurality of the receiving side devices, each of the receiving side devices having a predetermined pilot signal corresponding thereto, wherein respective predetermined pilot signals corresponding to the respective receiving side devices are orthogonal to each other.
  • the respective predetermined pilot signals corresponding to the respective receiving side devices are simultaneously transmitted to the transmitting side.
  • the predetermined pilot signal is a sounding reference signal.
  • a predetermined pilot signal corresponding to the receiving side device is configured by the transmitting side for the receiving side device.
  • the analog weight parameter indicates a value mode of a plurality of phase shifters connected to the plurality of antennas.
  • Determining the analog weight parameter according to the receiving situation of the receiving side device to the common sequence from the transmitting side includes: setting values of the plurality of phase shifters connected to the plurality of antennas in different value mode to receive the Determining the analog sequence by describing a common sequence and a mode corresponding to values of a plurality of phase shifters capable of obtaining a reception quality of the common sequence satisfying a predetermined condition Heavy parameters.
  • the common sequence is repeatedly transmitted by the transmitting side for multiple times in a first time period, and the one or more processors are further configured to set the same in a different value mode for a common sequence of each transmission.
  • the values of the plurality of phase shifters are respectively received in a common sequence of each transmission.
  • the one or more processors are further configured to set values of the plurality of phase shifters based on the determined analog weight parameters to transmit the predetermined pilot signals at least once during a second time period To the transmitting side.
  • the receiving device operates as a communication terminal, and the receiving device further includes: the plurality of antennas configured to receive the common sequence and transmit the predetermined pilot signal; one or more radio frequency links, Configuring to connect to the plurality of antennas via the plurality of phase shifters; and a memory configured to store a beamform codebook, wherein a value pattern of a set of phase shifters connected to a radio frequency link corresponds to And a codeword in the beamforming codebook, wherein the plurality of antennas are further configured to receive a control instruction from the transmitting side, the control instruction comprising at least one of the following control parameters: a first time period, a number of times the common sequence is repeatedly transmitted, the second time period, and a number of times the predetermined pilot signal is transmitted, wherein the number of times the common sequence is repeatedly transmitted and the beamforming codebook The size is related.
  • the value patterns of the sets of phase shifters connected to the respective radio frequency links are set in the same manner to transmit the predetermined pilot signals to the transmitting side.
  • the one or more processors are further configured to determine the analog weight parameter based on a maximized received signal power criterion or a maximized signal to interference ratio criterion.
  • the one or more processors are further configured to: correct the determined analog weight parameter and determine an antenna configuration for transmitting the predetermined pilot signal based on the corrected analog weight parameter.
  • a transmitting side device for a communication network comprising one or more processors, the one or more processors configured to: generate a common sequence for transmission to a plurality of receiving side devices; for the plurality of receiving side devices And determining, according to a reception condition of a predetermined pilot signal from the receiving side device, an analog weight parameter of the plurality of antennas of the transmitting side device for the receiving side device, wherein the predetermined The pilot signal is sent by the receiving-side device based on the multi-antenna transmission weight parameter of the receiving-side device, where the multi-antenna transmission weight parameter is determined by the receiving-side device according to the receiving condition of the common sequence. of.
  • the one or more processors are further configured to: determine an antenna configuration for transmitting data for the receiving side device based on the determined analog weight parameter to transmit the data to the The receiving side device.
  • the common sequence is broadcast to the plurality of receiving side devices multiple times.
  • the common sequence corresponds to a channel state information reference signal.
  • the analog weight parameter indicates a value mode of a plurality of phase shifters connected to the plurality of antennas of the transmitting side device.
  • Determining the analog weight parameter of the plurality of antennas of the transmitting side device for the receiving side device according to the receiving condition of the predetermined pilot signal from the receiving side device includes: setting the setting in different value mode Determining a value of the plurality of phase shifters to receive the predetermined pilot signal, and determining the mode based on a mode corresponding to a value of a phase shifter capable of obtaining a reception condition of the predetermined pilot signal that satisfies a predetermined condition Simulate weight parameters.
  • the one or more processors are configured to control to repeatedly transmit the common sequence multiple times during a first time period to cause the receiving side device to receive based on the reception of the common sequence of multiple transmissions
  • the multi-antenna transmission weight parameter is determined.
  • the one or more processors are configured to set the plurality of phase shifters in different value patterns for the predetermined pilot signals transmitted by the receiving side device at least once in a second time period The values are received to receive the predetermined pilot signals transmitted each time.
  • the transmitting device operates as a base station, and the transmitting device further includes: the multiple antennas configured to send the common sequence and receive the predetermined pilot signal; and multiple radio frequency links configured to be configured
  • the plurality of phase shifters are coupled to the plurality of antennas; and a memory configured to store a beamform codebook, wherein a value pattern of a set of phase shifters connected to a radio frequency link corresponds to the a codeword in the beamforming codebook, wherein the one or more processors are further configured to generate a control instruction for the receiving side device, the control instruction comprising at least one of the following control parameters: a first time period, a number of times of repeatedly transmitting the common sequence, the second time period, and a number of times the predetermined pilot signal is transmitted, wherein the number of times the predetermined pilot signal is transmitted and the beam are repeatedly transmitted
  • the shape of the codebook is related.
  • the one or more processors are further configured to: correct the determined analog weight parameter and determine an antenna configuration for transmitting the data based on the corrected analog weight parameter.
  • a receiving side device in a communication system comprising: an analog weight parameter determining module, configured to determine an analog weight of a plurality of antennas of the receiving side device according to a receiving situation of the receiving side device to a common sequence from a transmitting side device a parameter; and an antenna configuration module configured to determine, according to the analog weight parameter, a predetermined pilot signal for transmitting the device corresponding to the receiving device An antenna configuration of the number to transmit the predetermined pilot signal to the transmitting side.
  • the analog weight parameter determination module is further configured to: set values of a plurality of phase shifters connected to the plurality of antennas in different value patterns to receive the common sequence; and based on being able to obtain the public
  • the analog weight parameter is determined by a pattern corresponding to values of a plurality of phase shifters of the sequence satisfying the predetermined condition.
  • the common sequence is repeatedly transmitted by the transmitting side a plurality of times.
  • the analog weight parameter determination module is further configured to set the values of the plurality of phase shifters in different value patterns for the common sequence of each transmission to respectively receive the common sequence of each transmission.
  • the antenna configuration module is further configured to set a value of the plurality of phase shifters according to the determined analog weight parameter, thereby transmitting the predetermined pilot signal to the transmitting side at least once.
  • the antenna configuration module is further configured to set the value mode of each group of phase shifters connected to the respective radio frequency links in the same manner to transmit the predetermined pilot signals to the transmitting side.
  • the analog weight parameter determination module is further configured to determine the analog weight parameter according to a maximized received signal power criterion or a maximized signal to interference ratio criterion.
  • the receiving side device further includes a correction module configured to correct the determined analog weight parameter.
  • the antenna configuration module is further configured to determine an antenna configuration for transmitting the predetermined pilot signal based on the corrected analog weight parameter.
  • a transmitting side device for a communication network comprising: a common sequence generating module configured to generate a common sequence to transmit to a plurality of receiving side devices; an analog weight parameter determining module configured to be for the plurality of receiving sides Each of the devices determines an analog weight parameter of the plurality of antennas of the transmitting side device for the receiving side device according to a receiving condition of a predetermined pilot signal from the receiving side device, where The predetermined pilot signal is sent by the receiving-side device based on the multi-antenna transmission weight parameter of the receiving-side device, wherein the multi-antenna transmission weight parameter is received by the receiving-side device according to the public sequence. definite.
  • the transmitting side device further includes an antenna configuration module configured to determine an antenna configuration for transmitting data for the receiving side device according to the determined analog weight parameter to transmit the data to the receiving side device .
  • the analog weight parameter determination module is further configured to: set values of the plurality of phase shifters in different value mode to receive the predetermined pilot signal; and based on being capable of obtaining the predetermined pilot signal The mode corresponding to the value of the phase shifter that satisfies the reception condition of the predetermined condition, The analog weight parameter is determined.
  • the analog weight parameter determining module is further configured to: set, according to the predetermined pilot signal that is sent by the receiving device at least once, the values of the plurality of phase shifters in different value mode to respectively receive The predetermined pilot signal transmitted each time.
  • the transmitting side device further includes a control instruction generating module configured to generate a control instruction for the receiving side device, the control instruction including at least one of the following control parameters: transmitting a time period of the common sequence, repeating The number of times the common sequence is transmitted, the time period during which the predetermined pilot signal is transmitted, and the number of times the predetermined pilot signal is transmitted.
  • the transmitting side device further includes a correction module configured to correct the determined analog weight parameter.
  • the antenna configuration module is further configured to determine an antenna configuration for transmitting the data based on the corrected analog weight parameter.
  • a training method in a communication system comprising: generating a common sequence by a transmitting side device to transmit to a plurality of receiving side devices; each of the plurality of receiving side devices determining the first according to a reception condition of the common sequence Simulating a weight parameter, and determining an antenna configuration for transmitting a predetermined pilot signal corresponding to the receiving side device according to the determined first analog weight parameter to transmit the predetermined pilot signal to the transmitting side device; And the transmitting side device determines a second analog weight parameter for the receiving side device according to the receiving condition of the predetermined pilot signal, and determines, according to the determined second analog weight parameter, that the sending is for the receiving An antenna configuration of data of the side device to transmit the data to the receiving side device.

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Abstract

一种无线通信方法和无线通信设备，该方法包括：由发送侧设备生成公共序列以发送至多个接收侧设备；所述多个接收侧设备中的每一个根据对公共序列的接收情况来确定第一模拟权重参数，并且根据确定的第一模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信号的天线配置，以将预定导频信号发送至发送侧设备；发送侧设备根据对预定导频信号的接收情况来确定针对所述接收侧设备的第二模拟权重参数，并且根据确定的第二模拟权重参数来确定用于发送针对所述接收侧设备的数据的天线配置，以将数据发送至所述接收侧设备。

Description

无线通信方法和无线通信设备 技术领域
本发明涉及一种无线通信方法和无线通信设备，特别地，涉及一种适用于多用户大规模天线系统的波束赋形训练方法以及使用该方法的设备。
背景技术
近年来，毫米波技术和大规模多输入多输出(Massive Multi-Input Multi-Output,MIMO)技术被认为是未来第五代移动通信(5G)的关键技术，因此引起了广泛关注。毫米波频段具有大量可用频谱资源，能够满足日益增长的业务流量需求。此外，由于毫米波的波长较短，使得能够在小范围空间中设置几百甚至上千根天线，更有利于大规模天线技术在现实系统中的应用。
图1示意性地示出了一个单基站多用户毫米波大规模天线系统。如图1所示，基站100配备有M根天线，并且服务于K个用户设备UE1-UE K，每个用户设备配备有N根天线。在传统的全数字预编码架构下(一个射频链路仅连接一个天线单元)，用于K个用户设备的数据被通过一个全数字预编码矩阵W∈CM×K映射到M个射频链路和天线单元上，可以获得最优的预编码性能。然而这种全数字预编码架构需要M个射频链路，从而造成硬件复杂度高、功耗大等问题。因此，图1所示的系统采用全连接混合预编码架构，在此架构下，用于K个用户设备的数据流首先被数字预编码器110利用数字预编码矩阵B(B∈CK×K)映射到K个射频链路(K<M)。各个射频链路的信号经上变频后，经由模拟移相网络120连接到M个天线，从而进行发射。由于每个射频链路对应多个移相器及天线单元而使得单独的一个射频链路可以形成一个波束，因此相比于全数字预编码架构下多个射频链路才能形成一个波束，大大缩减了硬件成本。模拟移相网络120中的移相器的值构成模拟预编码矩阵F。由于移相器只改变信号的相位，不改变其幅度，因此模拟预编码矩阵F∈CM×K满足约束|[F]m,n|2＝M-1。相应地，用户设备UE 1-UE K的各个天线上接收的信号经由移相网络140而连接到各自的一个或多个射频链路上。在该混合预编码架构下，下行信号传输模型可表示为
Figure PCTCN2016112967-appb-000001
其中yk为第k个用户设备的接收信号，Hk为第k个用户设备和基站100之间的下行信道矩阵，F和B分别为模拟预编码矩阵和数字预编码矩阵，其中模拟预编码矩阵F的第k列fk表示针对第k个用户设备的模拟发送权重矢量(例如用于第k个射频链路所连接的多个移相器的相位设置)，wk表示第k个用户设备的接收权重矢量，nk表示高斯白噪声，x表示发送给K个用户设备UE 1-UE K的数据。受器件的限制，模拟发送权重矢量fk和接收权重矢量wk通常从预先定义的码本中选择，更具体地，是分别从基站100的码本Fc和用户设备UE的码本Wc中选择的。
在混合预编码架构下，通常将模拟发送和接收权重矢量与数字预编码矩阵B分开设计，以降低计算复杂度。从码本中选择出针对每个用户设备最优的模拟发送权重矢量/接收权重矢量的过程被称为波束赋形训练。可以采用最大化用户接收功率的准则来进行波束赋形训练，该准则表示如下：
Figure PCTCN2016112967-appb-000002
其中，{wk,opt,fk,opt}表示针对第k个用户设备最优的下行接收权重矢量/下行发送权重矢量。
在获得模拟接收权重矢量/发送权重矢量{wk,opt,fk,opt}之后，可以得到下行等效信道Heq∈CK×K，其中[Heq]i,j＝wi,opt THifj,opt。根据随机矩阵理论，当基站100的天线数目远远大于用户设备UE的数目时(即M>>K)，Heq为主对角占优矩阵，因此可以使用线性数字预编码算法，例如迫零算法(ZF)来设计数字预编码矩阵B，表示如下：
B＝Heq H(HeqHeq H)-1Λ，
其中Λ为对角矩阵，用于用户设备间的发射功率分配。
传统的波束赋形训练机制主要包括物理信道估计、穷尽搜索、多层反馈和单次反馈。
物理信道估计机制通过导频直接估计下行物理信道Hk∈CN×M，然后用户设备根据估计的物理信道计算最优的发送/接收权重矢量，并将发送权重矢量反馈给基站。但是在毫米波系统中，基站和用户设备均配备有大量天线，因此信道估计的复杂度极高，并且由于导频未经波束赋形，导致接收信噪比较低，信道估计的准确度较低。
穷尽搜索机制搜索所有可能的发送/接收权重矢量对，用户设备针对每对发送/接收权重矢量测量信道质量，从而选择最优的权重矢量对，并将发送权重矢量反馈给基站。穷尽搜索机制可以达到最优的性能，但复杂度极高。
多层反馈机制通过预先设计的多层码本，将训练过程分为多层进行，在每层中使用穷尽搜索。由于每层中备选码字数量较小，因而复杂度得到降低。但是多层反馈机制需要向基站多次反馈发送权重矢量，导致额外占用较多的资源。此外由于每个用户设备的训练过程不同，所有用户设备必须逐个单独地进行训练，使得总体复杂度较高。
单次反馈机制将波束赋形训练分为两个流程，首先基站搜索所有可能的发送权重矢量，用户设备使用全向波束接收信号并估计信道质量，从而选择出最优的发送权重矢量并将其反馈给基站。随后，基站固定发送权重矢量，用户搜索最优的接收权重矢量。相比于穷尽搜索机制，单次反馈机制的复杂度得到降低，但同时也造成一定性能损失，此外其复杂度随着用户设备数量的增加而增大。
综上所述，传统的波束赋形训练机制主要面临着复杂度过高的问题，而在毫米波系统中波束赋形训练的复杂度影响着通信建立时间，这在移动通信系统中是一项重要指标。因此，需要一种适用于多用户毫米波大规模天线系统的快速波束赋形训练机制。
出于有助于更好地理解本发明的实施例的目的提供了以上说明。然而应当理解，这并不意味着承认上述说明属于现有技术。上述说明也可能包含了属于本发明实施例的内容。
发明内容
为了解决上述问题，本发明提出了一种通信系统中的接收侧设备，包括一个或多个处理器，所述一个或多个处理器被配置为：根据所述接收侧设备对来自发送侧的公共序列的接收情况来确定所述接收侧设备的多个天线的模拟权重参数；根据所述模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信号的天线配置，以将所述预定导频信号发送至所述发送侧。
本发明还提出了一种用于通信网络的发送侧设备，包括一个或多个处理器，所述一个或多个处理器被配置为：生成公共序列以发送至多个接收 侧设备；针对所述多个接收侧设备中的每一个，根据对来自所述接收侧设备的预定导频信号的接收情况来确定针对所述接收侧设备的、所述发送侧设备的多个天线的模拟权重参数，其中，所述预定导频信号是由所述接收侧设备基于所述接收侧设备的多天线发送权重参数发送的，其中所述多天线发送权重参数是由所述接收侧设备根据对所述公共序列的接收情况确定的。
本发明还提出了一种通信系统中的训练方法，包括：由发送侧设备生成公共序列以发送至多个接收侧设备；所述多个接收侧设备中的每一个根据对所述公共序列的接收情况来确定第一模拟权重参数，并且根据确定的第一模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信号的天线配置，以将所述预定导频信号发送至所述发送侧设备；以及所述发送侧设备根据对所述预定导频信号的接收情况来确定针对所述接收侧设备的第二模拟权重参数，并且根据确定的第二模拟权重参数来确定用于发送针对所述接收侧设备的数据的天线配置，以将所述数据发送至所述接收侧设备。
附图说明
可以通过参考下文中结合附图所给出的描述来更好地理解本发明，其中在所有附图中使用了相同或相似的附图标记来表示相同或者相似的部件。附图连同下面的详细说明一起包含在本说明书中并且形成本说明书的一部分，而且用来进一步说明本发明的优选实施例和解释本发明的原理和优点。在附图中：
图1是本发明所适用的单基站多用户毫米波大规模天线通信系统的示意性结构框图。
图2示意性地示出了基站的全连接移相网络的结构。
图3示意性地示出了基站的子连接移相网络的结构。
图4示意性地示出了配备有多个射频链路的用户设备的结构。
图5示意性地示出了配备有单个射频链路的用户设备的结构。
图6根据本发明的波束赋形训练的一个示例的流程图。
图7是用于说明根据本发明的下行训练的视图。
图8A和8B是用于说明根据本发明的上行训练的视图。
图9是根据本发明的波束赋形训练的另一个示例的流程图。
图10A和10B示出了根据本发明的波束赋形训练与现有技术的性能比较。
图11是示出了计算机硬件的示例配置的框图。
具体实施方式
图1示意地示出了本发明所适用的通信系统的结构框图。如图1所示，在基站100中，K个用户数据流被输入到基带数字预编码器110，数字预编码器110利用数字预编码矩阵B对K个数据流进行数字预编码，以将其以不同的加权系数映射到K条射频链路。数字预编码主要用于在多个数据流复用相同的物理传输资源时消除不同数据流之间的干扰。需要注意的是，由于模拟预编码可以实现在空间上分开的不同波束传输，从而可在一定程度上降低不同传输流之间的干扰，因此在本发明中数字预编码并非是必需的处理。为了降低系统复杂度或降低成本，在一些实施例中可以不设置数字预编码器。另外，数字预编码是在基带部分完成的，因此数字预编码器可以例如由基带处理器来实现，并且因此有时也被称作基带预编码器。此外，模拟预编码是由处理电路控制在射频部分实现的，因此有时也被称作模拟波束赋形。
需要注意的是，在已知的现有技术中已有波束赋形的概念，然而其中大部分是在射频链路与天线单元一一对应的架构下的讨论，并不存在器件约束，从实现的角度而言无需进行反复训练以从固定码本中选择码字供实际传输之用。而且现有技术中通常是仅在基站侧进行波束赋形传输，用户设备侧仅被动接收信号，而无需进行天线配置(例如射频器件)的调整。然而在本发明中，用户设备的射频链路对应多个移相器及天线单元，并在接收或发送信号时采用特定的天线配置方案，以与基站进行配合以实现高质量的信号传输。
经数字预编码后，在K条射频链路中，基带信号被进行上变频、放大、滤波，从而形成射频信号。
K条射频链路连接到模拟移相网络120，移相网络120的M个输出分别与M个天线连接。移相网络120中的移相器的值构成模拟预编码矩阵(或称为模拟波束赋形矩阵)F。与数字预编码不同，模拟波束赋形主要用于提高用户设备的接收信噪比，克服信道路径衰落，因而通常需要针 对不同的用户设备生成不同的波束。
处理器130用于生成或者确定数字预编码矩阵B和模拟预编码矩阵F，也就是说，处理器130用于控制数字预编码处理以及移相网络120中的移相器的配置。可以理解，本文中的处理器130可以实现为一个或者多个高层控制器、基带处理器等处理器，并且可以由不同的处理器分别生成数字预编码矩阵B和模拟预编码矩阵F。
典型地，移相网络120包括全连接移相网络和子连接移相网络两种类型。图2示意地示出了全连接移相网络的结构。如图2所示，每条射频链路连接到M个移相器，每K(K<M)个移相器的输出信号经加法器相加后连接到一个天线单元。图3示意地示出了子连接移相网络的结构。如图3所示，每条射频链路连接到M/K个移相器，每个移相器连接到一个天线单元。
在图1中示意地示出了每个用户设备UE配备有N个接收天线，事实上，各个用户设备UE可以配备不同数量的天线，本发明并不限于此。图4更加详细地示出了用户设备UE的结构。如图4所示，通过N个天线单元接收的信号经由移相网络410而连接至多个射频链路(射频链路数量小于天线单元数量)，然后经滤波、放大、下变频后得到基带接收信号(未示出)。移相网络410的结构与基站侧的移相网络120类似。移相网络410中的移相器的值构成用户设备UE的模拟接收权重矩阵W。此外，与基站侧类似地，由处理器420来配置接收权重矩阵W，即，配置移相网络410中的移相器的值。
此外，图5示出了用户设备UE的另一结构，该结构相比于图4更加简化。在图5中，用户设备UE仅具有一条射频链路，因此通过N个天线接收的信号被相加并输出至该射频链路，而不再需要移相网络。在此情况下，与N个天线相连的N个移相器的值构成用户设备UE的模拟接收权重矢量w。类似地，由处理器510来配置N个移相器的值，即配置接收权重矢量w。
在本发明的示例中，一个权重矢量对应于多个移相器的一种取值模式，该权重矢量的元素表示一组移相器的相位值，而权重矩阵包括分别用于多个射频链路的多个权重矢量。此外，所有可用的权重矢量构成波束赋形码本，换言之，每个权重矢量对应于波束赋形码本中的一个码字。
以上结合图1-图5介绍了根据本发明的通信系统结构以及基站和用 户设备的结构。如上所述，与基站侧的第k个数据流(需要注意，配备有多条射频链路的用户设备可以接收多个数据流)对应的接收信号可表示为：
Figure PCTCN2016112967-appb-000003
其中，Hk为第k个数据流所对应的用户设备与基站之间的下行信道矩阵。B∈CK×K是数字预编码矩阵，通常，数字预编码矩阵B是对角占优矩阵，即对角元素值较大，因此在数字预编码之后，第k个射频链路上的信号将主要来自于第k个数据流。F∈CM×K是模拟预编码矩阵，模拟预编码矩阵F的第k列fk表示用于第k个射频链路(主要承载第k个数据流)的模拟发送权重矢量。在如图2所示的全连接移相网络的结构下，由于每个射频链路与所有天线都连接，因此矢量fk的所有元素均非零。在如图3所示的子连接移相网络的结构下，由于每个射频链路仅与部分天线连接，因此矢量fk只有第
Figure PCTCN2016112967-appb-000004
到第
Figure PCTCN2016112967-appb-000005
个元素非零，其它元素均为零。
此外，wk表示用户设备对于第k个数据流的模拟接收权重矢量。在用户设备侧的移相网络410为全连接移相网络或子连接移相网络的情况下，矢量wk与上述fk类似。
此外，x表示对应于K个数据流的基站发送的信号，nk表示高斯白噪声。
如上所述，由于受到器件约束的限制，模拟发送权重矢量fk和模拟接收权重矢量wk只能从预先定义的码本中选择，即，只能采用预定码本中的某一码字。在本发明中，将基站侧的码本定义为Fc，将用户设备侧的码本定义为Wc。特别地，在子连接移相网络结构下，码本指的是权重矢量中非零元素的所有可能取值集合。
以下将结合图6详细描述根据本发明的波束赋形训练的流程。
如图6所示，首先在步骤S601，基站100通过例如广播信道向其所服务的所有用户设备UE通知下行训练信息，该下行训练信息例如可以包括发送下行训练序列(例如导频信号)的时间段、发送下行训练序列的次数等。其中，下行训练序列由基站100(例如处理器130)生成，并在步骤S602由基站100发送至所有用户设备UE。例如，在本发明应用于高 级长期演进(LTE-A)系统的情况下，该下行训练序列可以是信道状态信息参考信号(CSI-RS)、公共参考信号(CRS)、解调参考信号(DMRS)等，此外广播信道例如可以是广播控制信道(BCCH)。在一个示例中，当下行训练信息中包括发送CSI-RS的时间段，并且包括指示仅在特定子帧上发送CSI-RS的信息时，由于该时间段中包含确定数量的该特定子帧，因此该下行训练信息可以不必包含发送CSI-RS的次数。
在步骤S602，基站100利用全向波束fomni向所有用户设备UE多次广播下行训练序列(CSI-RS)。全向波束fomni被定义为满足
Figure PCTCN2016112967-appb-000006
的模拟发送权重矢量，其中
Figure PCTCN2016112967-appb-000007
表示基站发射天线响应向量，θ和
Figure PCTCN2016112967-appb-000008
分别表示水平方向到达角和垂直方向到达角，C表示常数。
针对基站100某一次发送的下行训练序列，用户设备UE可以估计在采用码本Wc中的某个码字作为模拟接收权重矢量的情况下的等效信道系数。而针对基站100另一次广播的下行训练序列，该用户设备UE可以估计在采用另一码字作为模拟接收权重矢量的情况下的等效信道。这样，由于基站发送下行训练序列的次数(例如P次)与用户设备UE的码本Wc中的码字的数量(即，码本大小)相等，因此通过接收P次发送的下行训练序列，用户设备UE可以对采用码本Wc中所有码字的情况下的等效信道都进行估计。
具体来说，参见图7，示出了基站100利用全向波束fomni将下行训练序列向用户设备UE 1-K广播P次。针对第一次广播的下行训练序列，用户设备UE 1-UE K分别估计在采用码字w1作为接收权重矢量的情况下的等效信道系数，然后针对第二次广播的下行训练序列，用户设备UE 1-UE K分别估计在采用码字w2作为接收权重矢量的情况下的等效信道系数，以此类推，直至针对码本Wc中的P个码字都完成估计。可以理解的是，在多个用户设备各自的码本Wc大小不同的情况下，基站100例如根据具有最大码本的用户设备的码本大小来确定重复广播训练序列的次数，以确保每个用户设备能够进行完整估计。
此外，具有多个射频链路的用户设备(采用全连接结构)可以利用每个射频链路来估计一个码字，因此在接收到基站100一次广播的下行训练序列时可以同时针对多个码字进行估计。理论上，在此情况下基站100可以减少重复发送下行训练序列的次数。但是在实际中，由于同时存在着具有单个射频链路和多个射频链路的用户设备，为了确保单射频链路的用 户设备能够进行完整估计，基站100仍需要按照用户设备的码本大小P来重复广播下行训练序列。
在用户设备UE针对所有码字完成等效信道的估计后，可以根据估计结果选择出使得下行训练序列的接收质量满足预定条件的下行接收权重矢量，或者优选地，选择使得接收质量最好的接收权重矢量，作为自身将在通信中采用的下行接收权重矢量，如图6的步骤S603所示。用于选择的准则可以包括：1)最大化接收信号功率准则，2)最大化信干比准则，它们分别适用于用户设备UE配备有单个射频链路和多个射频链路的情形。
例如，当用户设备UE配备有单个射频链路时，最大化接收信号功率准则可以表示如下：
{wopt}＝argmax||wTHfomni||s.t.w∈Wc,
其中，w表示为单个射频链路采用的下行接收权重矢量，如上所述，w选自码本Wc中的各个码字，Wc表示用户设备中预定的模拟波束赋形码本。H∈CN×M表示基站和用户设备间的下行信道矩阵(N和M分别表示用户设备和基站配备的天线数量)，fomni表示基站采用的全向波束。
进一步地，基于上下行信道特性的对称性，可以根据如上确定的wopt来配置与用户设备UE的单个射频链路相连的移相器的值，以向基站发送上行训练序列(将在后文描述)。
当用户设备UE配备有多个射频链路时，最大化信干比准则可以表示如下：
Figure PCTCN2016112967-appb-000009
其中，
Figure PCTCN2016112967-appb-000010
NRF表示用户设备配备的射频链路的数量，wj表示为第j个射频链路采用的模拟接收权重矢量，如上所述，wj选自码本Wc中的各个码字，Wc表示用户设备中预定的模拟波束赋形码本。H∈CN×M表示基站和用户设备之间的下行信道矩阵，fomni表示基站采用的全向波束。
可以根据如上确定的wj,opt来配置与用户设备UE的第j个射频链路相连的一组移相器的值，以向基站发送上行训练序列(将在后文描述)。在一个示例中，可以利用该wj,opt来配置与用户设备UE的各个射频链路相连的各组移相器的值，也就是说，对各组移相器进行相同的配置。
作为一个扩展示例，具有多个射频链路的用户设备UE可以通过例如LTE-A通信协议中规定的双连接(Dual Connectivity)技术同时与两个基站(例如一个宏基站和一个小基站)进行训练，在此情形下，用户设备UE可以分别针对两个基站获得模拟接收权重矢量w1和w2，然后用户设备UE针对基站1利用确定的权重矢量w1来配置与射频链路1相连的一组移相器的值，并且针对基站2利用确定的权重矢量w2来配置与射频链路2相连的一组移相器的值，从而实现同时与两个基站的模拟波束赋形传输。
当用户设备UE在步骤S603获得用于通信的下行接收权重矢量后，下行训练过程结束。
此后，用户设备UE在步骤S604根据所确定的下行接收权重矢量来计算上行发送权重矢量，从而利用所计算的上行发送权重矢量来发送上行训练序列，开始上行训练过程。对于时分双工(TDD)系统，由于上行信道和下行信道的信道特性具有互易性，因此可以直接将所确定的接收权重矢量作为用户设备UE的上行发送权重矢量。而对于频分双工(FDD)系统，则可以对接收权重矢量进行矫正以得到上更准确的行发送权重矢量，这将在下文详细描述。
在步骤S605，基站100向所有用户设备UE广播上行训练信息，该上行训练信息例如可以包括发送上行训练序列的时间段、发送上行训练序列的次数等。在一个示例中，当上行训练信息中包括发送上行训练序列的时间段，并且包括指示在每个子帧中发送一个上行训练序列的信息时，由于该时间段中包含确定数量的子帧，因此该上行训练信息可以不必包含发送上行训练序列的次数。在另一示例中，基站在用户设备接入网络时已将有关射频链路、波束赋形码本等的信息包含在系统信息中通知给用户设备，在此情况下，该上行训练信息也可以不必包含发送上行训练序列的次数。在另一些示例中，可以预先设置在下行训练结束后经过预定时间之后开始上行训练，因此基站100可以无需专门发送上行训练信息。此外，基站100利用特定信道例如RRC信令等专用信令，将对用户设备UE分配的上行训练序列通知给用户设备UE。
然后，用户设备UE根据在步骤S604获得的上行发送权重矢量，以及在步骤S605获知的上行训练序列以及上行训练信息，向基站100发送上行训练序列，如步骤S606所示。特别地，各个用户设备UE使用的上行训练序列相互正交，包括训练序列本身相互正交以及物理传输资源相互正交中的至少一个。上行训练序列例如可以是正交导频信号，如探测参考信号(SRS)。在上行训练序列是SRS的情况下，由于用户设备基于下行训练结果对SRS进行波束赋形并进行发送，因此在对基站提供资源调度参考的同时能够更准确地隐含地反馈下行信道信息，而无需专门的反馈信令开销。
针对每个用户设备UE发送的上行训练序列，基站100估计在采用码本Fc中的各个码字作为上行接收权重矢量的情况下的等效信道系数，并且根据估计结果确定使得上行训练序列的接收质量满足预定条件(或接收质量最优的)的上行接收权重矢量，如步骤S607所示。
特别地，在基站100配置有全连接移相网络的优选示例中，由于基站100通常具有多个射频链路，因此可以同时对多个码字进行估计，即，在每个射频链路采用一个码字作为接收权重矢量的情况下估计等效信道。因此，针对一个用户设备UE一次发送的上行训练序列，基站100可以完成针对KRF个码字的等效信道估计，其中KRF是基站100配备的射频链路的数量。这样，假设基站100中预定的码本Fc的大小为Q，则理论上一个用户设备UE需要发送上行训练序列的次数为Q/KRF。
具体来说，参见图8A，示出了用户设备UE 1-UE K分别使用其对应的上行发送权重矢量w1-wK来多次发送上行训练序列。例如，针对用户设备UE 1以权重矢量w1第一次发送的上行训练序列，基站100由于具有KRF个射频链路，因此可以针对KRF个码字f1，f2…
Figure PCTCN2016112967-appb-000011
来估计等效信道系数。然后对于用户设备UE 1以权重矢量w1第二次发送的上行训练序列，基站100针对另外的KRF个码字
Figure PCTCN2016112967-appb-000012
来估计等效信道系数，以此类推，直至完成对码本Fc中全部Q个码字的估计。对于其它的用户设备UE 2-UE K，基站100的处理与对用户设备UE 1的处理方式相同。
多个用户设备UE 1-UE K发送的上行训练序列在基站100的天线上相互重叠地接收，但由于各个用户设备UE发送的上行训练序列相互正交，因此基站100能够解析出各个用户设备UE发送的序列，并针对各个用户设备UE分别进行上行训练。在此情况下，上行训练过程所消耗的资 源与用户数量无关。因此，可以在可用正交导频信号(上行训练序列)的数量允许的情况下，使尽可能多的用户设备UE同时发送上行训练序列，从而节省总的训练开销。优选的是，在基站100的移相网络120采用图2所示的全连接移相网络结构时，每个射频链路与所有天线相连，因而可以体验所有传输路径上的信号的接收情况，在此情况下，可以使基站100所服务的所有用户设备UE同时发送上行训练序列，从而基站100可以同时针对所有用户设备UE进行上行训练并选择针对各个用户设备UE的接收权重矢量。
另一方面，在基站100的移相网络120采用图3所示的子连接移相网络结构的情况下，可以将基站100的每个射频链路设置为使用相同的接收权重矢量来接收所有用户设备UE发送的上行训练序列，并进行等效信道估计。如图8B所示，针对用户设备UE 1以权重矢量w1第一次发送的上行训练序列，基站100的KRF个射频链路都采用码字f1作为接收权重矢量来进行接收，并估计等效信道系数。然后对于用户设备UE 1以权重矢量w1第二次发送的上行训练序列，基站100的KRF个射频链路都采用码字f2来进行接收并估计等效信道系数，以此类推，直至针对码本Fc中全部Q个码字完成估计。在此情况下，虽然训练开销会稍大于基站100配备有全连接移相网络的情况，但相比于穷尽搜索机制等现有方式仍具有明显优势。
对于某一用户设备UE的上行训练，基站100在针对波束赋形码本Fc中所有Q个码字完成等效信道估计之后，根据估计结果选择使得上行训练序列的接收质量满足预定条件的上行接收权重矢量。选择的准则包括：1)最大化接收信号功率准则，2)最大化信干比准则，它们分别适用于用户设备UE配备单个射频链路和多个射频链路的场景。
当用户设备UE配备有单个射频链路时，最大化接收信号功率准则可以表示如下：
{fopt}＝argmax||fTHw||s.t.f∈Fc,
其中，f表示针对用户设备100所发送的上行训练序列所采用的基站侧接收权重矢量，如上所述，f选自码本Fc中的各个码字，Fc表示基站100中预定的模拟波束赋形码本。H∈CM×N表示用户设备UE和基站100之间的上行信道矩阵(N和M分别表示用户设备和基站配备的天线数量)，w 表示用户设备UE采用的上行发送权重矢量。
可以根据如上确定的fopt来配置与基站100中针对该用户设备UE的RF链路相连的一组移相器的值，以发送针对该用户设备UE的数据(将在后文描述)。
当用户设备UE配备有多个射频链路时，最大化信干比准则可以表示如下：
Figure PCTCN2016112967-appb-000013
其中
Figure PCTCN2016112967-appb-000014
NRF表示用户设备100配备的射频链路的数量，fj表示针对用户设备100的第j个射频链路所采用的基站侧接收权重矢量，如上所述，fj选自码本Fc中的各个码字，Fc表示基站100中预定的模拟波束赋形码本。H∈CM×N表示用户设备和基站100之间的上行信道矩阵，wj表示用户设备100的第j个射频链路采用的发送权重矢量。
可以根据如上确定的fj,opt来配置与基站100中针对该用户设备UE第j个射频链路的射频链路相连的一组移相器的值，以发送针对该用户设备的数据(将在后文描述)。
然后，基站100在步骤S608根据所确定的上行接收权重矢量来计算用于通信的下行发送权重矢量。对于时分双工(TDD)系统，由于上行信道和下行信道的信道特性具有互易性，因此可以直接将所确定的接收权重矢量作为发送权重矢量。而对于频分双工(FDD)系统，则需要对上行接收权重矢量进行矫正以获得下行发送权重矢量。
如步骤S604和S608所述，在FDD系统的情况下，用户设备UE和基站100都需要对所确定的接收权重矢量进行矫正，以得到发送权重矢量，以下将具体描述这一处理。
总体来说，对接收权重矢量的矫正方法与天线配置和码本设计有关。以下给出在常见的线性等距天线阵列和快速傅里叶变换(FFT)码本设计下的一种矫正方法。
假设上行、下行频率对应的电磁波波长分别为λup和λdown，天线间隔 为d。FFT码本由码本矩阵
Figure PCTCN2016112967-appb-000015
给出，矩阵的每一列是一个接收/发送权重矢量，其中Na为天线数量，Nc为码本大小。矩阵C的第i行第m列的元素取值为
Figure PCTCN2016112967-appb-000016
在以上条件下，当用户设备100在步骤S603中确定的下行接收权重矢量是码本矩阵中的第kdown列时，其在步骤S604选择码本矩阵中的第kup列作为用于上行传输的发送权重矢量，其中kup由下式给出：
Figure PCTCN2016112967-appb-000017
此外，当基站100在步骤S607中确定的上行接收权重矢量是码本矩阵中的第kup列时，其在步骤S608选择码本矩阵中的第kdown列作为用于下行传输的发送权重矢量，其中kdown由下式给出：
Figure PCTCN2016112967-appb-000018
当基站100在步骤S608获得下行发送权重矢量后，上行训练过程结束。此后，基站100在步骤S609进行数字预编码处理。
具体来说，基站100首先估计等效信道矩阵，该等效信道矩阵的第(i,j)个元素的最小二乘(LS)估计如下:
Figure PCTCN2016112967-appb-000019
其中,fj,opt是基站100采用的上行接收权重矢量，yj是基站100采用fj,opt时接收的信号序列。wi,opt是第i个用户设备(假设该用户设备具有单个射频链路)在下行训练阶段获得的最优上行发送矢量，Hi是基站与第i个用 户设备之间的下行信道矩阵，Φi是第i个用户设备采用的正交导频。
然后，基站100利用迫零(ZF)算法来计算数字预编码矩阵B。数字预编码矩阵B可以表示如下：
B＝Heq H(HeqHeq H)-1Λ,
其中，Λ是表示用户设备间发射功率分配的对角矩阵。
通过以上处理，基站100已获得数字预编码矩阵B，因此可以对K个数据流进行数字预编码。另一方面，基站100已获得针对各个用户设备UE(或其各个射频链路)的下行发送权重矢量，即，获得模拟预编码矩阵F，因此可以配置模拟移相网络120中的移相器的值。从而，利用上述配置，基站100可以在步骤S610向用户设备UE发送实际的数据(区别于训练序列)。相应地，用户设备UE也可以利用在步骤S603确定的接收权重矢量来接收该实际数据。
需要说明的是，为了清楚起见，在对图6所示流程的描述中描述了由基站100和用户设备UE执行各个步骤，但本领域技术人员易于理解的是，该各个步骤的处理或计算可以由基站100的处理器130或用户设备UE的处理器420,510来执行。
图6所示的波束赋形训练处理可以适用于基站100与用户设备UE之间周期性的训练模式。即，基站100定期地向用户设备UE通知下行训练信息(如步骤S601所示)，从而开始训练过程。图9示出了非周期训练模式下的波束赋形训练过程。
如图9所示，用户设备100在步骤S901执行信道质量测量。当测量的信道质量低于预定阈值时，用户设备100向基站100主动发送训练请求，如步骤S902所示。响应于用户设备UE的请求，与步骤S601类似地，基站100在步骤S903向用户设备UE广播下行训练信息，从而开始训练过程。此后的步骤S904-S912与图6中的步骤S602-S610相同，故在此不再赘述。
以上已经结合附图对本发明的实施方式进行了详细描述。根据本发明，在下行训练过程中，由基站广播下行训练序列，所有用户设备可以同时参加训练，所需的探测波束对的数量(Number of Probing Pair，NPP)为P，其中P为用户设备中的波束赋形码本大小。在上行训练过程中，具有正交的上行训练序列的所有用户设备可以同时参加训练，并且基站配备的KRF个射频链路可以针对不同的码字同时进行等效信道估计，因此所需 的探测波束对的数量为Q/KRF，其中Q为基站的波束赋形码本大小。因此，根据本发明的波束赋形训练机制的总体复杂度为Q/KRF+P，并且其复杂度不随用户数量的增加而增大，因此非常适用于多用户毫米波通信系统。此外，根据本发明的波束赋形训练机制不需要用户设备对基站的反馈操作。
图10A和10B分别示出了在不同信道条件下，根据本发明的快速多用户波束赋形训练机制和现有的穷尽搜索机制和单次反馈机制分别能够实现的用户平均下行可达速率。在图中，横坐标表示信噪比，纵坐标表示平均下行可达速率，其中Ncl表示信道散射簇的数目，Nray表示每个散射簇中包含的子径的数目，τ表示训练序列长度。从图中可以看出，当毫米波信道的散射体数量较少，即信道较为稀疏时，快速多用户波束赋形训练机制和单次反馈机制几乎逼近了穷尽搜索机制的最优性能。随着信道散射体数量的增加，这两种方案出现很小的性能损失，但本发明的波束赋形训练机制的性能仍优于单次反馈机制的性能。此外，随着信噪比的增加，在有噪声环境下本发明的波束赋形训练机制的性能迅速收敛到无噪声环境下的性能，即，该机制的性能上界。
本发明能够应用于各种产品。例如，上述实施例中的基站可以被实现为任何类型的演进型节点B(eNB)，诸如宏eNB和小eNB。小eNB可以为覆盖比宏小区小的小区的eNB，诸如微微eNB、微eNB和家庭(毫微微)eNB。代替地，基站可以被实现为任何其他类型的基站，诸如NodeB和基站收发台(BTS)。基站可以包括：被配置为控制无线通信的主体(也称为基站设备)；以及设置在与主体不同的地方的一个或多个远程无线头端(RRH)。另外，各种类型的终端也可以通过暂时地或半持久性地执行基站功能而作为基站工作。
另一方面，上述实施例中的用户设备例如可以被实现为通信终端(诸如智能电话、平板个人计算机(PC)、笔记本式PC、便携式游戏终端、便携式/加密狗型移动路由器和数字摄像装置)，或者车载终端(诸如汽车导航设备)。用户设备还可以被实现为执行机器对机器(M2M)通信的终端，也称为机器类型通信(MTC)终端。此外，用户设备也可以是安装在上述终端中的每个终端上的无线通信模块(诸如包括单个晶片的集成电路模块)。
此外，本发明中的处理器可以实现为基带处理器或者基带处理器与通用处理器的组合，例如实现为中央处理单元(CPU)或数字信号处理器 (DSP)。
本文中所描述的各个设备或模块仅是逻辑意义上的，并不严格对应于物理设备或实体。例如，本文所描述的每个模块的功能可能由多个物理实体来实现，或者，本文所描述的多个模块的功能可能由单个物理实体来实现。此外需要说明的是，在一个实施例中描述的特征、部件、元素、步骤等并不局限于该实施例，而是也可应用于其它实施例，例如替代其它实施例中的特定特征、部件、元素、步骤等，或者与其相结合。
在上述实施例中由每个设备或模块执行的一系列处理可以由软件、硬件或者软件和硬件的组合来实现。包括在软件中的程序可以事先存储在每个设备的内部或外部所设置的存储介质中。作为一个示例，在执行期间，这些程序被写入随机存取存储器(RAM)并且由处理器(例如CPU)来执行。
图11是示出了根据程序执行上述处理的计算机硬件的示例配置框图。
在计算机1100中，中央处理单元(CPU)1101、只读存储器(ROM)1102以及随机存取存储器(RAM)1103通过总线1104彼此连接。
输入/输出接口1105进一步与总线1104连接。输入/输出接口1105连接有以下组件：以键盘、鼠标、麦克风等形成的输入单元1106；以显示器、扬声器等形成的输出单元1107；以硬盘、非易失性存储器等形成的存储单元1108；以网络接口卡(诸如局域网(LAN)卡、调制解调器等)形成的通信单元1109；以及驱动移动介质1111的驱动器1110，该移动介质1111诸如是磁盘、光盘、磁光盘或半导体存储器。
在具有上述结构的计算机中，CPU 1101将存储在存储单元1108中的程序经由输入/输出接口1105和总线1104加载到RAM 1103中，并且执行该程序，以便执行上述处理。
要由计算机(CPU 1101)执行的程序可以被记录在作为封装介质的移动介质1111上，该封装介质以例如磁盘(包括软盘)、光盘(包括压缩光盘-只读存储器(CD-ROM))、数字多功能光盘(DVD)等)、磁光盘、或半导体存储器来形成。此外，要由计算机(CPU 1101)执行的程序也可以经由诸如局域网、因特网、或数字卫星广播的有线或无线传输介质来提供。
当移动介质1111安装在驱动器1110中时，可以将程序经由输入/输出 接口1105安装在存储单元1108中。另外，可以经由有线或无线传输介质由通信单元1109来接收程序，并且将程序安装在存储单元1108中。可替选地，可以将程序预先安装在ROM 1102或存储单元1108中。
要由计算机执行的程序可以是根据本说明书中描述的顺序来执行处理的程序，或者可以是并行地执行处理或当需要时(诸如，当调用时)执行处理的程序。
以上已经结合附图详细描述了本发明的实施例以及技术效果，但是本发明的范围不限于此。本领域普通技术人员应该理解的是，取决于设计要求和其他因素，在不偏离本发明的原理和精神的情况下，可以对本文中所讨论的实施方式进行各种修改或变化。本发明的范围由所附权利要求或其等同方案来限定。
此外，本发明也可以被配置如下。
一种通信系统中的接收侧设备，包括一个或多个处理器，所述一个或多个处理器被配置为：根据所述接收侧设备对来自发送侧的公共序列的接收情况来确定所述接收侧设备的多个天线的模拟权重参数；根据所述模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信号的天线配置，以将所述预定导频信号发送至所述发送侧。
所述通信系统包括多个所述接收侧设备，每个所述接收侧设备具有与其对应的预定导频信号，其中，与各个接收侧设备对应的各个预定导频信号相互正交。
与各个接收侧设备对应的各个预定导频信号被同时发送至所述发送侧。
所述预定导频信号是探测参考信号。
与所述接收侧设备对应的预定导频信号是由所述发送侧为所述接收侧设备配置的。
所述模拟权重参数指示与所述多个天线相连的多个移相器的取值模式。
根据所述接收侧设备对来自发送侧的公共序列的接收情况来确定模拟权重参数包括：以不同的取值模式来设置与所述多个天线相连的多个移相器的值，以接收所述公共序列，以及基于能够获得所述公共序列的满足预定条件的接收质量的多个移相器的值所对应的模式，来确定所述模拟权 重参数。
所述公共序列被所述发送侧在第一时间段内多次重复发送，所述一个或多个处理器还被配置为针对各次发送的公共序列，以不同的取值模式来设置所述多个移相器的值以分别接收各次发送的公共序列。
所述一个或多个处理器还被配置为根据确定的所述模拟权重参数来设置所述多个移相器的值，从而在第二时间段内将所述预定导频信号至少一次地发送至所述发送侧。
所述接收侧设备工作为通信终端，所述接收侧设备还包括：所述多个天线，被配置为接收所述公共序列以及发送所述预定导频信号；一个或多个射频链路，被配置为经由所述多个移相器连接至所述多个天线；以及存储器，被配置为存储波束赋形码本，其中，与一个射频链路相连的一组移相器的取值模式对应于所述波束赋形码本中的一个码字，其中，所述多个天线还被配置为接收来自所述发送侧的控制指令，所述控制指令包括以下控制参数中至少之一：所述第一时间段、重复发送所述公共序列的次数、所述第二时间段、以及发送所述预定导频信号的次数，其中，重复发送所述公共序列的次数与所述波束赋形码本大小有关。
与各个射频链路相连的各组移相器的取值模式被以相同的方式设置，以将所述预定导频信号发送至所述发送侧。
所述一个或多个处理器还被配置为：根据最大化接收信号功率准则或最大化信号干扰比准则来确定所述模拟权重参数。
所述一个或多个处理器还被配置为：对确定的所述模拟权重参数进行矫正，并且根据经矫正的模拟权重参数来确定用于发送所述预定导频信号的天线配置。
一种用于通信网络的发送侧设备，包括一个或多个处理器，所述一个或多个处理器被配置为：生成公共序列以发送至多个接收侧设备；针对所述多个接收侧设备中的每一个，根据对来自所述接收侧设备的预定导频信号的接收情况来确定针对所述接收侧设备的、所述发送侧设备的多个天线的模拟权重参数，其中，所述预定导频信号是由所述接收侧设备基于所述接收侧设备的多天线发送权重参数发送的，其中所述多天线发送权重参数是由所述接收侧设备根据对所述公共序列的接收情况确定的。
所述一个或多个处理器还被配置为：根据确定的模拟权重参数来确定用于发送针对所述接收侧设备的数据的天线配置，以将所述数据发送至所 述接收侧设备。
所述公共序列被以多次广播至所述多个接收侧设备。
所述公共序列对应于信道状态信息参考信号。
所述模拟权重参数指示与所述发送侧设备的多个天线相连的多个移相器的取值模式。
根据对来自所述接收侧设备的预定导频信号的接收情况来确定针对所述接收侧设备的、所述发送侧设备的多个天线的模拟权重参数包括：以不同的取值模式来设置所述多个移相器的值，以接收所述预定导频信号，以及基于能够获得所述预定导频信号的满足预定条件的接收情况的移相器的值所对应的模式，来确定所述模拟权重参数。
所述一个或多个处理器被配置为进行控制以在第一时间段内多次重复发送所述公共序列，以使所述接收侧设备根据对多次发送的所述公共序列的接收情况来确定所述多天线发送权重参数。
所述一个或多个处理器被配置为针对所述接收侧设备在第二时间段内至少一次地发送的所述预定导频信号，以不同的取值模式来设置所述多个移相器的值以分别接收各次发送的所述预定导频信号。
所述发送侧设备工作为基站，所述发送侧设备还包括：所述多个天线，被配置为发送所述公共序列以及接收所述预定导频信号；多个射频链路，被配置为经由所述多个移相器连接至所述多个天线；以及存储器，被配置为存储波束赋形码本，其中，与一个射频链路相连的一组移相器的取值模式对应于所述波束赋形码本中的一个码字，其中，所述一个或多个处理器还被配置为生成针对所述接收侧设备的控制指令，所述控制指令包括以下控制参数中至少之一：所述第一时间段、重复发送所述公共序列的次数、所述第二时间段、以及发送所述预定导频信号的次数，其中，重复发送所述预定导频信号发送的次数与所述波束赋形码本大小有关。
所述一个或多个处理器还被配置为：对确定的所述模拟权重参数进行矫正，并且根据经矫正的模拟权重参数来确定用于发送所述数据的天线配置。
一种通信系统中的接收侧设备，包括：模拟权重参数确定模块，配置为根据所述接收侧设备对来自发送侧的公共序列的接收情况来确定所述接收侧设备的多个天线的模拟权重参数；以及天线配置模块，配置为根据所述模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信 号的天线配置，以将所述预定导频信号发送至所述发送侧。
所述模拟权重参数确定模块还被配置为：以不同的取值模式来设置与所述多个天线相连的多个移相器的值，以接收所述公共序列；以及基于能够获得所述公共序列的满足预定条件的接收质量的多个移相器的值所对应的模式，来确定所述模拟权重参数。
所述公共序列被所述发送侧多次重复发送。所述模拟权重参数确定模块还被配置为：针对各次发送的公共序列，以不同的取值模式来设置所述多个移相器的值以分别接收各次发送的公共序列。
所述天线配置模块还被配置为：根据确定的所述模拟权重参数来设置所述多个移相器的值，从而将所述预定导频信号至少一次地发送至所述发送侧。
所述天线配置模块还被配置为：以相同的方式设置与各个射频链路相连的各组移相器的取值模式，以将所述预定导频信号发送至所述发送侧。
所述模拟权重参数确定模块还被配置为：根据最大化接收信号功率准则或最大化信号干扰比准则来确定所述模拟权重参数。
所述接收侧设备还包括矫正模块，其被配置为对确定的所述模拟权重参数进行矫正。所述天线配置模块还配置为根据经矫正的模拟权重参数来确定用于发送所述预定导频信号的天线配置。
一种用于通信网络的发送侧设备，包括：公共序列生成模块，其被配置为生成公共序列以发送至多个接收侧设备；模拟权重参数确定模块，其被配置为针对所述多个接收侧设备中的每一个，根据对来自所述接收侧设备的预定导频信号的接收情况来确定针对所述接收侧设备的、所述发送侧设备的多个天线的模拟权重参数，其中，所述预定导频信号是由所述接收侧设备基于所述接收侧设备的多天线发送权重参数发送的，其中所述多天线发送权重参数是由所述接收侧设备根据对所述公共序列的接收情况确定的。
所述发送侧设备还包括天线配置模块，其被配置为根据确定的模拟权重参数来确定用于发送针对所述接收侧设备的数据的天线配置，以将所述数据发送至所述接收侧设备。
所述模拟权重参数确定模块还被配置为：以不同的取值模式来设置所述多个移相器的值，以接收所述预定导频信号；以及基于能够获得所述预定导频信号的满足预定条件的接收情况的移相器的值所对应的模式，来确 定所述模拟权重参数。
所述模拟权重参数确定模块还被配置为：针对所述接收侧设备至少一次地发送的所述预定导频信号，以不同的取值模式来设置所述多个移相器的值以分别接收各次发送的所述预定导频信号。
所述发送侧设备还包括控制指令生成模块，其被配置为生成针对所述接收侧设备的控制指令，所述控制指令包括以下控制参数中至少之一：发送所述公共序列的时间段、重复发送所述公共序列的次数、发送所述预定导频信号的时间段、以及发送所述预定导频信号的次数。
所述发送侧设备还包括矫正模块，其被配置为对确定的所述模拟权重参数进行矫正。所述天线配置模块还配置为根据经矫正的模拟权重参数来确定用于发送所述数据的天线配置。
一种通信系统中的训练方法，包括：由发送侧设备生成公共序列以发送至多个接收侧设备；所述多个接收侧设备中的每一个根据对所述公共序列的接收情况来确定第一模拟权重参数，并且根据确定的第一模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信号的天线配置，以将所述预定导频信号发送至所述发送侧设备；以及所述发送侧设备根据对所述预定导频信号的接收情况来确定针对所述接收侧设备的第二模拟权重参数，并且根据确定的第二模拟权重参数来确定用于发送针对所述接收侧设备的数据的天线配置，以将所述数据发送至所述接收侧设备。

Claims (23)

  1. 一种通信系统中的接收侧设备，包括一个或多个处理器，所述一个或多个处理器被配置为：
    根据所述接收侧设备对来自发送侧的公共序列的接收情况来确定所述接收侧设备的多个天线的模拟权重参数；
    根据所述模拟权重参数来确定用于发送与所述接收侧设备对应的预定导频信号的天线配置，以将所述预定导频信号发送至所述发送侧。
  2. 根据权利要求1所述的接收侧设备，其中，所述通信系统包括多个所述接收侧设备，每个所述接收侧设备具有与其对应的预定导频信号，
    其中，与各个接收侧设备对应的各个预定导频信号相互正交。
  3. 根据权利要求2所述的接收侧设备，其中，与各个接收侧设备对应的各个预定导频信号被同时发送至所述发送侧。
  4. 根据权利要求1所述的接收侧设备，其中，所述预定导频信号是探测参考信号。
  5. 根据权利要求1所述的接收侧设备，其中，与所述接收侧设备对应的预定导频信号是由所述发送侧为所述接收侧设备配置的。
  6. 根据权利要求1所述的接收侧设备，其中，所述模拟权重参数指示与所述多个天线相连的多个移相器的取值模式。
  7. 根据权利要求6所述的接收侧设备，其中，根据所述接收侧设备对来自发送侧的公共序列的接收情况来确定模拟权重参数包括：
    以不同的取值模式来设置与所述多个天线相连的多个移相器的值，以接收所述公共序列，以及
    基于能够获得所述公共序列的满足预定条件的接收质量的多个移相器的值所对应的模式，来确定所述模拟权重参数。
  8. 根据权利要求7所述的接收侧设备，其中，所述公共序列被所述发送侧在第一时间段内多次重复发送，所述一个或多个处理器还被配置为针对各次发送的公共序列，以不同的取值模式来设置所述多个移相器的值以分别接收各次发送的公共序列。
  9. 根据权利要求7所述的接收侧设备，其中，所述一个或多个处理器还被配置为根据确定的所述模拟权重参数来设置所述多个移相器的值，从而在第二时间段内将所述预定导频信号至少一次地发送至所述发送侧。
  10. 根据权利要求7-9中任一项所述的接收侧设备，其中，所述接收侧设备工作为通信终端，所述接收侧设备还包括：
    所述多个天线，被配置为接收所述公共序列以及发送所述预定导频信号；
    一个或多个射频链路，被配置为经由所述多个移相器连接至所述多个天线；以及
    存储器，被配置为存储波束赋形码本，
    其中，与一个射频链路相连的一组移相器的取值模式对应于所述波束赋形码本中的一个码字，
    其中，所述多个天线还被配置为接收来自所述发送侧的控制指令，所述控制指令包括以下控制参数中至少之一：所述第一时间段、重复发送所述公共序列的次数、所述第二时间段、以及发送所述预定导频信号的次数，
    其中，重复发送所述公共序列的次数与所述波束赋形码本大小有关。
  11. 根据权利要求10所述的接收侧设备，其中，与各个射频链路相连的各组移相器的取值模式被以相同的方式设置，以将所述预定导频信号发送至所述发送侧。
  12. 根据权利要求7所述的接收侧设备，其中，所述一个或多个处理器还被配置为：根据最大化接收信号功率准则或最大化信号干扰比准则来确定所述模拟权重参数。
  13. 根据权利要求1所述的接收侧设备，其中，所述一个或多个处理器还被配置为：对确定的所述模拟权重参数进行矫正，并且根据经矫正的模拟权重参数来确定用于发送所述预定导频信号的天线配置。
  14. 一种用于通信网络的发送侧设备，包括一个或多个处理器，所述一个或多个处理器被配置为：
    生成公共序列以发送至多个接收侧设备；
    针对所述多个接收侧设备中的每一个，根据对来自所述接收侧设备的预定导频信号的接收情况来确定针对所述接收侧设备的、所述发送侧设备 的多个天线的模拟权重参数，
    其中，所述预定导频信号是由所述接收侧设备基于所述接收侧设备的多天线发送权重参数发送的，其中所述多天线发送权重参数是由所述接收侧设备根据对所述公共序列的接收情况确定的。
  15. 根据权利要求14所述的发送侧设备，其中，所述一个或多个处理器还被配置为：根据确定的模拟权重参数来确定用于发送针对所述接收侧设备的数据的天线配置，以将所述数据发送至所述接收侧设备。
  16. 根据权利要求14所述的发送侧设备，其中，所述公共序列被以多次广播至所述多个接收侧设备。
  17. 根据权利要求14所述的发送侧设备，其中，所述公共序列对应于信道状态信息参考信号。
  18. 根据权利要求14所述的发送侧设备，其中，所述模拟权重参数指示与所述发送侧设备的多个天线相连的多个移相器的取值模式。
  19. 根据权利要求18所述的发送侧设备，其中，根据对来自所述接收侧设备的预定导频信号的接收情况来确定针对所述接收侧设备的、所述发送侧设备的多个天线的模拟权重参数包括：
    以不同的取值模式来设置所述多个移相器的值，以接收所述预定导频信号，以及
    基于能够获得所述预定导频信号的满足预定条件的接收情况的移相器的值所对应的模式，来确定所述模拟权重参数。
  20. 根据权利要求14所述的发送侧设备，其中，所述一个或多个处理器被配置为进行控制以在第一时间段内多次重复发送所述公共序列，以使所述接收侧设备根据对多次发送的所述公共序列的接收情况来确定所述多天线发送权重参数。
  21. 根据权利要求19所述的发送侧设备，其中，所述一个或多个处理器被配置为针对所述接收侧设备在第二时间段内至少一次地发送的所述预定导频信号，以不同的取值模式来设置所述多个移相器的值以分别接收各次发送的所述预定导频信号。
  22. 根据权利要求19-21中任一项所述的发送侧设备，其中，所述发送侧设备工作为基站，所述发送侧设备还包括：
    所述多个天线，被配置为发送所述公共序列以及接收所述预定导频信 号；
    多个射频链路，被配置为经由所述多个移相器连接至所述多个天线；以及
    存储器，被配置为存储波束赋形码本，
    其中，与一个射频链路相连的一组移相器的取值模式对应于所述波束赋形码本中的一个码字，
    其中，所述一个或多个处理器还被配置为生成针对所述接收侧设备的控制指令，所述控制指令包括以下控制参数中至少之一：所述第一时间段、重复发送所述公共序列的次数、所述第二时间段、以及发送所述预定导频信号的次数，
    其中，重复发送所述预定导频信号发送的次数与所述波束赋形码本大小有关。
  23. 根据权利要求15所述的发送侧设备，其中，所述一个或多个处理器还被配置为：对确定的所述模拟权重参数进行矫正，并且根据经矫正的模拟权重参数来确定用于发送所述数据的天线配置。
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