WO2019061186A1 - 一种逆变器的pwm控制信号同步方法及逆变器和电网系统 - Google Patents

一种逆变器的pwm控制信号同步方法及逆变器和电网系统 Download PDF

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Publication number
WO2019061186A1
WO2019061186A1 PCT/CN2017/104067 CN2017104067W WO2019061186A1 WO 2019061186 A1 WO2019061186 A1 WO 2019061186A1 CN 2017104067 W CN2017104067 W CN 2017104067W WO 2019061186 A1 WO2019061186 A1 WO 2019061186A1
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Prior art keywords
phase
voltage
inverter
carrier
preset
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Ceased
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PCT/CN2017/104067
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English (en)
French (fr)
Inventor
袁红文
许富强
刘方诚
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Huawei Technologies Co Ltd
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Huawei Technologies Co Ltd
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Priority to EP17926771.1A priority Critical patent/EP3681007B1/en
Priority to EP22185955.6A priority patent/EP4148942B1/en
Priority to PCT/CN2017/104067 priority patent/WO2019061186A1/zh
Priority to CN201780088966.7A priority patent/CN110462963B/zh
Priority to ES22185955T priority patent/ES2988039T3/es
Publication of WO2019061186A1 publication Critical patent/WO2019061186A1/zh
Anticipated expiration legal-status Critical
Priority to US16/833,969 priority patent/US11223205B2/en
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/38—Arrangements for feeding a single network from two or more generators or sources in parallel; Arrangements for feeding already energised networks from additional generators or sources in parallel
    • H02J3/40—Synchronisation of generators for connection to a network or to another generator
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/38—Arrangements for feeding a single network from two or more generators or sources in parallel; Arrangements for feeding already energised networks from additional generators or sources in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/493—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode the static converters being arranged for operation in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy
    • Y02E10/56—Power conversion systems, e.g. maximum power point trackers

Definitions

  • the present application relates to the field of power technologies, and in particular, to a PWM control signal synchronization method for an inverter, and an inverter and a power grid system.
  • the inverter is a power conversion device that converts direct current into alternating current, and is widely used in the modern power industry. In some industrial applications, such as photovoltaic electric fields, more and more inverters are connected in parallel as the installed capacity increases.
  • the PWM (pulse width modulation) carrier phase is not synchronized due to the difference of the DSP (digital signal processor) crystal oscillator in each inverter, making the inverse
  • the PWM control signals of the transformers are not synchronized, and the final result is that high frequency ripple currents will be generated between the inverters.
  • the high-frequency circulating current is superimposed on the inverter's output fundamental current, causing severe distortion. Current distortion not only increases inverter losses, reduces system efficiency, but also threatens the internal device safety of the inverter.
  • Embodiments of the present application provide a PWM control signal synchronization method for an inverter, and an inverter and a power grid system, which can realize PWM control signal synchronization of an inverter connected to the power grid.
  • a method for synchronizing a PWM control signal of an inverter is provided.
  • the DC voltage terminal of the inverter circuit of the inverter is connected to an external power source, and the AC voltage terminal of the inverter circuit of the inverter is connected to the AC common connection point of the power grid.
  • the method includes: obtaining a phase ⁇ of an alternating voltage of the power grid; and determining a phase period T ⁇ of a phase of the alternating voltage that changes in a preset threshold phase interval when the phase ⁇ of the alternating voltage is detected to satisfy a threshold phase, wherein the threshold phase a start phase value of the preset threshold phase interval; calculating a period value T c of the preset carrier according to the preset carrier ratio N T and the time period T ⁇ ; and generating the preset carrier C according to the period value T c of the preset carrier 0 (t); generating a PWM control signal of the inverter according to the PWM modulation signal and the preset carrier C 0 (t), so that the inverter circuit of the inverter converts the DC voltage of the external DC power source into the power grid according to the PWM control signal AC voltage.
  • An exemplary embodiment is: obtaining a phase ⁇ of an AC voltage of the power grid, comprising: phase-locking an AC voltage of the power grid, obtaining a phase waveform of the grid voltage, and acquiring the AC voltage in the phase waveform Phase.
  • the phase voltage of the grid voltage is obtained by phase-locking the AC voltage of the power grid, and at least includes the following two methods:
  • Manner 1 Phase lock is performed on the grid voltage by using a predetermined phase-locking algorithm to obtain a phase waveform of the grid voltage.
  • the predetermined phase-locking algorithm includes at least one of the following: a single-step coordinate system software phase-locked loop, and a single step of the symmetric component method. Coordinate system software phase-locked loop, decoupling software phase-locked loop based on double-synchronous coordinate system, based on double second-order generalized product The software phase-locked loop of the divider.
  • Method 2 acquiring any phase voltage of the AC voltage of the power grid; detecting a voltage zero-crossing point and a voltage frequency of the any phase voltage, and acquiring the voltage zero-crossing point according to the voltage zero-crossing point and the voltage frequency a waveform, and obtaining a positive voltage period on both sides of the voltage zero-crossing point and a second waveform corresponding to the negative voltage period; acquiring a phase waveform of the AC voltage of the power grid according to the first waveform and the second waveform.
  • An exemplary embodiment is: when detecting that the phase ⁇ of the alternating voltage satisfies a threshold phase, determining a time period T ⁇ in which the phase of the alternating voltage changes in a preset threshold phase interval includes: when the alternating current is detected When the phase ⁇ of the voltage satisfies the threshold phase, the counting is triggered; the counting period value between the current triggering count and the next triggering count is obtained; and the phase of the alternating voltage is determined according to the counting period value and the single counting duration ⁇ t Let the time period T ⁇ of the threshold phase interval change.
  • An exemplary embodiment is, according to the preset value of the carrier period T c generates scheduled carrier C 0 (t), comprising: a theoretical value of T c in accordance with the carrier cycle, the preset initial phase and a preset carrier The carrier amplitude generates the preset carrier C 0 (t).
  • An exemplary embodiment is that generating the PWM control signal of the inverter from the preset carrier C 0 (t) according to the PWM modulation signal comprises: replacing the preset carrier C 0 (t) with the current Inverter carrier C(t); generates a PWM control signal of the inverter according to the PWM modulated signal and the replaced current inverter carrier C(t).
  • An exemplary implementation manner is: generating the PWM control signal of the inverter according to the PWM modulation signal and the preset carrier C 0 (t), including: using the preset carrier C 0 (t) with current Inverter carrier C(t) comparison generates a carrier adjustment amount; updating the current inverter carrier C(t) according to the carrier adjustment amount; and updating the current inverter carrier C(t) according to the PWM modulation signal Generate the PWM control signal of the inverter.
  • the comparing the preset carrier C 0 (t) with the current inverter carrier C(t) to generate a carrier adjustment amount including: using the preset carrier C 0 (t) with a current inverter carrier C(t) compares and generates a carrier difference value; and performs one or more of the following at least one control according to the carrier difference value: proportional control, integral control, and differential control to generate the carrier adjustment amount.
  • an inverter wherein a DC voltage terminal of an inverter circuit of the inverter is connected to an external DC power source, and an AC voltage terminal of the inverter circuit of the inverter is connected to an AC common connection point of the power grid,
  • the inverter includes:
  • a carrier synchronization module configured to obtain a phase ⁇ of an AC voltage of the power grid; and when detecting that the phase ⁇ of the AC voltage meets a threshold phase, determining a time period T ⁇ of the phase of the AC voltage that changes in a preset threshold phase interval,
  • the threshold phase is a starting end phase value of the preset threshold phase interval; calculating a period value T c of the preset carrier according to the preset carrier ratio and the time period T ⁇ ; according to the theoretical carrier period value T c Generating a preset carrier C 0 (t);
  • a modulation module configured to generate a PWM control signal of the inverter according to the PWM modulation signal and the preset carrier generated by the carrier synchronization module;
  • an inverter circuit configured to convert a DC voltage of the external DC power source into an AC voltage of the power grid according to the PWM control signal generated by the modulation module.
  • the carrier synchronization module is specifically configured to phase lock an AC voltage of a power grid, obtain a phase waveform of the grid voltage, and acquire a phase of the AC voltage in the phase waveform.
  • the carrier synchronization module locks the AC voltage of the power grid to obtain a phase waveform of the power grid voltage, and at least includes the following two methods:
  • the carrier synchronization module is specifically configured to phase lock the grid voltage by using a predetermined phase lock algorithm to obtain a phase waveform of the grid voltage, and the predetermined phase lock algorithm includes at least one of the following: a single step coordinate system software phase lock
  • the single-step coordinate system of the ring and symmetrical component method is a software phase-locked loop, the decoupling software phase-locked loop based on the double-synchronous coordinate system, and the software phase-locked loop based on the double second-order generalized integrator.
  • the carrier synchronization module is specifically configured to acquire any phase voltage of an AC voltage of the power grid; and detect a voltage zero-crossing point and a voltage frequency of the any phase voltage, according to the voltage zero-crossing point and the voltage frequency Obtaining a first waveform of the voltage zero-crossing point, and acquiring a positive voltage period on both sides of the voltage zero-crossing point and a second waveform corresponding to the negative voltage period; acquiring the power grid according to the first waveform and the second waveform The phase waveform of the AC voltage.
  • the carrier synchronization module is specifically configured to: when detecting that the phase ⁇ of the AC voltage meets a threshold phase, trigger a count; and obtain a counting period between the current trigger count and the next trigger count.
  • the value N ct (the number of ⁇ t); the time period T ⁇ at which the phase of the alternating voltage changes within a preset threshold phase interval is determined according to the count period value N ct and the single count duration ⁇ t.
  • the carrier synchronization module is specifically configured to generate the preset carrier C 0 (t) according to the theoretical carrier period value T c , a preset carrier initial phase, and a preset carrier amplitude.
  • the modulation module includes: a load control sub-module, configured to replace the preset carrier C 0 (t) with a current inverter carrier C(t);
  • a modulation submodule configured to generate a PWM control signal of the inverter according to the PWM modulation signal and the current inverter carrier C(t) replaced by the load control submodule.
  • the modulation module includes: a load control submodule, configured to compare the preset carrier C 0 (t) with a current inverter carrier C(t) to generate a carrier adjustment amount; The carrier adjustment amount updates the current inverter carrier C(t);
  • a modulation submodule configured to generate a PWM control signal of the inverter according to the PWM modulation signal and the current inverter carrier C(t) updated by the load control submodule.
  • the loading control sub-module is specifically configured to compare the preset carrier C 0 (t) with the current inverter carrier C(t) to generate a carrier difference value; and perform at least one of the following according to the carrier difference value;
  • the third aspect provides a power grid system, including at least two sets of inverters, wherein a DC voltage end of the inverter is connected to an external DC power source, and an AC voltage end of the inverter is connected to an AC common connection point of the AC power grid;
  • the inverter is any of the inverters described in the second aspect.
  • any of the inverters or grid systems provided above are used to perform the PWM control signal synchronization method of the inverter corresponding to the first aspect provided above, and therefore, the beneficial effects can be achieved.
  • FIG. 1 is a schematic structural diagram of a power grid system according to an embodiment of the present invention
  • FIG. 2 is a schematic flowchart diagram of a method for synchronizing a PWM control signal of an inverter according to an embodiment of the present invention
  • FIG. 3 is a schematic diagram of an implementation manner of a phase locked loop according to an embodiment of the present invention.
  • FIG. 4 is a schematic diagram of an output waveform of a phase locked loop according to an embodiment of the present invention.
  • FIG. 5 is a schematic diagram of an implementation manner of a phase locked loop according to another embodiment of the present invention.
  • FIG. 6 is a schematic diagram of a threshold phase according to an embodiment of the present invention.
  • FIG. 7 is a schematic diagram of a threshold phase according to another embodiment of the present invention.
  • FIG. 8 is a schematic diagram of a threshold phase according to still another embodiment of the present invention.
  • FIG. 9 is a schematic diagram of a method for generating a preset carrier C 0 (t) according to an embodiment of the present invention.
  • FIG. 10 is a schematic diagram of a method for generating an inverter carrier C(t) according to an embodiment of the present invention.
  • FIG. 11 is a schematic diagram of a method for generating an inverter carrier C(t) according to another embodiment of the present invention.
  • FIG. 12 is a schematic flowchart diagram of a method for synchronizing a PWM control signal of an inverter according to another embodiment of the present invention.
  • FIG. 13 is a schematic structural diagram of an inverter according to an embodiment of the present invention.
  • FIG. 14 is a schematic structural diagram of an inverter according to another embodiment of the present invention.
  • the embodiment of the present invention is applied to a DC-converted power grid system in the field of power technology, wherein the system may include at least two sets of inverters, wherein the DC voltage terminal of the inverter is connected to an external DC power source, and the inverter is AC. The voltage terminal is connected to the AC common connection point of the grid.
  • the typical external DC power supply may be: a main unit of photovoltaic power generation, a main unit of wind power generation, a main unit of hydroelectric power generation or an energy storage DC storage battery, or a DC power generation or storage device in other scenarios, and the present application is external to the external application.
  • the form of the DC power supply is not limited.
  • an embodiment of the present invention provides a power grid system including an external DC power source, an inverter, and a power grid; wherein the inverter #1 and Inverter #2 can be a separate inverter without a common DC bus, that is, inverter #1 and inverter #2 are each connected to a separate external DC power supply, or inverter #1 and inverter #2 can be two inverters of a common DC bus, that is, inverter #1 and inverter #2 are connected to the same external DC power source (not shown) through the same DC bus.
  • the working principle of the above-mentioned power grid system is that the inverter boosts and inverts the power of the external DC power source and then transmits it to the power grid.
  • the inverter provides a phase-constant PWM control signal to the inverter circuit according to the phase of the AC voltage of the power grid.
  • the phases of the PWM control signals of the two inverters are in an asynchronous state, and may be time-varying and uncertain; and the phase of the PWM control signal generated by the embodiment of the present application can be eliminated. Time-varying effect, reaching a steady state, making two The phase of the PWM control signal of the inverter tends to be uniform.
  • the PWM control signal synchronization method of the inverter specifically includes the following steps:
  • the power grid typically includes transmission lines, isolation transformers, and the like.
  • a combiner box may also be included.
  • inverter #1 and inverter #2 are usually connected to the power grid through a combiner box.
  • the isolation transformer generally belongs to the booster box, and is composed of a primary winding, a secondary winding and a magnetic core.
  • the phase ⁇ of the AC voltage obtained by the step S101 is generally obtained from the primary winding side of the isolation transformer, that is, acquired on the low voltage side.
  • the effective interval length of the phase ⁇ of the alternating voltage is 2 ⁇ , and the actual output phase ⁇ is any one of [- ⁇ , ⁇ ) or [0, 2 ⁇ ).
  • the specific step S101 may be: phase-locking the AC voltage of the power grid, obtaining a phase waveform of the grid voltage, and acquiring a phase of the AC voltage in the phase waveform.
  • the principle is as follows: the frequency and phase of the voltage of the power grid can be obtained through the phase-locked loop, and the phase waveform of the grid voltage is obtained, wherein the phase waveform is usually a triangular wave of 0°-360°.
  • the phase-locked loop can be a software phase-locked loop or a hardware phase-locked loop; according to the number of phases, a three-phase phase-locked loop or a single-phase phase-locked loop can be used; according to the control structure, an open-loop phase-locked loop and a closed-loop phase-locked loop can be used. ring.
  • phase voltage of the grid voltage is obtained by phase-locking the AC voltage of the power grid, and at least includes the following two methods:
  • Method 1 Implementing by using a software phase-locked loop method, specifically, phase locking the grid voltage by using a predetermined phase-locking algorithm to obtain a phase waveform of the grid voltage, and the predetermined phase-locking algorithm includes at least one of the following: single-step coordinate system software Phase-locked loop, symmetrical component method, single-step coordinate system, software phase-locked loop, decoupling software phase-locked loop based on double-synchronous coordinate system, software phase-locked loop based on double second-order generalized integrator.
  • the three-phase grid voltage (V a , V b , V c ) is converted to the voltage (V ⁇ , V ⁇ ) of the two-phase stationary coordinate system by the T 3s/2s module, and the process can be performed by Clarke transform.
  • the calculation formula is:
  • the voltage (V ⁇ , V ⁇ ) of the two-phase stationary coordinate system is converted into the voltage (V d , V q ) of the synchronous rotating coordinate system by the T 2s/2r module.
  • the process can be performed by Park (Pike) transformation, and the calculation formula is as follows :
  • ⁇ is the phase of the phase-locked loop output
  • the above two transformations can transform the sine quantity in the three-phase static abc coordinate system into the DC quantity in the two-phase synchronous rotation dq coordinate system.
  • V q is sent to a PI regulator (Proportional Integral Controller), and the output of the PI regulator is added to the nominal angular frequency ⁇ ff to obtain an actual angular frequency ⁇ 0 .
  • the integral phase is calculated by the 1/s integration module to obtain the original phase ⁇ 1 , and the remainder of the ⁇ 1 is calculated by the modulo remainder module, and the remainder of ⁇ 1 divided by 2 ⁇ is calculated.
  • the remainder is the output phase ⁇ , where the remainder of ⁇ can be defined between 0 and 2 ⁇ to avoid overflow.
  • Method 2 Implemented by a hardware phase-locked loop method, which specifically includes: obtaining any phase voltage of an AC voltage of the power grid; detecting a voltage zero-crossing point and a voltage frequency of any phase voltage, and obtaining a voltage zero-crossing point according to the voltage zero-crossing point and the voltage frequency; a first waveform, and obtaining a positive voltage period on both sides of the voltage zero-crossing point and a second waveform corresponding to the negative voltage period; acquiring a phase waveform of the AC voltage of the power grid according to the first waveform and the second waveform.
  • FIG. 5 a schematic structural diagram of a hardware phase locked loop is provided:
  • the zero-crossing point and the voltage frequency of the A-phase AC voltage are detected in real time through the zero-crossing detection circuit, and the voltage is obtained according to the voltage zero-crossing point and the voltage frequency.
  • the first waveform comprises: a positive zero-crossing positive pulse signal and a negative zero-crossing positive pulse signal; and simultaneously obtaining a positive voltage period on both sides of the voltage zero-crossing point and a second waveform corresponding to the negative voltage period, wherein the second waveform
  • the waveform includes: a positive half cycle square wave signal and a negative half cycle square wave signal; then the first waveform and the second waveform are provided to the subsequent CPU as a synchronous reference signal of the AC voltage of the power grid, and the latter CPU according to the first waveform and the first
  • the second waveform tracks the AC voltage frequency change of the power grid to obtain the phase waveform sin ⁇ / cos ⁇ of the AC voltage of the power grid.
  • the latter CPU can be a digital processing chip or a logic programmable chip.
  • the three threshold phases may be 0, 2 ⁇ /3, 4 ⁇ /3, and the interval between each two threshold phases is 2 ⁇ /3, as shown in FIG. Three equal parts, taking the three equal points as the threshold phase.
  • the five threshold phases may be 0, 2 ⁇ /5, 4 ⁇ /5, 6 ⁇ /5, 8 ⁇ /5, respectively, and the interval between each two threshold phases is 2 ⁇ /5.
  • a circle is equally divided into five, and the five equal points are taken as a threshold phase.
  • Step 102 is specifically as follows:
  • the preset phase threshold interval change time T ⁇ refers to the time taken for the AC voltage phase ⁇ to run from the previous preset threshold phase to the current threshold phase.
  • the specific acquisition mode is: when the AC voltage phase ⁇ is equal to the previous threshold phase
  • the count period value N ct is multiplied by the single count duration ⁇ t; an example of running from the previous threshold phase to the current threshold phase is, for example, from 0 to 2 ⁇ /5, from 2 ⁇ /5 to 4 ⁇ /5, from 4 ⁇ /5 to 6 ⁇ / 5, and so on.
  • phase time length T ⁇ i.e., the phase of the AC voltage in the phase interval changes a predetermined threshold time period T ⁇ .
  • Step S103 is specifically: dividing T ⁇ by the preset carrier ratio N T to obtain a period T c of the preset carrier, wherein the preset carrier ratio N T generally refers to the frequency Fn of the power grid and the switching frequency Fsw of the inverter.
  • N T Fsw/Fn.
  • the frequency Fn of the power grid is constant, the closer the preset carrier ratio N T is, the closer the waveform of the inverter output is to the sine wave, and of course the higher the switching frequency Fsw of the inverter is required.
  • the carrier preset initial phase ⁇ C 0 (t) is 0 and a predetermined carrier wave C 0 (t)
  • the amplitude A generates a preset carrier C 0 (t).
  • preset initial phase ⁇ Carrier C 0 (t) 0 0, the default carrier C 0 (t) is the amplitude A is 1, generating a predetermined carrier wave C 0 (t)
  • the waveform is a triangular wave or a sawtooth wave.
  • Step 105 can be implemented by adopting the following stepwise replacement or direct replacement:
  • step a in the foregoing mode 2 may be implemented by a comparator and a controller
  • step b may be implemented by an adder, specifically: the preset carrier C 0 (t) and the current inverter Carrier C(t) is sent to the comparator to calculate the carrier difference; the carrier difference is sent to the controller, and the carrier difference is subjected to one or more of the following at least one control: proportional control, integral control, differential Control, generate carrier adjustment amount.
  • the carrier adjustment amount is added to the current inverter carrier C(t), and the current inverter carrier C(t) is updated.
  • the above steps S101-S105 can be implemented by embedding a software program in the DSP without changing the current inverter hardware facilities. As shown in FIG. 12, the above steps S101-S105 can be performed in the DSP interrupt resource. .
  • the interrupt is a cyclically executed process at a fixed frequency. Each time an interrupt is required, an internal or external trigger is required. After all interrupt programs have been executed, the interrupt is exited until the next trigger arrives again. After entering the interrupt program, the interrupt program 1 is executed first, then the steps S101-S105 are executed, then the interrupt program 2 is executed, all the interrupt programs are executed, and then the interrupt is entered again with the next interrupt trigger. Execute all interrupt routines.
  • the interrupt program 1 is a program from the start of the interrupt to the start of the steps S101-S105
  • the interrupt program 2 is a program between the end of the steps S101-S105 and the end of the interrupt
  • the portion between the interrupt program 1 and the interrupt program 2 is Steps S101-S105.
  • the embodiment of the present application provides an inverter.
  • the DC voltage end of the inverter circuit of the inverter is connected to an external DC power source, and the AC voltage end of the inverter circuit of the inverter is connected to the AC public connection of the power grid.
  • the inverter 13 includes a carrier synchronization module 1301, a modulation module 1302, and an inverter circuit 1303.
  • the carrier synchronization module 1301 is configured to support the inverter to perform the processes S101-S104 in FIG. 2; the modulation module 1302 is used in the inverter to perform the process S105 in FIG.
  • the inverter circuit 1303 is configured to use the external DC power supply according to the PWM control signal.
  • the DC voltage is converted to the AC voltage of the grid.
  • the modulation module 1302 specifically includes a load control submodule 13021 for replacing the preset carrier C 0 (t) with the current inverter carrier C(t); and a modulation submodule 13022 for The modulation signal and the current inverter carrier C(t) replaced by the load control sub-module 13021 generate a PWM control signal of the inverter.
  • the modulation module 1302 specifically includes a load control sub-module 13021, configured to compare the preset carrier C 0 (t) with a current inverter carrier C(t) to generate a carrier adjustment amount; The current inverter carrier C(t) is updated; the modulation sub-module 13022 is configured to generate PWM control of the inverter according to the PWM modulation signal and the current inverter carrier C(t) updated by the load control sub-module 13021. signal.
  • a load control sub-module 13021 configured to compare the preset carrier C 0 (t) with a current inverter carrier C(t) to generate a carrier adjustment amount; The current inverter carrier C(t) is updated; the modulation sub-module 13022 is configured to generate PWM control of the inverter according to the PWM modulation signal and the current inverter carrier C(t) updated by the load control sub-module 13021. signal.
  • the load control sub-module 13021 is configured to compare the preset carrier C 0 (t) with the current inverter carrier C(t) to generate a carrier difference value; and perform at least one of the following control according to the carrier difference value; One or more controls: proportional control, integral control, differential control, generating the carrier adjustment amount. All the related content of the steps involved in the foregoing method embodiments may be referred to the functional descriptions of the corresponding functional modules, and details are not described herein again.
  • the disclosed systems, devices, and methods may be implemented in other manners.
  • the device embodiments described above are merely illustrative.
  • the division of the unit is only a logical function division.
  • there may be another division manner for example, multiple units or components may be combined or Can be integrated into another system, or some features can be ignored or not executed.
  • the mutual coupling or direct coupling or communication connection shown or discussed may be an indirect coupling or communication connection through some interface, device or unit, and may be electrical, mechanical or otherwise.

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Abstract

一种逆变器的PWM控制信号同步方法及逆变器和电网系统，能够实现接入电网的逆变器的PWM控制信号同步。逆变器的直流电压端连接外部电源，逆变器的交流电压端连接电网的交流公共连接点，该方法包括：获取电网的交流电压的相位θ（S101）；当检测到交流电压的相位满足阈值相位时，确定交流电压的相位在预设阈值相位区间变化的时间周期（S102），其中阈值相位为预设阈值相位区间的起始端相位值；按照预设载波比和时间周期计算预设载波的周期值（S103）；根据预设载波的周期值生成预设载波（S104）；根据PWM调制信号与预设载波生成逆变器的PWM控制信号（S105）。

Description

一种逆变器的PWM控制信号同步方法及逆变器和电网系统 技术领域
本申请涉及电力技术领域，尤其涉及一种逆变器的PWM控制信号同步方法及逆变器和电网系统。
背景技术
逆变器是一种将直流电转换为交流电的电力变换装置，广泛应用于现代电力工业。在一些工业场合如光伏电场，随着装机容量的增大，越来越多的采用多台逆变器并联。多台光伏逆变器并联运行时，由于每台逆变器内DSP(digital signal processor，数字信号处理器)晶振的差异，导致PWM(pulse width modulation，脉宽调制)载波相位不同步，使得逆变器的PWM控制信号不同步，最终引发的后果是，逆变器之间将产生高频纹波环流。高频的环流叠加在逆变器输出基波电流上，带来严重畸变。电流畸变不但增加逆变器损耗，降低系统效率，而且会威胁到逆变器内部器件安全。
发明内容
本申请的实施例提供一种逆变器的PWM控制信号同步方法及逆变器和电网系统，能够实现接入电网的逆变器的PWM控制信号同步。
为达到上述目的，本申请的实施例采用如下技术方案：
第一方面，提供一种逆变器的PWM控制信号同步方法，逆变器的逆变电路的直流电压端连接外部电源，逆变器的逆变电路的交流电压端连接电网的交流公共连接点，该方法包括：获取电网的交流电压的相位θ；当检测到交流电压的相位θ满足阈值相位时，确定交流电压的相位在预设阈值相位区间变化的时间周期Tθ，其中所述阈值相位为所述预设阈值相位区间的起始端相位值；按照预设载波比NT和时间周期Tθ计算预设载波的周期值Tc；根据预设载波的周期值Tc生成预设载波C0(t)；根据PWM调制信号与预设载波C0(t)生成逆变器的PWM控制信号，以便于逆变器的逆变电路根据PWM控制信号将外部直流电源的直流电压转换为电网的交流电压。在上述方案中，由于接入电网的每个逆变器的PWM控制信号的生成过程均参考了电网的相位θ，因此能够避免因每台逆变器内DSP晶振的差异，导致逆变器的PWM控制信号不同步，保证了每台逆变器的PWM控制信号同步。
一种示例性的实施方式是：获取电网的交流电压的相位θ，包括：对电网的交流电压锁相，得到所述电网电压的相位波形，并在所述相位波形中获取所述交流电压的相位。其中，对电网的交流电压锁相获取所述电网电压的相位波形，至少包括如下两种方式：
方式一：采用预定锁相算法对电网电压锁相，得到所述电网电压的相位波形，所述预定锁相算法至少包括以下任一：单步坐标系软件锁相环、对称分量法的单步坐标系软件锁相环、基于双同步坐标系的解耦软件锁相环、基于双二阶广义积 分器的软件锁相环。
方式二：获取所述电网的交流电压的任一相电压；检测所述任一相电压的电压过零点及电压频率，根据所述电压过零点及所述电压频率获取所述电压过零点的第一波形、并获取所述电压过零点两侧的正电压周期以及负电压周期对应的第二波形；根据所述第一波形和所述第二波形获取所述电网的交流电压的相位波形。
一种示例性的实施方式是：当检测到所述交流电压的相位θ满足阈值相位时，确定交流电压的相位在预设阈值相位区间变化的时间周期Tθ，包括：当检测到所述交流电压的相位θ满足阈值相位时，触发计数；获取本次触发计数和下一次触发计数之间的计数周期值；根据所述计数周期值和单次计数时长Δt确定所述交流电压的相位在预设阈值相位区间变化的时间周期Tθ。
一种示例性的实施方式是，根据所述预设载波的周期值Tc生成预设载波C0(t)，包括：根据所述理论载波周期值Tc、预设载波初始相位以及预设载波幅值生成所述预设载波C0(t)。
一种示例性的实施方式是，所述根据PWM调制信号与所述预设载波C0(t)生成逆变器的PWM控制信号，包括：将所述预设载波C0(t)替换当前逆变器载波C(t)；根据PWM调制信号以及替换后的所述当前逆变器载波C(t)生成逆变器的PWM控制信号。
一种示例性的实施方式是，所述根据PWM调制信号与所述预设载波C0(t)生成逆变器的PWM控制信号，包括：将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波调节量；根据所述载波调节量更新所述当前逆变器载波C(t)；根据PWM调制信号与更新后的当前逆变器载波C(t)生成逆变器的PWM控制信号。其中，所述将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波调节量，包括：将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波差值；根据所述载波差值进行如下至少一种控制中的一种或多种控制：比例控制、积分控制、微分控制，生成所述载波调节量。
第二方面，提供一种逆变器，逆变器的逆变电路的直流电压端连接外部直流电源，所述逆变器的逆变电路的交流电压端连接电网的交流公共连接点，所述逆变器包括：
载波同步模块，用于获取电网的交流电压的相位θ；当检测到所述交流电压的相位θ满足阈值相位时，确定所述交流电压的相位在预设阈值相位区间变化的时间周期Tθ，其中所述阈值相位为所述预设阈值相位区间的起始端相位值；按照预设载波比和所述时间周期Tθ计算预设载波的周期值Tc；根据所述理论载波周期值Tc生成预设载波C0(t)；
调制模块，用于根据PWM调制信号与所述载波同步模块生成的预设载波生成逆变器的PWM控制信号；
逆变电路，用于根据所述调制模块生成的PWM控制信号将外部直流电源的直流电压转换为电网的交流电压。
在上述方案中，由于接入电网的每个逆变器的PWM控制信号的生成过程均参考了电网的相位θ，因此能够避免因每台逆变器内DSP晶振的差异，导致逆变 器的PWM控制信号不同步，保证了每台逆变器的PWM控制信号同步。
一种示例性的实施方式是，所述载波同步模块具体用于对电网的交流电压锁相，得到所述电网电压的相位波形，并在所述相位波形中获取所述交流电压的相位。其中，所述载波同步模块对电网的交流电压锁相，得到所述电网电压的相位波形，至少包括如下两种方式：
方式一：所述载波同步模块具体用于采用预定锁相算法对电网电压锁相，得到所述电网电压的相位波形，所述预定锁相算法至少包括以下任一：单步坐标系软件锁相环、对称分量法的单步坐标系软件锁相环、基于双同步坐标系的解耦软件锁相环、基于双二阶广义积分器的软件锁相环。
方式二：所述载波同步模块具体用于获取所述电网的交流电压的任一相电压；检测所述任一相电压的电压过零点及电压频率，根据所述电压过零点及所述电压频率获取所述电压过零点的第一波形、并获取所述电压过零点两侧的正电压周期以及负电压周期对应的第二波形；根据所述第一波形和所述第二波形获取所述电网的交流电压的相位波形。
一种示例性的实施方式是，所述载波同步模块具体用于当检测到所述交流电压的相位θ满足阈值相位时，触发计数；获取本次触发计数和下一次触发计数之间的计数周期值Nct(Δt的个数)；根据计数周期值Nct和单次计数时长Δt确定所述交流电压的相位在预设阈值相位区间变化的时间周期Tθ。
一种示例性的实施方式是，所述载波同步模块具体用于根据所述理论载波周期值Tc、预设载波初始相位以及预设载波幅值生成所述预设载波C0(t)。
一种示例性的实施方式是，所述调制模块包括：加载控制子模块，用于将所述预设载波C0(t)替换当前逆变器载波C(t)；
调制子模块，用于根据PWM调制信号以及所述加载控制子模块替换后的所述当前逆变器载波C(t)生成逆变器的PWM控制信号。
一种示例性的实施方式是，所述调制模块包括：加载控制子模块，用于将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波调节量；根据所述载波调节量更新所述当前逆变器载波C(t)；
调制子模块，用于根据PWM调制信号与所述加载控制子模块更新后的当前逆变器载波C(t)生成逆变器的PWM控制信号。其中，所述加载控制子模块，具体用于将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波差值；根据所述载波差值进行如下至少一种控制中的一种或多种控制：比例控制、积分控制、微分控制，生成所述载波调节量。
第三方面，提供一种电网系统，包括至少两组逆变器，其中逆变器的直流电压端连接外部直流电源，所述逆变器的交流电压端连接交流电网的交流公共连接点；所述逆变器为第二方面所述的任一逆变器。
可以理解地，上述提供的任一种逆变器或电网系统均用于执行上文所提供的第一方面对应的逆变器的PWM控制信号同步方法，因此，其所能达到的有益效果可参考上文第一方面的逆变器的PWM控制信号同步方法以及下文具体实施方式中对应的方案的有益效果，此处不再赘述。
附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍。
图1为本发明的实施例提供一种电网系统的结构示意图；
图2为本发明的实施例提供一种逆变器的PWM控制信号同步方法的流程示意图；
图3为本发明的实施例提供一种锁相环的实现方式示意图；
图4为本发明的实施例提供一种锁相环的输出波形的示意图；
图5为本发明的另一实施例提供一种锁相环的实现方式示意图；
图6为本发明的实施例提供一种阈值相位的示意图；
图7为本发明的另一实施例提供一种阈值相位的示意图；
图8为本发明的又一实施例提供一种阈值相位的示意图；
图9为本发明的实施例提供一种预设载波C0(t)的生成方法示意图；
图10为本发明的实施例提供一种逆变器载波C(t)的生成方法示意图；
图11为本发明的另一实施例提供一种逆变器载波C(t)的生成方法示意图；
图12为本发明的另一实施例提供一种逆变器的PWM控制信号同步方法的流程示意图；
图13为本发明的实施例提供一种逆变器的结构示意图；
图14为本发明的另一实施例提供一种逆变器的结构示意图。
具体实施方式
下面结合附图，对本申请的实施例进行描述。
首先对本发明的实施例应用场景进行描述如下：
本发明的实施例应用于电力技术领域中直流交流转换的电网系统中，其中该系统可以是包括至少两组逆变器，其中逆变器的直流电压端连接外部直流电源，逆变器的交流电压端连接电网的交流公共连接点。其中，典型的外部直流电源可以为：光伏发电的主体装置、风力发电的主体装置、水利发电的主体装置或者储能直流蓄电池等，或者其他场景的直流发电或蓄电装置，本申请对该外部直流电源的形式不作限定。
示例性的以两台逆变器并联的场景为例，参照图1所示，本发明的实施例提供一种电网系统：包括外部直流电源、逆变器和电网；其中逆变器#1与逆变器#2可以为不共直流母线的独立逆变器，即，逆变器#1与逆变器#2各自分别连接一个独立的外部直流电源，或者逆变器#1与逆变器#2可以为共直流母线的两台逆变器，即，逆变器#1与逆变器#2通过同一直流母线连接至同一个外部直流电源(图中未示出)。
其中，上述的电网系统的工作原理为：逆变器把外部直流电源的电能进行升压、逆变后输送到电网上。逆变器根据电网的交流电压的相位为逆变电路提供相对交流电网的相位恒定的PWM控制信号。现有技术中，两台逆变器的PWM控制信号的相位处于非同步的状态，而且可能是时变的，不确定的；而通过本申请的实施例生成的PWM控制信号的相位则能够消除时变影响，达到稳定状态，使得两 台逆变器的PWM控制信号的相位趋于一致。
基于上述的电网系统，逆变器的PWM控制信号同步方法，参照图2所示，具体包括如下步骤：
S101、获取电网的交流电压的相位θ。
如图1所示，电网通常包括传输线、隔离变压器等。在一些应用场景中，可能还包括汇流箱，如图1所示，逆变器#1和逆变器#2通常通过汇流箱接入电网。其中隔离变压器一般属于升压箱变，由原边绕组、副边绕组和磁芯组成。步骤S101获取电网的交流电压的相位θ一般是从位于隔离变压器的原边绕组侧获取，即在低压侧获取。交流电压的相位θ的有效区间长度为2π，实际输出的相位θ为[-π,π)或[0,2π)中的任一值。
具体的步骤S101可以为：对电网的交流电压锁相，得到电网电压的相位波形，并在相位波形中获取所述交流电压的相位。其原理为：可以通过锁相环跟踪获取电网的电压的频率和相位，获取电网电压的相位波形，其中相位波形通常为0°～360°的三角波。锁相环可以采用软件锁相环或硬件锁相环；按相数划分，可采用三相锁相环或单相锁相环；按控制结构划分，可采用开环锁相环和闭环锁相环。
其中，对电网的交流电压锁相，得到所述电网电压的相位波形，至少包括如下两种方式：
方式一：采用软件锁相环方式实现，具体为采用预定锁相算法对电网电压锁相，得到所述电网电压的相位波形，所述预定锁相算法至少包括以下任一：单步坐标系软件锁相环、对称分量法的单步坐标系软件锁相环、基于双同步坐标系的解耦软件锁相环、基于双二阶广义积分器的软件锁相环。
参照图3所示，提供一种三相软件锁相环实现方式：
首先，通过T3s/2s模块将三相电网电压(Va、Vb、Vc)转换为两相静止坐标系的电压(Vα、Vβ)，该过程可以采用Clarke(克拉克)变换，计算公式为：
Figure PCTCN2017104067-appb-000001
通过T2s/2r模块将两相静止坐标系的电压(Vα、Vβ)转换为同步旋转坐标系的电压(Vd、Vq)，该过程可以采用Park(派克)变换，计算公式如下：
Figure PCTCN2017104067-appb-000002
其中，θ为锁相环输出的相位，以上两次变换能将三相静止abc坐标系中的正弦量变换成两相同步旋转dq坐标系中的直流量。
将计算得到的Vq送入PI调节器(Proportional Integral Controller)，将PI调节器的输出与额定角频率ωff相加，得到实际角频率ω0。根据PI调节器的工作原理，只有当Vq＝0时，PI调节器的输出才会保持恒定，此时整个锁相环就停止调节，输出相位与三相电压相位保持一致。
在得到实际角频率ω0之后，通过1/s积分模块对其进行积分计算，获得原始相 位θ1，通过Mod取余模块对θ1进行取余计算，计算得到θ1除以2π的余数，该余数即为输出相位θ，其中通过取余可以限定θ的范围在0和2π之间而避免溢出。最终，输出的相位波形示意图如图4所示。
方式二：采用硬件锁相环方式实现，具体包括：获取电网的交流电压的任一相电压；检测任一相电压的电压过零点及电压频率，根据电压过零点及电压频率获取电压过零点的第一波形、并获取电压过零点两侧的正电压周期以及负电压周期对应的第二波形；根据第一波形和所述第二波形获取电网的交流电压的相位波形。
如图5所示，提供一种硬件锁相环的结构示意图：
以电网的A相交流电压为例，当A相交流电压经电压互感器处理后，通过过零检测电路实时检测A相交流电压的过零点以及电压频率，根据电压过零点及电压频率获取电压过零点的第一波形，其中第一波形包括：正过零点正脉冲信号和负过零点正脉冲信号；同时获取电压过零点两侧的正电压周期以及负电压周期对应的第二波形，其中第二波形包括：正半周期正方波信号和负半周期正方波信号；之后将第一波形和第二波形提供给后级CPU作为电网的交流电压的同步基准信号，后级CPU根据第一波形和第二波形跟踪电网的交流电压频率变化获取电网的交流电压的相位波形sinθ/cosθ。后级CPU可以为数字处理芯片，也可以为逻辑可编程芯片。
S102、当检测到交流电压的相位θ满足阈值相位时，确定交流电压的相位在预设阈值相位区间变化的时间周期Tθ。
其中，阈值相位θ为预设阈值相位区间的起始端相位值；例如：在长度为2π的交流相位有效区间内选择N个恒定相位，这N个恒定相位作为预设的阈值相位，N是大于等于1的自然数，这N个阈值相位将长度为2π的交流相位有效区间等分，相邻两个预设阈值相位区间的相位间隔为△θ＝2π/N。
例如，若设置3个阈值相位，则这3个阈值相位可以分别是0,2π/3,4π/3，每两个阈值相位之间间隔为2π/3，如图6所示，将一个圆三等分，取其三等分点为阈值相位。
又例如：若设置5个阈值相位，则这5个阈值相位可以分别是0、2π/5、4π/5、6π/5、8π/5，每两个阈值相位之间间隔为2π/5，具体可参考图7所示，将一个圆五等分，取其五等分点为阈值相位。
步骤102具体为：
S1：当检测到交流电压的相位θ满足阈值相位时，触发计数；
S2、获取本次触发计数和下一次触发计数之间的计数周期值Nct(Δt的个数)；
S3、根据计数周期值Nct和单次计数时长Δt确定交流电压的相位在预设阈值相位区间变化的时间周期Tθ。
举例说明，预设相位阈值区间变化用时Tθ，是指交流电压相位θ从前一个预设阈值相位运行到当前阈值相位所用的时间，具体获取方式为：当交流电压相位θ等于前一个阈值相位时触发计数器从1(计数周期值Nct＝1)开始计数，在交流电压相位θ等于当前阈值相位时读取计数器的计数周期值Nct，同时将计数器置1并重新开始计 数；Tθ等于当前计数周期值Nct乘以单次计数时长Δt；从前一个阈值相位运行到当前阈值相位的示例为：例如从0到2π/5，从2π/5到4π/5，从4π/5到6π/5，以此类推。举例说明如下：参照图8、9所示，在长度为2π的交流电压的相位有效区间内选择2个恒定相位作为阈值相位，分别是0和π，则两个预设阈值相位区间为：[0，π]，[π，2π]，于是，当步骤S101输出的交流电压的相位θ等于0和π时，触发计数；当θ等于0或π时，读取计数器计数值Nct并将计数器置1重新开始计数；根据Tθ＝Δt·Nct，得到计数器从上一次置1到本次置1之间的时间长度，即对应为交流电压的相位θ从上一个阈值相位变化到当前阈值相位的时间长度Tθ，即交流电压的相位在预设阈值相位区间变化的时间周期Tθ。
S103、按照预设载波比NT和时间周期Tθ计算预设载波的周期值Tc。
步骤S103，具体为：用Tθ除以预设载波比NT，得到预设载波的周期Tc，其中，该预设载波比NT通常参考电网的频率Fn和逆变器的开关频率Fsw设定，NT＝Fsw/Fn。当电网的频率Fn一定时，预设载波比NT越大时，逆变器输出的波形越接近正弦波，当然也要求逆变器的开关频率Fsw越高。通常，中国的电网的频率Fn＝50HZ，选用逆变器的开关频率Fsw＝10KHZ或以上时，设定NT≥200。
S104、根据预设载波的周期值Tc生成预设载波C0(t)。
参照图9所示，在得到预设载波的周期值Tc后，根据预设载波的周期值Tc、预设载波C0(t)的初始相位θ0以及预设载波C0(t)的幅值A生成预设载波C0(t)。示例性的，如图9所示，预设载波C0(t)的初始相位θ0＝0，预设载波C0(t)的幅值A为1，生成预设载波C0(t)，波形为三角波或者锯齿波。
S105、根据PWM调制信号与预设载波C0(t)生成逆变器的PWM控制信号，以便于逆变器的逆变电路根据PWM控制信号将外部直流电源的直流电压转换为电网的交流电压。
其中步骤105可以采用如下逐步替换或者直接替换的方式实现：
方式一：在采用直接替换时，包括如下步骤：
a、将预设载波C0(t)替换当前逆变器载波C(t)；
b、根据PWM调制信号以及替换后的当前逆变器载波C(t)生成逆变器的PWM控制信号。
如图10所示，在获得预设载波C0(t)后，当交流电压的相位θ等于预设的阈值相位π时，将同步载波C0(t)替换当前逆变器载波C(t)，在此之前，保持原有逆变器载波C(t)不变。
方式二：在采用逐步替换时，包括如下步骤：
a、将预设载波C0(t)与当前逆变器载波C(t)比较生成载波调节量。
b、根据载波调节量更新当前逆变器载波C(t)。
c、根据PWM调制信号与更新后的当前逆变器载波C(t)生成逆变器的PWM控制信号。
其中，如图11所示，上述方式二中的步骤a可以通过比较器和控制器实现，上述步骤b可以通过加法器实现，具体的：将预设载波C0(t)和当前逆变器载波C(t)送入比较器，计算载波差值；将载波差值送入控制器，对载波差值进行如下至少一种 控制中的一种或多种控制：比例控制、积分控制、微分控制，生成载波调节量。将载波调节量与当前逆变器载波C(t)相加，更新当前逆变器载波C(t)。
上述步骤S101-S105、可以在不改变当前逆变器硬件设施的基础上，在DSP中嵌入一段软件程序即可实现,具体如图12所示，上述步骤S101-S105可以在DSP中断资源中进行。中断是以固定频率不断循环执行的过程，每次进中断需要内部或外部触发，执行完所有的中断程序后，退出中断，直到下一次触发到来再次进中断。进入中断程序后，首先被执行的是中断程序1部分，其次执行步骤S101-S105，之后执行中断程序2，所有的中断程序被执行完毕，然后随着下一次中断触发的到来再次进入中断，从头执行所有中断程序。中断程序1为从开始进中断到步骤S101-S105开始之间的一段程序，中断程序2为步骤S101-S105结束到中断结束之间的一段程序，中断程序1和中断程序2之间的部分为步骤S101-S105。
上述方案中，由于接入电网的每个逆变器的PWM控制信号的生成过程均参考了电网的的相位θ，因此能够避免因每台逆变器内DSP晶振的差异，导致逆变器的PWM控制信号不同步，保证了每台逆变器的PWM控制信号同步。
本申请实施例提供一种逆变器，参照图1所示，逆变器的逆变电路的直流电压端连接外部直流电源，逆变器的逆变电路的交流电压端连接电网的交流公共连接点，用于执行上述逆变器的PWM控制信号同步方法，参照图1以及13所示，逆变器13包括：载波同步模块1301、调制模块1302和逆变电路1303。载波同步模块1301用于支持逆变器执行图2中的过程S101-S104；调制模块1302用于逆变器执行图2中的过程S105；逆变电路1303用于根据PWM控制信号将外部直流电源的直流电压转换为电网的交流电压。此外，如图14所示，调制模块1302具体包括加载控制子模块13021，用于将预设载波C0(t)替换当前逆变器载波C(t)；调制子模块13022，用于根据PWM调制信号以及加载控制子模块13021替换后的所述当前逆变器载波C(t)生成逆变器的PWM控制信号。或者，调制模块1302具体包括加载控制子模块13021，用于，用于将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波调节量；根据所述载波调节量更新所述当前逆变器载波C(t)；调制子模块13022，用于根据PWM调制信号与加载控制子模块13021更新后的当前逆变器载波C(t)生成逆变器的PWM控制信号。加载控制子模块13021，具体用于将所述预设载波C0(t)与当前逆变器载波C(t)比较生成载波差值；根据所述载波差值进行如下至少一种控制中的一种或多种控制：比例控制、积分控制、微分控制，生成所述载波调节量。其中，上述方法实施例涉及的各步骤的所有相关内容均可以援引到对应功能模块的功能描述，在此不再赘述。
在本申请所提供的几个实施例中，应该理解到，所揭露的系统、设备和方法，可以通过其它的方式实现。例如，以上所描述的设备实施例仅仅是示意性的，例如，所述单元的划分，仅仅为一种逻辑功能划分，实际实现时可以有另外的划分方式，例如多个单元或组件可以结合或者可以集成到另一个系统，或一些特征可以忽略，或不执行。另一点，所显示或讨论的相互之间的耦合或直接耦合或通信连接可以是通过一些接口，设备或单元的间接耦合或通信连接，可以是电性，机械或其它的形式。
以上所述，仅为本申请的具体实施方式，但本申请的保护范围并不局限于此，任何熟悉本技术领域的技术人员在本申请揭露的技术范围内，可轻易想到变化或替换，都应涵盖在本申请的保护范围之内。因此，本申请的保护范围应以所述权利要求的保护范围为准。

Claims (19)

  1. 一种逆变器的PWM控制信号同步方法，其特征在于，所述逆变器的逆变电路的直流电压端连接外部直流电源，所述逆变器的逆变电路的交流电压端连接电网的交流公共连接点，所述方法包括：
    获取电网的交流电压的相位；
    当检测到所述交流电压的相位满足阈值相位时，确定所述交流电压的相位在预设阈值相位区间变化的时间周期，其中所述阈值相位为所述预设阈值相位区间的起始端相位值；
    按照预设载波比和所述时间周期计算预设载波的周期值；
    根据所述预设载波的周期值生成所述预设载波；
    根据PWM调制信号与所述预设载波生成逆变器的PWM控制信号，以便于所述逆变器的逆变电路根据所述PWM控制信号将外部直流电源的直流电压转换为为电网的交流电压。
  2. 根据权利要求1所述的方法，其特征在于，所述获取电网的交流电压的相位，包括：对电网的交流电压锁相，得到所述电网电压的相位波形，并在所述相位波形中获取所述交流电压的相位。
  3. 根据权利要求2所述的方法，其特征在于，所述获取电网的交流电压的相位，包括：对电网的交流电压锁相，得到所述电网电压的相位波形，包括：采用预定锁相算法对电网电压锁相，得到所述电网电压的相位波形，所述预定锁相算法至少包括以下任一：单步坐标系软件锁相环、对称分量法的单步坐标系软件锁相环、基于双同步坐标系的解耦软件锁相环、基于双二阶广义积分器的软件锁相环。
  4. 根据权利要求2所述的方法，其特征在于，所述获取电网的交流电压的相位，包括：对电网的交流电压锁相，得到所述电网电压的相位波形，包括：
    获取所述电网的交流电压的任一相电压；
    检测所述任一相电压的电压过零点及电压频率，根据所述电压过零点及所述电压频率获取所述电压过零点的第一波形、并获取所述电压过零点两侧的正电压周期以及负电压周期对应的第二波形；
    根据所述第一波形和所述第二波形获取所述电网的交流电压的相位波形。
  5. 根据权利要求1所述的方法，其特征在于，所述当检测到所述交流电压的相位满足阈值相位时，确定所述交流电压的相位在预设阈值相位区间变化的时间周期，包括：
    当检测到所述交流电压的相位满足阈值相位时，触发计数；
    获取本次触发计数和下一次触发计数之间的计数周期值；
    根据所述计数周期值和单次计数时长确定所述交流电压的相位在预设阈值相位区间变化的时间周期。
  6. 根据权利要求1所述的方法，其特征在于，所述根据所述预设载波的周期值生成预设载波，包括：
    根据所述预设载波的周期值、预设载波的初始相位以及预设载波的幅值生成 所述预设载波。
  7. 根据权利要求1所述的方法，其特征在于，所述根据PWM调制信号与所述预设载波生成逆变器的PWM控制信号，包括：
    将所述预设载波替换当前逆变器载波；
    根据PWM调制信号以及替换后的所述当前逆变器载波生成逆变器的PWM控制信号。
  8. 根据权利要求1所述的方法，其特征在于，所述根据PWM调制信号与所述预设载波生成逆变器的PWM控制信号，包括：
    将所述预设载波与当前逆变器载波比较生成载波调节量；
    根据所述载波调节量更新所述当前逆变器载波；
    根据PWM调制信号与更新后的当前逆变器载波生成逆变器的PWM控制信号。
  9. 根据权利要求8所述的方法，其特征在于，所述将所述预设载波与当前逆变器载波比较生成载波调节量，包括：
    将所述预设载波与当前逆变器载波比较生成载波差值；
    根据所述载波差值进行如下至少一种控制中的一种或多种控制：比例控制、积分控制、微分控制，生成所述载波调节量。
  10. 一种逆变器，其特征在于，所述逆变器的逆变电路的直流电压端连接外部直流电源，所述逆变器的逆变电路的交流电压端连接电网的交流公共连接点，所述逆变器包括：
    载波同步模块，用于获取电网的交流电压的相位；当检测到所述交流电压的相位满足阈值相位时，确定所述交流电压的相位在预设阈值相位区间变化的时间周期，其中所述阈值相位为所述预设阈值相位区间的起始端相位值；按照预设载波比和所述时间周期计算预设载波的周期值；根据所述预设载波的周期值生成预设载波；
    调制模块，用于根据PWM调制信号与所述载波同步模块生成的预设载波生成逆变器的PWM控制信号；
    逆变电路，用于根据所述调制模块生成的PWM控制信号将外部直流电源的直流电压转换为电网的交流电压。
  11. 根据权利要求10所述的逆变器，其特征在于，所述载波同步模块具体用于对电网的交流电压锁相，得到所述电网电压的相位波形，并在所述相位波形中获取所述交流电压的相位。
  12. 根据权利要求11所述的逆变器，其特征在于，所述载波同步模块具体用于采用预定锁相算法对电网电压锁相，得到所述电网电压的相位波形，所述预定锁相算法至少包括以下任一：单步坐标系软件锁相环、对称分量法的单步坐标系软件锁相环、基于双同步坐标系的解耦软件锁相环、基于双二阶广义积分器的软件锁相环。
  13. 根据权利要求11所述的逆变器，其特征在于，所述载波同步模块具体用于获取所述电网的交流电压的任一相电压；检测所述任一相电压的电压过零点及 电压频率，根据所述电压过零点及所述电压频率获取所述电压过零点的第一波形、并获取所述电压过零点两侧的正电压周期以及负电压周期对应的第二波形；根据所述第一波形和所述第二波形获取所述电网的交流电压的相位波形。
  14. 根据权利要求10所述的逆变器，其特征在于，所述载波同步模块具体用于当检测到所述交流电压的相位满足阈值相位时，触发计数；获取本次触发计数和下一次触发计数之间的计数周期值；根据所述计数周期值和单次计数时长确定所述交流电压的相位在预设阈值相位区间变化的时间周期。
  15. 根据权利要求10所述的逆变器，其特征在于，所述载波同步模块具体用于根据所述预设载波的周期值、预设载波初始相位以及预设载波幅值生成所述预设载波。
  16. 根据权利要求10所述的逆变器，其特征在于，所述调制模块，包括：加载控制子模块用于将所述预设载波替换当前逆变器载波；
    调制子模块，用于根据PWM调制信号以及所述加载控制子模块获取的替换后的所述当前逆变器载波生成逆变器的PWM控制信号。
  17. 根据权利要求10所述的逆变器，其特征在于，所述调制模块，包括：加载控制子模块用于将所述预设载波与当前逆变器载波比较生成载波调节量；根据所述载波调节量更新所述当前逆变器载波；
    调制子模块，用于根据PWM调制信号与所述加载控制子模块更新后的当前逆变器载波生成逆变器的PWM控制信号。
  18. 根据权利要求17所述的逆变器，其特征在于，所述加载控制子模块，具体用于将所述预设载波与当前逆变器载波比较生成载波差值；根据所述载波差值进行如下至少一种控制中的一种或多种控制：比例控制、积分控制、微分控制，生成所述载波调节量。
  19. 一种电网系统，其特征在于，至少两组逆变器，其中所述逆变器的直流电压端连接外部直流电源，所述逆变器的交流电压端连接交流电网的交流公共连接点；
    所述逆变器为如权利要求10-18任意一项所述的逆变器。
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