WO2019206230A1 - Dcdc变换器、车载充电机和电动车辆 - Google Patents

Dcdc变换器、车载充电机和电动车辆 Download PDF

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Publication number
WO2019206230A1
WO2019206230A1 PCT/CN2019/084328 CN2019084328W WO2019206230A1 WO 2019206230 A1 WO2019206230 A1 WO 2019206230A1 CN 2019084328 W CN2019084328 W CN 2019084328W WO 2019206230 A1 WO2019206230 A1 WO 2019206230A1
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Prior art keywords
switch tube
unit
phase
capacitor
phase bridge
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PCT/CN2019/084328
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English (en)
French (fr)
Inventor
张晓彬
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BYD Co Ltd
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BYD Co Ltd
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Priority to US17/050,166 priority Critical patent/US11870357B2/en
Priority to JP2020559441A priority patent/JP2021522770A/ja
Priority to EP19792994.6A priority patent/EP3787170A4/en
Publication of WO2019206230A1 publication Critical patent/WO2019206230A1/zh
Anticipated expiration legal-status Critical
Priority to US18/375,432 priority patent/US12224674B2/en
Priority to US18/375,422 priority patent/US12334834B2/en
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R15/00—Details of measuring arrangements of the types provided for in groups G01R17/00 - G01R29/00, G01R33/00 - G01R33/26 or G01R35/00
    • G01R15/14—Adaptations providing voltage or current isolation, e.g. for high-voltage or high-current networks
    • G01R15/18—Adaptations providing voltage or current isolation, e.g. for high-voltage or high-current networks using inductive devices, e.g. transformers
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/25—Arrangements for measuring currents or voltages or for indicating presence or sign thereof using digital measurement techniques
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries
    • H02J7/90—Regulation of charging or discharging current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/165—Indicating that current or voltage is either above or below a predetermined value or within or outside a predetermined range of values
    • G01R19/16533—Indicating that current or voltage is either above or below a predetermined value or within or outside a predetermined range of values characterised by the application
    • G01R19/16538—Indicating that current or voltage is either above or below a predetermined value or within or outside a predetermined range of values characterised by the application in AC or DC supplies
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Details of circuit arrangements for charging or discharging batteries or supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the present disclosure relates to the field of vehicle technology, and in particular, to a DCDC converter, and an in-vehicle charger including the DCDC converter and an electric vehicle on which the in-vehicle charger is mounted.
  • a car charger In order to save charging and discharging time, a large-capacity battery module requires a more powerful two-way car charger (hereinafter referred to as a car charger).
  • the mainstream car charger power level in the industry is single-phase 3.3KW/6.6KW.
  • three-phase 10/20/40KW car chargers have an increasingly large market.
  • the main power topology of the vehicle charger generally includes PFC (Power Factor Correction) + bidirectional DCDC, PFC plays the role of power factor correction; bidirectional DCDC realizes energy controllable isolation transmission, which is the core power conversion unit of the vehicle charger.
  • PFC Power Factor Correction
  • bidirectional DCDC realizes energy controllable isolation transmission, which is the core power conversion unit of the vehicle charger.
  • high-power bidirectional DCDC converters usually use multiple modules in parallel, but there are some problems in paralleling multiple modules, which makes high requirements for system hardware circuit design and software algorithms.
  • the present disclosure aims to solve at least one of the technical problems in the related art to some extent.
  • an embodiment of the present disclosure is to provide a DCDC converter that is more suitable for a high-power vehicle charger, which is low in cost and simple in structure.
  • Yet another embodiment of the present disclosure is directed to an in-vehicle charger including the DCDC converter.
  • Yet another embodiment of the present disclosure is to provide an electric vehicle in which the in-vehicle charger is mounted.
  • a DCDC converter includes: a first adjustment module, a resonance module, a second adjustment module, a current detection module, and a controller, wherein the first adjustment module is configured to: Adjusting the frequency of the input signal of the DCDC converter when the battery module of the vehicle is externally charged, or for rectifying the output signal of the resonant module when the battery module discharges the outside; the resonant module, And configured to resonate an output signal of the first adjustment module when the battery module of the vehicle is externally charged, or to resonate an output signal of the second adjustment module when the battery module discharges to the outside
  • the second adjustment module is configured to adjust a frequency of an output signal of the battery module when the battery module of the vehicle discharges to the outside, or to the resonance module when the battery module is externally charged
  • the output signal is rectified; a current detecting module, wherein the current detecting module is configured to detect a current signal of the resonant module;
  • the controller is respectively connected to the control end of the
  • the resonant module can be bidirectionally resonated compared to the conventional three-phase interleaved LLC resonant converter, and the energy bidirectional transmission is realized, and the output ripple current is smaller, compared to the multi-module parallel mode.
  • the device has few components and low cost.
  • the current detection signal of the resonant module is directly collected by the current detecting module. Compared with the output current feedback, the acquisition accuracy is higher and the response is faster, and the current of the resonant module can be monitored more effectively, and the current signal is reduced when the current signal exceeds the limit.
  • the output power can avoid damage caused by excessive load.
  • an in-vehicle charger of a second aspect of the present disclosure includes a three-phase PFC circuit and the DCDC converter.
  • the in-vehicle charger of the embodiment of the present disclosure by adopting the DCDC converter of the embodiment of the above aspect, high-power charging and discharging can be realized, the output ripple current is small, and the overcurrent protection function response is fast and reliable.
  • an electric vehicle includes the above-described in-vehicle charger.
  • the in-vehicle charger 1000 of the embodiment of the above aspect by installing the in-vehicle charger 1000 of the embodiment of the above aspect, high-power charging and discharging can be realized, the output ripple current is small, and the overcurrent protection function response is fast and reliable.
  • FIG. 1 is a topological schematic diagram of a three-module parallel bidirectional DCDC circuit in the related art
  • FIG. 2 is a block diagram of a DCDC transform module of one embodiment of the present disclosure
  • FIG. 3 is a circuit topology diagram of a DCDC converter in accordance with an embodiment of the present disclosure
  • FIG. 4 is a schematic diagram of an output ripple current waveform of a DCDC converter, in accordance with an embodiment of the present disclosure
  • FIG. 5 is a circuit topology diagram of a DCDC converter according to an embodiment of the present disclosure.
  • FIG. 6 is a block diagram of a DCDC converter, in accordance with one embodiment of the present disclosure.
  • FIG. 7 is a circuit topology diagram of a DCDC converter in accordance with an embodiment of the present disclosure.
  • FIG. 8 is a circuit topology diagram of a DCDC converter according to another embodiment of the present disclosure.
  • FIG. 9 is a block diagram of an in-vehicle charger in accordance with an embodiment of the present disclosure.
  • FIG. 10 is a block diagram of an electric vehicle in accordance with an embodiment of the present disclosure.
  • Embodiments of the present disclosure are based on the inventors' knowledge and research on the following issues:
  • FIG. 1 it is a circuit diagram of a typical multi-module parallel bidirectional DCDC converter. More modules are connected in parallel and so on.
  • the cost of the device is high.
  • Each module requires independent voltage, current sampling, and drive control circuits. The redundancy is large, and the cost and volume are difficult to optimize.
  • the output is The ripple current is still difficult to solve.
  • each module still needs a large filter capacitor.
  • the slave setup and high coordination requirements place high demands on the system hardware circuit design and software algorithms.
  • the present disclosure proposes a novel three-phase interleaved resonant bidirectional DCDC converter.
  • the DCDC converter 100 of the embodiment of the present disclosure includes a first adjustment module 10, a resonance module 20, a second adjustment module 30, and a controller 40. And current detection module 50.
  • the first adjustment module 10 is configured to adjust the frequency of the input signal of the DCDC converter 100 to adjust the impedance of the resonant module 20 when the battery module of the vehicle is externally charged, where the external environment may be a power grid or other power supply device.
  • the power grid charges the battery module; or, when the battery module discharges to the outside, where the external environment can be an electrical load, for example, the battery module discharges the electrical load, and the output signal of the resonant module 20 is rectified and filtered.
  • the battery module may be a power battery
  • the external device is a device, a device, or the like that can be charged and discharged with the battery module, and is not specifically limited in the embodiment of the present disclosure.
  • the resonance module 20 is configured to resonate the output signal of the first adjustment module 10 to generate a high-frequency resonance current when the battery module of the vehicle is externally charged, or to the second adjustment module 30 when the battery module discharges to the outside.
  • the output signal resonates to produce a high frequency resonant current.
  • the second adjusting module 30 is configured to adjust the frequency of the output signal of the battery module to adjust the impedance of the resonant module 20 when the battery module of the vehicle discharges to the outside, or to adjust the impedance of the resonant module 20 when the battery module is externally charged.
  • the output signal is rectified, and the high-frequency resonant current is changed to direct current to be supplied to the battery module to charge the battery module.
  • the current detecting module 50 is configured to detect the current signal of the resonant module 20, that is, directly detect the current of the resonant module 20, and feed back the current signal to the controller 40.
  • the resonance module 20 may include N primary LC cells, N phase transformation cells, and N secondary LC cells.
  • N is a positive integer greater than 1, for example, N may be 2, 3, 4, or the like.
  • N is equal to 3 as an example for description.
  • the resonance module 20 includes three primary LC units 21, a three-phase transformer unit 22, and three secondary LC units 23.
  • the three primary LC units 21 and the three-phase transformer unit 22 are used to resonate the output signal of the first adjustment module 10 to generate a high-frequency current, thereby being high.
  • the frequency current is rectified and filtered by the second adjustment module 30 to become DC power, which can be supplied to the battery module of the vehicle to realize charging of the battery module; when the battery module discharges to the outside, the three-way secondary LC unit 23 and the three-phase voltage transformation
  • the unit 22 is configured to resonate the output signal of the second adjustment module 30 to generate a high-frequency current, and the high-frequency current is rectified and filtered by the first adjustment module 10 to become a direct current, and the direct current can be supplied to a subsequent component for processing, thereby being a load. Power is supplied to discharge the battery module of the vehicle.
  • the first adjustment module 10 includes a first three-phase bridge circuit
  • the second adjustment module 30 includes a second three-phase bridge circuit, wherein each primary LC unit 21 One end is connected to a phase connection point of a corresponding phase bridge arm of the first three-phase bridge circuit 10, and the same end of the primary coil of the three-phase transformer unit 22 is respectively connected to the other end of the corresponding primary LC unit 21, and the three-phase transformer unit
  • the synonyms of the primary coils of 22 are joined together to form a Y-connection.
  • the same-name ends of the secondary coils of the three-phase transformer unit 22 are respectively connected to one ends of the corresponding secondary LC units 23, and the different-name ends of the secondary coils of the three-phase transformer unit 22 are connected together to form a Y-type connection.
  • the Y-type connection method is beneficial to the automatic current sharing of the three-phase bridge circuit, and avoids uneven power distribution due to device parameter deviation of the three-phase bridge circuit.
  • phase line connection point of each phase leg of the second three-phase bridge circuit 30 is connected to the other end of the corresponding secondary LC unit 23.
  • the controller 40 is respectively connected to the control end of the switch tube of the first three-phase bridge circuit 10 and the control end of the switch tube of the second three-phase bridge circuit 30 for the first three-phase bridge circuit 10 and the first according to the charge and discharge signal.
  • the switching tubes of the two-phase bridge circuit 30 are controlled.
  • the three-phase transformer unit 22 may adopt three independent magnetic cores or may be wound by the same magnetic core.
  • each primary LC unit 21 and the primary coil of the corresponding transformer unit 22 may constitute a corresponding input resonant cavity, and the controller 40 performs high on the first three-phase bridge circuit 10.
  • Frequency resonance control and rectification control of the second three-phase bridge circuit 30, the first three-phase bridge circuit 10 and the three primary LC units 21 and the primary coil of the three-phase transformer unit 22 form a three-phase interleaved LLC to operate at high frequency resonance
  • the state outputs a high-frequency current, and the high-frequency current is rectified by the second three-phase bridge circuit 30 to become a direct current output, which can charge the entire vehicle battery module of the electric vehicle.
  • each secondary LC unit 23 and the secondary coil of the corresponding transformer unit 22 may constitute a corresponding input resonant cavity, and the controller 40 performs high frequency resonance control on the second three-phase bridge circuit 30. And performing rectification control on the first three-phase bridge circuit 10, the second three-phase bridge circuit 10 and the three-way secondary LC unit 23 and the secondary coil of the three-phase transformer unit 22 form a three-phase interleaved LLC to operate in a high-frequency resonance state And outputting a high-frequency current, which is rectified by the first three-phase bridge circuit 10 to become a direct current output, and discharge of the battery module can be realized.
  • the secondary side of the transformer unit increases the resonance unit compared to the conventional three-phase interleaved LLC resonant converter, and can perform bidirectional resonance, realize energy bidirectional transmission, and have uniform power distribution and output.
  • the ripple current is smaller and the device is less costly.
  • the DCDC converter described above still has some disadvantages.
  • the three-phase transformer can be naturally current-averaged by the Y-connection method, if the three-phase bridge resonance parameter deviation is large, the resonance parameters of the three resonators may be deviated. Eventually the three-phase bridge power imbalance occurs. Because of the characteristics of the LLC circuit, the resonant cavity will have a large resonant current when the system starts. The conventional output current feedback start control strategy is difficult to effectively monitor the resonant cavity current. If the feedback parameters are not well matched, the resonant cavity will have a large inrush current during the startup process. Will affect the life of the product or even damage in advance.
  • the DCDC converter 100 of the embodiment of the present disclosure directly detects the current signal of the resonance module 20 through the current detecting module 50, that is, the current flowing through each phase.
  • the detection is performed separately, and the current signal is fed back to the controller 40, and the current signal of the resonance module 20 is directly collected with respect to the conventional output current feedback, and the precision is high, and the feedback response is faster.
  • the controller 40 is connected to the control end of the first adjustment module 10, and the controller 40 is also connected to the control end of the second adjustment module 30 for the first adjustment module 10 and the second adjustment module 30 when the current signal is greater than the current threshold. Control is performed to reduce the output power to reduce the output power of the system and reduce the operating current of the system to avoid excessive load, resulting in damage to the three-phase bridge circuit.
  • the current signal of the resonance module 20 is directly collected by the current detecting module 50. Compared with the output current feedback, the acquisition accuracy is higher, the response is faster, and the resonance module 20 can be monitored more effectively.
  • the current reduces the output power when the current signal exceeds the limit, which can avoid damage caused by excessive load.
  • the first three-phase bridge circuit 10 and the second three-phase bridge circuit 30 may be constituted by a switching tube such as a MOS tube or an IGBT or other components to form a three-phase bridge structure
  • the LC unit may include a capacitor and an inductor
  • the transformer unit may be a transformer structure achieve.
  • the first three-phase bridge circuit 10 includes a first one-phase bridge arm, a first two-phase bridge arm, and a first three-phase bridge arm.
  • the first phase bridge arm includes a first switch tube Q1 and a second switch tube Q2.
  • first switch tube Q1 is connected to one end of the second switch tube Q2, and one end of the first switch tube Q1 and the second switch tube Q2 There is a first phase line connection point Z1 between one end;
  • the first two-phase bridge arm includes a third switch tube Q3 and a fourth switch tube Q4, one end of the third switch tube Q3 is connected to one end of the fourth switch tube Q4, and the third A second phase line connection point Z2 is formed between one end of the switch tube Q3 and one end of the fourth switch tube Q4;
  • the first three bridge arm includes a fifth switch tube Q5 and a sixth switch tube Q6, and one end of the fifth switch tube Q5 is One end of the sixth switch tube Q6 is connected, and one end of the fifth switch tube Q5 and one end of the sixth switch tube Q6 have a third phase line connection point Z3;
  • the other end of the first switch tube Q1 and the third switch tube Q3 The other end is connected to the other end of the fifth switching transistor Q5 to form a first end point S11 of the first three-
  • the first three-phase bridge circuit 10 further includes a first capacitor C1.
  • One end of the first capacitor C1 is connected to the first end point S11 of the first three-phase bridge circuit 10, and the other end of the first capacitor C1 is The second terminal S12 of the first three-phase bridge circuit 10 is connected to filter the output or input of the first three-phase bridge circuit 10.
  • the three-way primary LC unit 21 includes a first primary LC unit, a second primary LC unit, and a third primary LC unit.
  • the first primary LC unit includes a second capacitor C2 and a first inductor L1.
  • One end of the second capacitor C2 is connected to the first phase line connection point Z1, and the other end of the second capacitor C2 is connected to one end of the first inductor L1.
  • the second primary LC unit includes a third capacitor C3 and a second inductor L2, and one end of the third capacitor C3 is connected to the second phase line Z2 Connected, the other end of the third capacitor C3 is connected to one end of the second inductor L2, the other end of the second inductor L2 is connected to the same end of the primary coil of the corresponding phase shifting unit 22; the third primary LC unit includes a fourth capacitor C4.
  • one end of the fourth capacitor C4 is connected to the third phase line connection point Z3
  • the other end of the fourth capacitor C4 is connected to one end of the third inductor L3
  • the other end of the third inductor L3 is corresponding to the phase change.
  • the same name end of the primary coil of the press unit 22 is connected.
  • the three-phase transformation unit 22 includes a first phase transformation unit T1, a second phase transformation unit T2, and a third phase transformation unit T3.
  • the first phase transformation unit T1 includes a first primary coil and a first secondary coil, and the same end of the first primary coil is connected to the other end of the first inductor L1, and the same name end of the first secondary coil and the corresponding secondary One end of the LC unit 23 is connected;
  • the second phase transforming unit T2 includes a second primary coil and a second secondary coil, the same end of the second primary coil is connected to the other end of the second inductor L2, and the second secondary coil has the same name The end is connected to one end of the corresponding secondary LC unit 23;
  • the third phase transforming unit T3 includes a third primary coil and a third secondary coil, and the same end of the third primary coil is connected to the other end of the third inductor L3, and the third The same-name end of the secondary coil is connected to one end of the corresponding secondary LC unit 23;
  • the different-name end of the first primary coil, the different-name end of the second primary coil, and the different-name end of the third primary coil are connected together, for example
  • the second three-phase bridge circuit 30 includes a second one-phase bridge arm, a second two-phase bridge arm, and a second three-phase bridge arm.
  • the second phase bridge arm includes a seventh switch tube Q7 and an eighth switch tube Q8.
  • One end of the seventh switch tube Q7 is connected to one end of the eighth switch tube Q8, and one end of the seventh switch tube Q7 and the eighth switch tube
  • the second two-phase bridge arm includes a ninth switch tube Q9 and a tenth switch tube Q10, and one end of the ninth switch tube Q9 is connected to one end of the tenth switch tube Q10,
  • a fifth phase line connection point Z5 is formed between one end of the ninth switch tube Q9 and one end of the tenth switch tube Q10;
  • the second three-phase bridge arm includes an eleventh switch tube Q11 and a twelfth switch tube Q12, the eleventh One end of the switch tube Q11 is connected to one end of the twelfth switch tube Q12, and one end of the eleventh switch tube Q11 and one end of the twelfth switch tube Q12 have a sixth
  • the second three-phase bridge circuit 30 further includes a fifth capacitor C5.
  • One end of the fifth capacitor C5 is connected to the first end point S21 of the second three-phase bridge circuit 30, and the other end of the fifth capacitor C5 is The second end point S22 of the second three-phase bridge circuit 30 is connected.
  • the fifth capacitor C5 can filter the output or input of the second three-phase bridge circuit 30.
  • the three-way secondary LC unit 23 includes a first secondary LC unit, a second secondary LC unit, and a third secondary LC unit.
  • the first secondary LC unit includes a fourth inductor L4 and a sixth capacitor C6.
  • One end of the fourth inductor L4 is connected to the same end of the first secondary coil, and the other end of the fourth inductor L4 and one end of the sixth capacitor C6.
  • the other end of the sixth capacitor C6 is connected to the fourth phase line connection point Z4;
  • the second secondary LC unit includes a fifth inductor L5 and a seventh capacitor C7, and one end of the fifth inductor L5 has the same name as the second secondary coil
  • the other end of the fifth inductor L5 is connected to one end of the seventh capacitor C7, the other end of the seventh capacitor C7 is connected to the fifth phase line connection point Z5, and
  • the third secondary LC unit includes a sixth inductor L6 and the eighth The capacitor C8, one end of the sixth inductor L6 is connected to the same end of the third coil, the other end of the sixth inductor L6 is connected to one end of the eighth capacitor C8, and the other end of the eighth capacitor C8 is connected to the sixth phase line Z6. Connected.
  • the first three-phase bridge circuit 10 is connected to the charging input, and the second three-phase bridge circuit 30 is connected to the battery module of the electric vehicle.
  • the second capacitor C2, the first inductor L1 and the first The primary coil constitutes a resonant cavity of the first one-phase bridge arm
  • the third capacitor C3, the second inductor L2 and the second primary coil constitute a resonant cavity of the first two-phase bridge arm
  • a fourth capacitor C4 a third inductor L3 and a third The primary coil constitutes a resonant cavity of the first three-phase bridge arm.
  • the second capacitor C2, the third capacitor C3, and the fourth capacitor C4 are referred to as primary resonant capacitors, and the first inductor L1, the second inductor L2, and the third inductor L3 are referred to as primary resonant inductors.
  • each phase bridge arm of the first three-phase bridge arm circuit 10 and its corresponding resonance module form a three-phase interleaved LLC and operate in a high-frequency resonance state, and the controller 40 controls the first switch tube Q1.
  • the second switch tube Q2, the third switch tube Q3 and the fourth switch tube Q4, the fifth switch tube Q5 and the sixth switch tube Q6 are respectively alternately switched at a 50% duty ratio, and the first switch tube Q1 and the third switch are controlled.
  • the phase between the tube Q3 and the fifth switch tube Q5 is 120° different from each other, and the phase between the second switch tube Q2, the fourth switch tube Q4 and the sixth switch tube Q6 is controlled to be 120°, and the second phase is respectively
  • the bridge circuit 30 performs rectification control, and the second three-phase bridge circuit 30 functions as a secondary three-phase rectifier bridge.
  • the high-frequency current is rectified by the diode in the switching body of the second three-phase bridge circuit 30, and then converted into direct current and supplied to the entire vehicle.
  • a high voltage battery module wherein, as shown generally in FIG. 5, each of the switching tubes includes a diode element, which may be referred to as a switching body diode. If the drive signal is applied to the switching tube of the second three-phase bridge circuit 30, the second three-phase bridge circuit 30 will form a synchronous rectification circuit, further improving product efficiency.
  • the first three-phase bridge circuit 10 is connected to the power side
  • the second three-phase bridge circuit 30 is connected to the battery module of the electric vehicle.
  • the sixth capacitor C6, the fourth inductor L4, and the A secondary coil constitutes a resonant cavity of the second phase bridge arm
  • the seventh capacitor C7, the fifth inductor L5 and the second secondary coil constitute a resonant cavity of the second two-phase bridge arm
  • the third secondary coil constitutes a resonant cavity of the second three-phase bridge arm.
  • the sixth capacitor C6, the seventh capacitor C7, and the eighth capacitor C8 are referred to as secondary resonant capacitors
  • the fourth inductor L4, the fifth inductor L5, and the sixth inductor L6 are referred to as secondary resonances. inductance.
  • each phase bridge arm of the second three-phase bridge arm circuit 30 and its corresponding resonance module form a three-phase interleaved LLC and operate in a high-frequency resonance state, and the controller 40 controls the seventh switch tube Q7.
  • the eighth switch tube Q8, the ninth switch tube Q9 and the tenth switch tube Q10, the eleventh switch tube Q11 and the twelfth switch tube Q12 are respectively alternately switched at a 50% duty ratio, and the seventh switch tube Q7 is controlled.
  • the phase between the nine switch tube Q9 and the eleventh switch tube Q11 is 120° different from each other, and the phase between the eighth switch tube Q8, the tenth switch tube Q10 and the twelfth switch tube Q12 is controlled by 120°, respectively, and
  • the first three-phase bridge circuit 10 performs rectification control, and the first three-phase bridge circuit 30 functions as a discharge output three-phase rectifier bridge.
  • the high-frequency current is converted into direct current by a diode in the switching body of the first three-phase bridge circuit 30, and is provided.
  • the drive signal is applied to the switch tube of the first three-phase bridge circuit 10 will form a synchronous rectification circuit, further improving product efficiency.
  • the current detecting circuit 50 of the embodiment of the present disclosure includes a first acquiring unit 51, a second collecting unit 52, a third collecting unit 53, and a fourth.
  • the first collecting unit 51 is configured to collect the current signal of the first inductor L1; the second collecting unit 52 is configured to collect the current signal of the L2 second inductor; and the third collecting unit 53 is configured to collect the current signal of the third inductor L3;
  • the fourth collecting unit 54 is configured to collect the current signal of the fourth inductor L4; the fifth collecting unit 55 is configured to collect the current signal of the fifth inductor L5; and the sixth collecting unit 56 is configured to collect the current signal of the sixth inductor L6.
  • N 1 , 2, 3...6.
  • a first conversion unit 57, a second conversion unit 58, a third conversion unit 59, a fourth conversion unit 510, a fifth conversion unit 511, and a sixth conversion unit 512 are included.
  • the first converting unit 57 is configured to convert the current signal of the first inductor L1;
  • the second converting unit 58 is configured to convert the current signal of the second inductor L2;
  • the third converting unit 59 is configured to the third inductor L3.
  • the current signal is converted; the fourth converting unit 510 is configured to convert the current signal of the fourth inductor L4; the fifth converting unit 511 is configured to convert the current signal of the fifth inductor L5; and the sixth converting unit 512 is configured to The current signal of the sixth inductor L6 is converted. In order to convert the current signal of each path into a signal that the controller 40 can recognize and process.
  • the first acquiring unit 51, the second collecting unit 52, the third collecting unit 53, the fourth collecting unit 54, the fifth collecting unit 55, and the sixth collecting unit 56 are respectively an autotransformer or a current transformer. .
  • the auto-coupling inductor and the resonant inductance of each channel are induced to generate a high-frequency alternating current signal, thereby realizing the detection of the current signal of each resonant inductor.
  • the auto-coupling inductor is an auxiliary auto-coupling coil of resonant inductor.
  • the auto-coupling inductor does not need to add additional current detecting devices, and other related resistors, capacitors and op amps are common components, which has little effect on system cost.
  • the current transformer can be an independent external device. According to the detection principle of the current transformer, the main side coil and the resonant inductor are connected in series in the circuit, and the current signal of the resonant inductor is realized by the mutual inductance of the secondary side coil and the main side coil. Detection.
  • the Nth conversion unit includes an Nth rectifying circuit 501, an Nth voltage converting circuit 502, and an Nth voltage follower circuit 503.
  • the Nth rectifier circuit 501 is configured to rectify the current signal collected by the Nth acquisition unit to obtain a rectified signal;
  • the Nth voltage conversion circuit 502 is configured to convert the rectified signal into a voltage signal; and the Nth voltage follower circuit 503 is used.
  • the controller 40 is configured to control the switching tubes of the first three-phase bridge circuit 10 and the second three-phase bridge circuit 30 when the AD signal is greater than the preset AD value, when the AD value exceeds the standard.
  • the control output power is reduced, and the system operating current is reduced to avoid the phase load being excessively large.
  • the controller 40 controls the switching of the first one-phase bridge arm, the switching tube of the first two-phase bridge arm, and the opening of the first three-phase bridge arm
  • the ratio is reduced to reduce the output power; or, when the battery module discharges to the outside, if an overcurrent occurs, the switching tube of the second phase bridge arm, the switching tube of the second two-phase bridge arm, and the second three-phase bridge arm are controlled.
  • the duty cycle of the switching transistor is reduced to reduce the output power. By reducing the output power, the operating current of the system is reduced to avoid excessive load, and the product has a large inrush current, which may affect the product life or even damage in advance.
  • the Nth rectifying circuit 501 includes a first diode D1, a second diode D2, a third diode D3, and a fourth diode D4.
  • One end of the first diode D1 and the first One end of the diode D2 is connected, and one end of the first diode D1 and one end of the second diode D2 have a first input node, and the first input node is connected to the first output end of the corresponding acquisition unit, for example
  • the acquisition unit outputs a signal sense1, one end of the third diode D2 is connected to one end of the fourth diode D4, and a second input is provided between one end of the third diode D3 and one end of the fourth diode D4.
  • the second input node is connected to the second output end of the corresponding acquisition unit, for example, the acquisition unit output signal sense2 in the figure, the other end of the first diode D1 is connected with the other end of the third diode D3 to form The first rectified output end, the other end of the second diode D2 is connected to the other end of the fourth diode D4 and connected to the ground end;
  • the Nth voltage conversion circuit 502 includes a first resistor R1, and the first resistor R1 One end is connected to the first rectified output end, for example, the output signal Vsense, the first electric The other end of R1 is connected to the ground;
  • the Nth voltage follower circuit 503 includes a second resistor R2, a voltage follower U1B, a third resistor R3 and a ninth capacitor C9, one end of the second resistor R2 and one end of the first resistor R1 Connected, the forward input of the voltage follower U1B is connected to the other end of the second resistor R2, the output of
  • the other end of the third resistor R3 is connected to the controller 40, for example, the AD signal Isense is outputted to the controller 40, and one end of the ninth capacitor C9 is connected between the third resistor R3 and the controller 40, ninth The other end of the capacitor C9 is connected to the ground, and the controller 40 adjusts the system power according to the AD signal.
  • the circuit can also be adaptively deformed as needed, such as adding capacitance for filtering processing, or using parallel or series resistors for voltage conversion or acquisition, etc., and FIG. 5 is merely an example circuit.
  • the high frequency alternating current signal induced by the autotransformer 51 of the first inductor L1 is transmitted to the rectifier circuit and the first resistor R1, and then converted into a high frequency half-wave voltage signal Vsense, the voltage signal Vsense After passing through the voltage follower U1B, it becomes the AD signal Isense, and transmits the medium controller 40. If the controller 40 finds that the AD signal exceeds the standard, the control output power is lowered, and the system operating current is reduced to prevent the phase load from being excessively large, causing damage.
  • the Nth conversion unit further includes an Nth comparison circuit 504, that is, each conversion unit includes a respective The comparison circuit, the Nth comparison circuit 504 is configured to output a stop signal to the controller 40 when the current signal exceeds the jump threshold, and the controller 40 turns off the first three-phase bridge circuit 10 and the second three when detecting the stop signal
  • the switching of the switching tube of the phase bridge circuit 30 prevents the converter from being damaged and guarantees the life.
  • the Nth comparison circuit 504 includes a fourth resistor R4, a fifth resistor R5, and a tenth capacitor C10, a comparator U1A, an eleventh capacitor C11, and a twelfth capacitor C12.
  • the one end of the fourth resistor R4 is connected to one end of the first resistor R1.
  • the voltage signal Vsense outputted by the voltage conversion circuit 502 is input to the comparison circuit 504, and the other end of the fourth resistor R4 is connected to one end of the fifth resistor R5.
  • One end of the ten capacitor C10 is connected between the other end of the fourth resistor R4 and one end of the fifth resistor R5; the first input end of the comparator U1A is connected to the other end of the fifth resistor R5, and the second input end of the comparator U1A
  • the sixth end of the comparator U1A is connected to the ground terminal through the sixth resistor R6, the third end of the comparator U1A is connected to the preset power source, and the output end of the comparator U1A is controlled by the seventh resistor R7.
  • the controller 40 is connected, for example, to output a protection signal Iprotect to the controller 40; one end of the eleventh capacitor C11 is respectively connected to the fourth end of the comparator U1A and the preset power source, and the other end of the eleventh capacitor C11 is connected to the ground end, One end of the twelve capacitor C12 is connected between the seventh resistor R7 and the controller 40, and the other end of the twelfth capacitor C12 is connected to the ground.
  • the voltage signal Vsense is transmitted to the comparison circuit 504, and a hardware high and low level signal is output after the comparator U1A.
  • the U1A When the U1A outputs a high level, it indicates that the phase resonant cavity current has seriously exceeded the standard, and the controller 40 After the high level signal is detected, the switch tube drive is turned off immediately, and the system stops working to avoid damage to the converter.
  • the DCDC converter of the embodiment of the present disclosure directly forms a resonant cavity by forming a current transformer through an auxiliary autotransformer of the resonant inductor or by setting an independent external current transformer, compared to estimating the resonant cavity current by output current sampling.
  • the current signal is controlled and protected according to the current signal.
  • each of the acquisition units is an autotransformer of the resonant inductor.
  • the design requirements are as follows: the input voltage and output voltage rating of the DCDC converter are both 750V, and the full load power in both the charging direction and the discharging direction is 20KW.
  • the cavity parameter setting since the forward charging voltage and the power are equal, the resonant cavity corresponding to the first three-phase bridge circuit 10, for example, the resonant cavity of the primary resonant cavity and the corresponding second three-phase bridge circuit 30 is called, for example.
  • the parameters of the secondary resonator are the same.
  • the switch tube Q1-Q12 selects 1200V/40m ⁇ silicon oxide MOS (metal oxide semiconductor) tube
  • each acquisition unit is a current transformer of an independent peripheral, and the design requirement is: DCDC
  • the input voltage and output voltage rating of the converter are both 750V, and the full load power in both the charging direction and the discharging direction is 20KW.
  • the cavity parameter setting since the forward charging voltage and the power are equal, the resonant cavity corresponding to the first three-phase bridge circuit 10, for example, the resonant cavity of the primary resonant cavity and the corresponding second three-phase bridge circuit 30 is called, for example.
  • the parameters of the secondary resonator are the same.
  • the ratio of auto-coupling inductance to resonant inductance is 100:1
  • the DCDC converter 100 of the embodiment of the present disclosure adds a three-way resonance unit on the transformer secondary side, and the second three-phase bridge circuit 30 uses a controllable switch tube, compared with the conventional three-phase full-bridge DCDC converter.
  • bidirectional resonance can realize bidirectional transmission of energy, and bidirectional transmission works in soft switching mode; forming a three-phase interleaved LLC can realize greater power conversion, and can save power switching tube compared with ordinary three-phase interleaved LLC, and
  • the three-phase transformer unit 22 adopts a Y-connection method, which can realize automatic current sharing of the three-phase bridge circuit, avoid uneven power distribution, and the circuit structure of the DCDC converter 100 based on the embodiment of the present disclosure, and the output ripple current is more Smaller, smaller ripple currents save output filter capacitors, which is more conducive to cost reduction and product size reduction.
  • the resonant inductance of each channel is increased by one auto-coupling inductor.
  • the resonant inductor functions as a staggered resonance, and also constitutes a current transformer with the auto-transformer to achieve a pair.
  • the detection of the current signal of the resonant inductor does not require an additional current detecting device, and the cost is low; or, by adding a separate current transformer to each of the resonant inductors, the detection of the current signal of the resonant inductor is realized.
  • the current signal of the resonant inductor is directly collected, the precision is high, the response is faster, and the hardware and software are double-protected, and the reliability is high.
  • the current signal of the resonant cavity is processed and transmitted to the AD sampling port of the controller 40, and the controller 40 according to the AD The value is adjusted to the system power.
  • the resonant cavity current limit triggers the hardware fast comparator and directly outputs the overcurrent lock protection signal.
  • the controller 40 directly turns off the third.
  • the phase-bridge switch is driven to avoid system damage.
  • the over-current protection function is fast and stable through two-fold protection of hardware and software.
  • the in-vehicle charger 1000 of the embodiment of the present disclosure includes a three-phase PFC circuit 200 and the DCDC converter 100 of the above embodiment, a three-phase PFC circuit. 200 functions as a power factor correction.
  • the DCDC converter 100 implements controllable isolated transmission of energy. The specific structure and operation of the DCDC converter 100 are described with reference to the above embodiments.
  • the in-vehicle charger 1000 of the embodiment of the present disclosure by adopting the DCDC converter 100 of the above embodiment, high power charging and discharging can be realized, the output ripple current is small, and the overcurrent protection function response is fast and reliable.
  • an electric vehicle 10000 of an embodiment of the present disclosure includes the in-vehicle charger 1000 of the above-described embodiment.
  • the electric vehicle 10000 of the embodiment of the present disclosure by installing the in-vehicle charger 1000 of the above embodiment, high-power charging and discharging can be realized, the output ripple current is small, and the overcurrent protection function response is fast and reliable.

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Abstract

本公开公开了DCDC变换器、车载充电机和电动车辆，DCDC变换器包括第一调整模块、谐振模块、第二调整模块和控制器，第一调整模块用于在充电时对DCDC变换器的输入信号的频率进行调节，或者在放电时对谐振模块的输出信号进行整流；谐振模块用于在充电时对第一调整模块的输出信号进行谐振，或者在放电时对第二调整模块的输出信号进行谐振；第二调整模块用于在放电时对电池模块的输出信号的频率进行调节，在充电时对谐振模块的输出信号进行整流；电流检测模块用于检测谐振模块的电流信号；控制器用于在电流信号大于电流阈值时对第一调整模块和第二调整模块进行控制以降低输出功率。通过直接检测谐振模块的电流信号，更加精准，响应更快。

Description

DCDC变换器、车载充电机和电动车辆
相关申请的交叉引用
本申请基于申请号为201810385200.1，申请日为2018年04月26日的中国专利申请提出，并要求该中国专利申请的优先权，该中国专利申请的全部内容在此引入本申请作为参考。
技术领域
本公开涉及车辆技术领域，尤其涉及一种DCDC变换器，以及包括该DCDC变换器的车载充电机和安装该车载充电机的电动车辆。
背景技术
随着电动车辆的不断发展，电动车辆的电池模块的容量越来越大。为了节省充放电时间，大容量的电池模块需要更大功率的双向车载充电机(以下简称车载充电机)。目前行业上主流车载充电机功率等级为单相3.3KW/6.6KW，随着大功率车载充电机的进一步需求，三相10/20/40KW车载充电机有着越来越大的市场。
车载充电机主功率拓扑一般包括PFC(Power Factor Correction，功率因数校正)+双向DCDC两部分，PFC起到功率因素校正作用；双向DCDC实现能量可控隔离传输，是车载充电机的核心功率转换单元，为了满足大功率充放电的需求，大功率双向DCDC变换器通常采用多模块并联，但是，多模块并联存在一些问题，使得对系统硬件电路设计及软件算法均提出很高要求。
发明内容
本公开旨在至少在一定程度上解决相关技术中的技术问题之一。
为此，本公开的一个实施例在于提出一种DCDC变换器，该DCDC变换器更加适用于大功率车载充电机，成本低，结构简单。
本公开的再一个实施例在于提出一种包括该DCDC变换器的车载充电机。
本公开的又一个实施例在于提出一种安装该车载充电机的电动车辆。
为了达到上述目的，本公开第一方面实施例的DCDC变换器，包括：第一调整模块、谐振模块、第二调整模块、电流检测模块和控制器，其中，所述第一调整模块，用于在外界对车辆的电池模块充电时对DCDC变换器的输入信号的频率进行调节，或者，用于在所述电池模块对外界放电时对所述谐振模块的输出信号进行整流；所述谐振模块，用于在外界对 车辆的电池模块进行充电时对所述第一调整模块的输出信号进行谐振，或者，用于在所述电池模块对外界放电时对所述第二调整模块的输出信号进行谐振；所述第二调整模块，用于在车辆的电池模块对外界放电时对所述电池模块的输出信号的频率进行调节，或者，用于在外界对所述电池模块充电时对所述谐振模块的输出信号进行整流；；电流检测模块，所述电流检测模块用于检测所述谐振模块的电流信号；控制器，所述控制器分别与所述第一调整模块的控制端和所述第二调整模块的控制端相连，用于在所述电流信号大于电流阈值时对所述第一调整模块和所述第二调整模块进行控制以降低输出功率。
根据本公开实施例的DCDC变换器，相较于普通的三相交错LLC谐振变换器，谐振模块可以双向谐振，实现能量双向传输，输出纹波电流更小，相较于多模块并联方式，使用器件少，成本低，通过电流检测模块直接采集谐振模块的电流信号，相较于输出电流反馈，采集精度更高，响应更加快速，可以更加有效地监测谐振模块的电流，在电流信号超限时降低输出功率，可以避免负载过大而造成损坏。
为了达到上述目的，本公开第二方面实施例的车载充电机，包括三相PFC电路和所述的DCDC变换器。
根据本公开实施例的车载充电机，通过采用上述方面实施例的DCDC变换器，可以实现大功率充放电，输出纹波电流小，过流保护功能响应快速且可靠。
为了达到上述目的，本公开第三方面实施例的电动车辆，包括所述的车载充电机。
根据本公开实施例的电动车辆，通过安装上述方面实施例的车载充电机1000，可以实现大功率充放电，输出纹波电流小，过流保护功能响应快速且可靠。
附图说明
图1是相关技术中的三模块并联双向DCDC电路拓扑示意图；
图2是本公开的一个实施例的DCDC变换模块的框图；
图3是根据本公开的一个实施例的DCDC变换器的电路拓扑示意图；
图4是根据本公开的一个实施例的DCDC变换器的输出纹波电流波形示意图；
图5是根据本公开的一个实施例的DCDC变换器的电路拓扑示意图；
图6是根据本公开的一个实施例的DCDC变换器的框图；
图7是根据本公开的一个实施例的DCDC变换器的电路拓扑示意图；
图8是根据本公开另一个实施例的DCDC变换器的电路拓扑示意图；
图9是根据本公开的一个实施例的车载充电机的框图；
图10是根据本公开的一个实施例的电动车辆的框图。
具体实施方式
下面详细描述本公开的实施例，所述实施例的示例在附图中示出，其中自始至终相同或类似的标号表示相同或类似的元件或具有相同或类似功能的元件。下面通过参考附图描述的实施例是示例性的，旨在用于解释本公开，而不能理解为对本公开的限制。
本公开的实施例是基于发明人对以下问题的认识和研究做出的：
如图1所示，为典型的多模块并联双向DCDC变换器的电路示意图，更多模块并联以此类推。对于如图1所示的方案存在一些问题例如，器件多成本高，每个模块需要独立的电压、电流采样以及驱动控制电路，冗余性较大，成本、体积难以最优化；再例如，输出波纹电流大仍难以解决，为了降低波纹电流，每个模块仍需要较大的滤波电容，当然也有多个独立模块之间进行相位交错降低波纹电流，但也需要不同模块时间协同工作，需要有主从机设置且协同要求高，这对系统硬件电路设计及软件算法均提出很高要求。
下面参照附图描述根据本公开实施例的DCDC变换器。
针对相关技术中为了满足大功率充放电的需求采用如图1所示的多模块并联方式存在的缺陷，本公开实施例提出一种新颖的三相交错谐振双向DCDC变换器。
图2是根据本公开实施例的DCDC变换器的框图，如图3所示，本公开实施例的DCDC变换器100包括第一调整模块10、谐振模块20、第二调整模块30、控制器40和电流检测模块50。
其中，第一调整模块10用于在外界对车辆的电池模块充电时对DCDC变换器100的输入信号的频率进行调节以调整谐振模块20的阻抗，在这里，外界可以是电网或其他供电设备，例如电网对电池模块充电；或者，用于在电池模块对外界放电时，在这里，外界可以是用电负载，例如电池模块对用电负载放电，对谐振模块20的输出信号进行整流滤波以供后端负载用。其中，电池模块可以为动力电池，外界为能够与电池模块之间实现充放电的设备、装置或其他，在本公开的实施例中不作具体限定。
谐振模块20用于在外界对车辆的电池模块进行充电时对第一调整模块10的输出信号进行谐振以产生高频谐振电流，或者，用于在电池模块对外界放电时对第二调整模块30的输出信号进行谐振以产生高频谐振电流。
第二调整模块30用于在车辆的电池模块对外界放电时对电池模块的输出信号的频率进行调节以调节谐振模块20的阻抗，或者，用于在外界对电池模块充电时对谐振模块20的输出信号进行整流，高频谐振电流变为直流电，以提供给电池模块，实现对电池模块的充电。
电流检测模块50用于检测谐振模块20的电流信号，即直接对谐振模块20的电流进行检测，并将电流信号反馈至控制器40。
在本公开的实施例中，谐振模块20可包括N路初级LC单元、N相变压单元和N路次级LC单元。其中，N为大于1的正整数，例如，N可以为2、3、4等。为了便于对本公开进行描述，在下面的实施例中，均以N等于3为例进行说明。
如图3所示，谐振模块20包括三路初级LC单元21、三相变压单元22和三路次级LC单元23。
在本公开的实施例中，在外界对电池模块充电时，三路初级LC单元21和三相变压单元22用于对第一调整模块10的输出信号进行谐振以产生高频电流，进而高频电流通过第二调整模块30整流滤波后变成直流电，可以提供给车辆的电池模块，实现对电池模块的充电；在电池模块对外界放电时，三路次级LC单元23和三相变压单元22用于对第二调整模块30的输出信号进行谐振以产生高频电流，高频电流通过第一调整模块10进行整流滤波后变为直流电，直流电可提供给后续元器件处理，进而为负载供电，实现车辆的电池模块的放电。
在本公开的一些实施例中，如图3所示，第一调整模块10包括第一三相桥电路，第二调整模块30包括第二三相桥电路，其中，每一路初级LC单元21的一端与第一三相桥电路10中对应相桥臂的相线连接点相连，三相变压单元22的初级线圈的同名端分别与对应初级LC单元21的另一端相连，三相变压单元22的初级线圈的异名端连接在一起，以形成Y型连接。三相变压单元22的次级线圈的同名端分别与对应次级LC单元23的一端相连，三相变压单元22的次级线圈的异名端连接在一起，以形成Y型连接，采用Y型接法，有利于三相桥电路实现自动均流，避免由于三相桥电路的器件参数偏差带来的功率分布不均。
第二三相桥电路30的每一相桥臂的相线连接点与对应次级LC单元23的另一端相连。
控制器40分别与第一三相桥电路10的开关管的控制端和第二三相桥电路30的开关管的控制端相连，用于根据充放电信号对第一三相桥电路10和第二三相桥电路30的开关管进行控制。
在本公开的实施例中，三相变压单元22可以采用三个独立磁芯也可以采用同一个磁芯绕制。
在实施例中，在外界对电池模块充电时，每一路初级LC单元21与对应的变压单元22的初级线圈可以构成对应输入的谐振腔，控制器40对第一三相桥电路10进行高频谐振控制以及对第二三相桥电路30进行整流控制，第一三相桥电路10与三路初级LC单元21以及三相变压单元22的初级线圈组成三相交错LLC工作于高频谐振状态，并输出高频电流，高频电流通过第二三相桥电路30进行整流之后变成直流电输出，可以为电动车辆的整车电池模块充电。
在电池模块对外界放电时，每一路次级LC单元23与对应的变压单元22的次级线圈可 以构成对应输入的谐振腔，控制器40对第二三相桥电路30进行高频谐振控制以及对第一三相桥电路10进行整流控制，第二三相桥电路10与三路次级LC单元23以及三相变压单元22的次级线圈组成三相交错LLC工作于高频谐振状态，并输出高频电流，高频电流通过第一三相桥电路10进行整流之后变成直流电输出，可以实现电池模块的放电。
基于本公开实施例的DCDC变换器100，输出波纹电流小，如图4所示，P1为普通全桥电路输出波纹电流曲线，P2为本申请结构的输出波纹电流曲线，与普通全桥电路相比，在相同输出电流I 0的条件下，普通全桥电路输出波纹电流I ripple＝πI 0/2＝1.57I 0，而基于本申请的电路，输出波纹电流为
Figure PCTCN2019084328-appb-000001
显然输出纹波电流更小，更小的纹波电流更加有利于节省输出滤波电容。
根据本公开实施例的DCDC变换器100，相较于普通的三相交错LLC谐振变换器，变压单元的次级侧增加谐振单元，可以双向谐振，实现能量双向传输，且功率分布均匀，输出纹波电流更小，器件少成本低。
但是，以上描述的DCDC变换器仍然存在一些缺点，例如，虽然三相变压器以Y型接法可以自然均流，但是如果三相桥谐振参数偏差较大，三个谐振腔谐振参数会有偏差，最终导致三相桥功率不平衡。因为LLC电路的特性，系统启动时谐振腔会有较大谐振电流，常规的输出电流反馈启动控制策略难以有效监测谐振腔电流，如果反馈参数匹配不好，启动过程谐振腔会有较大冲击电流，将影响产品寿命甚至提前损坏。
针对上面提出的问题，本公开实施例进一步改进，如图2所示，本公开实施例的DCDC变换器100通过电流检测模块50直接检测谐振模块20的电流信号，即对流经每一相的电流分别进行检测，并将电流信号反馈至控制器40，相对于常规的输出电流反馈，直接采集谐振模块20的电流信号，精度高，反馈响应更加快速。控制器40与第一调整模块10的控制端连接，控制器40也与第二调整模块30的控制端连接，用于在电流信号大于电流阈值时对第一调整模块10和第二调整模块30进行控制以降低输出功率，以降低系统的输出功率，减小系统工作电流以避免负载过大，造成对三相桥电路的损坏。
根据本公开实施例的DCDC变换器100，通过电流检测模块50直接采集谐振模块20的电流信号，相较于输出电流反馈，采集精度更高，响应更加快速，可以更加有效地监测谐振模块20的电流，在电流信号超限时降低输出功率，可以避免负载过大而造成损坏。
下面参照附图对本公开的各个单元及其连接关系进一步说明。其中，第一三相桥电路10和第二三相桥电路30可以由开关管例如MOS管或IGBT或其他元件构成三相桥结构，LC 单元可以包括电容和电感，变压单元可以由变压器结构实现。
在本公开的一些实施例中，如图5所示，第一三相桥电路10包括第一一相桥臂、第一二相桥臂和第一三相桥臂。第一一相桥臂包括第一开关管Q1和第二开关管Q2，第一开关管Q1的一端与第二开关管Q2的一端相连，第一开关管Q1的一端与第二开关管Q2的一端之间具有第一相线连接点Z1；第一二相桥臂包括第三开关管Q3和第四开关管Q4，第三开关管Q3的一端与第四开关管Q4的一端相连，第三开关管Q3的一端与第四开关管Q4的一端之间具有第二相线连接点Z2；第一三桥臂包括第五开关管Q5和第六开关管Q6，第五开关管Q5的一端与第六开关管Q6的一端相连，第五开关管Q5的一端与第六开关管Q6的一端之间具有第三相线连接点Z3；第一开关管Q1的另一端、第三开关管Q3的另一端和第五开关管Q5的另一端连接在一起以形成第一三相桥电路的第一端点S11，第二开关管Q2的另一端、第四开关管Q4的另一端和第六开关管Q6的另一端连接在一起以形成第一三相桥电路10的第二端点S12，第一端点S11和第二端点S12可以连接其他模块以输入或输出。
如图5所示，第一三相桥电路10还包括第一电容C1，第一电容C1的一端与第一三相桥电路10的第一端点S11相连，第一电容C1的另一端与第一三相桥电路10的第二端点S12相连，可以对第一三相桥电路10的输出或输入进行滤波。
如图5所示，三路初级LC单元21包括第一初级LC单元、第二初级LC单元和第三初级LC单元。第一初级LC单元包括第二电容C2和第一电感L1，第二电容C2的一端与第一相线连接点Z1相连，第二电容C2的另一端与第一电感L1的一端相连，第一电感L1的另一端与对应相变压单元22的初级线圈的同名端相连；第二初级LC单元包括第三电容C3和第二电感L2，第三电容C3的一端与第二相线连接点Z2相连，第三电容C3的另一端与第二电感L2的一端相连，第二电感L2的另一端与对应相变压单元22的初级线圈的同名端相连；第三初级LC单元包括第四电容C4和第三电感L3相连，第四电容C4的一端与第三相线连接点Z3相连，第四电容C4的另一端与第三电感L3的一端相连，第三电感L3的另一端与对应相变压单元22的初级线圈的同名端相连。
在本公开的实施例中，如图5所示，三相变压单元22包括第一相变压单元T1、第二相变压单元T2和第三相变压单元T3。
其中，第一相变压单元T1包括第一初级线圈和第一次级线圈，第一初级线圈的同名端与第一电感L1的另一端相连，第一次级线圈的同名端与对应次级LC单元23的一端相连；第二相变压单元T2包括第二初级线圈和第二次级线圈，第二初级线圈的同名端与第二电感L2的另一端相连，第二次级线圈的同名端与对应次级LC单元23的一端相连；第三相变压单元T3包括第三初级线圈和第三次级线圈，第三初级线圈的同名端与第三电感L3的另一端相连，第三次级线圈的同名端与对应次级LC单元23的一端相连；第一初级线圈的异名 端、第二初级线圈的异名端和第三初级线圈的异名端连接在一起例如连接于NP，以形成Y型接法，第一次级线圈的异名端、第二次级线圈的异名端和第三次级线圈的异名端连接在一起例如连接于NS，以形成Y型接法。采用Y型接法，可以使得三相桥实现自动均流，避免由于三相桥器件参数偏差带来的功率分布不均。
如图5所示，第二三相桥电路30包括第二一相桥臂、第二二相桥臂和第二三相桥臂。
其中，第二一相桥臂包括第七开关管Q7和第八开关管Q8，第七开关管Q7的一端与第八开关管Q8的一端相连，第七开关管Q7的一端与第八开关管Q8的一端之间具有第四相线连接点Z4；第二二相桥臂包括第九开关管Q9和第十开关管Q10，第九开关管Q9的一端与第十开关管Q10的一端相连，第九开关管Q9的一端与第十开关管Q10的一端之间具有第五相线连接点Z5；第二三相桥臂包括第十一开关管Q11和第十二开关管Q12，第十一开关管Q11的一端与第十二开关管Q12的一端相连，第十一开关管Q11的一端与第十二开关管Q12的一端之间具有第六相线连接点Z6；第七开关管Q7的另一端，第九开关管Q9的另一端和第十一开关管Q11的另一端连接在一起以形成第二三相桥电路30的第一端点S21，第八开关管Q8的另一端、第十开关管Q10的另一端和第十二开关管Q12的另一端连接在一起以形成第二三相桥电路30的第二端点S22。第一端点S21和第二端点S22可以连接其他模块以输入或输出。
如图5所示，第二三相桥电路30还包括第五电容C5，第五电容C5的一端与第二三相桥电路30的第一端点S21相连，第五电容C5的另一端与第二三相桥电路30的第二端点S22相连。第五电容C5可以对第二三相桥电路30的输出或输入进行滤波。
在本公开的一些实施例中，如图5所示，三路次级LC单元23包括第一次级LC单元、第二次级LC单元和第三次级LC单元。
其中，第一次级LC单元包括第四电感L4和第六电容C6，第四电感L4的一端与第一次级线圈的同名端相连，第四电感L4的另一端与第六电容C6的一端相连，第六电容C6的另一端与第四相线连接点Z4相连；第二次级LC单元包括第五电感L5和第七电容C7，第五电感L5的一端与第二次级线圈的同名端相连，第五电感L5的另一端与第七电容C7的一端相连，第七电容C7的另一端与第五相线连接点Z5相连；第三次级LC单元包括第六电感L6和第八电容C8，第六电感L6的一端与第三次线圈的同名端相连，第六电感L6的另一端与第八电容C8的一端相连，第八电容C8的另一端与第六相线连接点Z6相连。
在一些实施例中，第一三相桥电路10连接充电输入，第二三相桥电路30连接电动车辆的电池模块，对于正向充电来说，第二电容C2、第一电感L1和第一初级线圈构成第一一相桥臂的谐振腔，第三电容C3、第二电感L2和第二初级线圈构成第一二相桥臂的谐振腔，第四电容C4、第三电感L3和第三初级线圈构成第一三相桥臂的谐振腔。其中，在一 些实施例中，第二电容C2、第三电容C3和第四电容C4被称为初级谐振电容，第一电感L1、第二电感L2和第三电感L3被称为初级谐振电感。
在外界对电池模块充电时，第一三相桥臂电路10的每一相桥臂及其对应的谐振模块组成三相交错LLC并工作于高频谐振状态，控制器40控制第一开关管Q1与第二开关管Q2、第三开关管Q3与第四开光管Q4、第五开关管Q5与第六开关管Q6分别以50％占空比交替开关，控制第一开关管Q1、第三开关管Q3和第五开关管Q5之间相位分别相差120°开关，控制第二开关管Q2、第四开关管Q4和第六开关管Q6之间相位分别相差120°开关，以及对第二三相桥电路30进行整流控制，第二三相桥电路30作为次级三相整流桥，高频电流通过第二三相桥电路30的开关管体中二极管整流之后转换为直流电并提供给整车的高压电池模块，其中，通常地如图5中所示，每个开关管中包括二极管元件，可以称之为开关管体二极管。如果将驱动信号给到第二三相桥电路30的开关管，第二三相桥电路30将形成同步整流电路，进一步提高产品效率。
在一些实施例中，第一三相桥电路10连接用电侧，第二三相桥电路30连接电动车辆的电池模块，对于反向放电来说，第六电容C6、第四电感L4和第一次级线圈构成第二一相桥臂的谐振腔，第七电容C7、第五电感L5和第二次级线圈构成第二二相桥臂的谐振腔，第八电容C8、第六电感L6和第三次级线圈构成第二三相桥臂的谐振腔。其中，在一些实施例中，第六电容C6、第七电容C7和第八电容C8被称为次级谐振电容，第四电感L4、第五电感L5和第六电感L6被称为次级谐振电感。
在电池模块对外界放电时，第二三相桥臂电路30的每一相桥臂及其对应的谐振模块组成三相交错LLC并工作于高频谐振状态，控制器40控制第七开关管Q7与第八开关管Q8、第九开关管Q9与第十开关管Q10、第十一开关管Q11与第十二开关管Q12分别以50％占空比交替开关，控制第七开关管Q7、第九开关管Q9和第十一开关管Q11之间相位分别相差120°开关，控制第八开关管Q8、第十开关管Q10和第十二开关管Q12之间相位分别相差120°开关，以及对第一三相桥电路10进行整流控制，第一三相桥电路30作为放电输出三相整流桥，高频电流通过第一三相桥电路30的开关管体中二极管整流之后转换为直流电并提供给用电输出侧的模块，如果将驱动信号给到第一三相桥电路10的开关管，第一三相桥电路10将形成同步整流电路，进一步提高产品效率。
如图6所示为根据本公开的一个实施例的DCDC变换器的框图，本公开实施例的电流检测电路50包括第一采集单元51、第二采集单元52、第三采集单元53、第四采集单元54、第五采集单元55和第六采集单元56。其中，第一采集单元51用于采集第一电感L1的电流信号；第二采集单元52用于采集L2第二电感的电流信号；第三采集单元53用于采集第三电感L3的电流信号；第四采集单元54用于采集第四电感L4的电流信号；第五采集单元 55用于采集第五电感L5的电流信号；第六采集单元56用于采集第六电感L6的电流信号。通过分别对谐振模块20的电感进行电流检测，可以更加有效地监测谐振腔电流，进而可以调节三相桥电路的功率，以使得三相桥的功率更加平衡。
本公开实施例的电流检测电路50还包括N个转换单元，第N转换单元与第N采集单元相连，第N转换单元用于对第N采集单元采集的电流信号进行转换，其中，N＝1,2,3……6。例如，如图6所示，包括第一转换单元57、第二转换单元58、第三转换单元59、第四转换单元510、第五转换单元511和第六转换单元512。其中，第一转换单元57用于对第一电感L1的电流信号进行转换；第二转换单元58用于对第二电感L2的电流信号进行转换；第三转换单元59用于对第三电感L3的电流信号进行转换；第四转换单元510用于对第四电感L4的电流信号进行转换；第五转换单元511用于对第五电感L5的电流信号进行转换；第六转换单元512用于对第六电感L6的电流信号进行转换。以便于将每一路的电流信号转换为控制器40可以识别和处理的信号。
在一些实施例中，第一采集单元51、第二采集单元52、第三采集单元53、第四采集单元54、第五采集单元55和第六采集单元56分别为自耦电感或电流互感器。其中，自耦电感与各路的谐振电感进行感应，产生出高频交流电流信号，实现对各路谐振电感的电流信号的检测。自耦电感为谐振电感的辅助自耦线圈，采用自耦电感无需额外增加电流检测器件，并且相关的其他电阻、电容和运放均为普通元器件，对系统成本几乎没有影响。电流互感器可以为独立外置的器件，根据电流互感器的检测原理，其主侧线圈与谐振电感串联连接在电路中，通过其次侧线圈与主侧线圈的互感实现对谐振电感的电流信号的检测。
在本公开的一些实施例中，参照图5所示，图中只示出了一路转换单元，其他转换单元相同。在实施例中，第N转换单元包括第N整流电路501、第N电压转换电路502和第N电压跟随器电路503。其中，第N整流电路501用于将第N采集单元采集的电流信号进行整流，得到整流信号；第N电压转换电路502用于将整流信号转换为电压信号；第N电压跟随器电路503路用于将电压信号转换为AD信号，控制器40用于在AD信号大于预设AD值时对第一三相桥电路10和第二三相桥电路30的开关管进行控制，在AD值超标时，控制输出功率降低，减小系统工作电流以避免该相负载过大。
在外界对电池模块充电时，如果发生过流，则控制器40控制第一一相桥臂的开关管、第一二相桥臂的开关管和第一三相桥臂的开光管的占空比减小以降低输出功率；或者，在电池模块对外界放电时，如果发生过流，则控制第二相桥臂的开关管、第二二相桥臂的开关管和第二三相桥臂的开关管的占空比减小以降低输出功率。通过降低输出功率，减小系统工作电流以避免负载过大，避免因谐振腔有较大冲击电流而影响产品寿命甚至提前损坏。
参照图5所示，第N整流电路501包括第一二极管D1、第二二极管D2、第三二极管 D3和第四二极管D4，第一二极管D1的一端与第二二极管D2的一端相连，第一二极管D1的一端与第二二极管D2的一端之间具有第一输入节点，第一输入节点与对应采集单元的第一输出端相连，例如图中采集单元输出信号sense1，第三二极管D2的一端与第四二极管D4的一端相连，第三二极管D3的一端与第四二极管D4的一端之间具有第二输入节点，第二输入节点与对应采集单元的第二输出端相连，例如图中采集单元输出信号sense2,第一二极管D1的另一端与第三二极管D3的另一端连接在一起以形成第一整流输出端，第二二极管D2的另一端与第四二极管D4的另一端连接在一起并与接地端相连；第N电压转换电路502包括第一电阻R1，第一电阻R1的一端与第一整流输出端相连，例如输出信号Vsense，第一电阻R1的另一端与接地端相连；第N电压跟随器电路503包括第二电阻R2、电压跟随器U1B、第三电阻R3和第九电容C9，第二电阻R2的一端与第一电阻R1的一端相连，电压跟随器U1B的正向输入端与第二电阻R2的另一端相连，电压跟随器U1B的输出端与第三电阻R3的一端相连，电压跟随器U1B的输出端与电压跟随器U1B的负向输入端相连，第三电阻R3的另一端与控制器40相连，例如输出AD信号Isense至控制器40，第九电容C9的一端连接于第三电阻R3与控制器40之间，第九电容C9的另一端连接接地端，控制器40根据该AD信号来对系统功率进行调配。当然电路也可以根据需要适应性地变形，例如增加电容以进行滤波处理，或者采用并联或串联电阻来进行电压转换或采集等，图5给出的仅仅是示例电路。
以第一初级LC单元为例，第一电感L1的自耦电感51感应出的高频交流信号传送该整流电路以及第一电阻R1之后，转换为高频半波电压信号Vsense，该电压信号Vsense经过电压跟随器U1B后成为AD信号Isense，并传输中控制器40，如果控制器40发现AD信号超标，则控制输出功率降低，减小系统工作电流避免该相负载过大，造成损坏。
在本公开的一些实施例中，如图5所示，其中只示出了一路转换单元，在实施例中，第N转换单元还包括第N比较电路504，即言每个转换单元分别包括各自的比较电路，第N比较电路504用于在电流信号超过跳变阈值时输出停止信号至控制器40，控制器40在检测到停止信号时关断对第一三相桥电路10和第二三相桥电路30的开关管的驱动，以避免变换器出现损坏，保证寿命。
参照图5所示，第N比较电路504包括第四电阻R4、第五电阻R5和第十电容C10，比较器U1A、第十一电容C11和第十二电容C12。其中，第四电阻R4的一端与第一电阻R1的一端相连，例如电压转换电路502输出的电压信号Vsense输入至比较电路504，第四电阻R4的另一端与第五电阻R5的一端相连，第十电容C10的一端连接在第四电阻R4的另一端与第五电阻R5的一端之间；比较器U1A的第一输入端与第五电阻R5的另一端相连，比较器U1A的第二输入端通过第六电阻R6与基准电压输入端相连，比较器U1A的第三端与接地 端相连，比较器U1A的第四端与预设电源相连，比较器U1A的输出端通过第七电阻R7与控制器40相连，例如输出保护信号Iprotect至控制器40；第十一电容C11的一端分别与比较器U1A的第四端和预设电源相连，第十一电容C11的另一端与接地端相连，第十二电容C12的一端连接于第七电阻R7和控制器40之间，第十二电容C12的另一端与接地端相连。
以第一初级LC单元为例，电压信号Vsense传输至比较电路504，经过比较器U1A之后输出一个硬件高低电平信号，当U1A输出高电平时，表示该相谐振腔电流已经严重超标，控制器40检测到高电平信号之后立即关断开关管驱动，系统停止工作，避免变换器出现损坏。
概括来说，相较于通过输出电流采样推算谐振腔电流，本公开实施例的DCDC变换器通过谐振电感的辅助自耦电感形成电流互感器或者设置独立外置的电流互感器，直接采集谐振腔的电流信号，根据电流信号进行控制以及保护。
下面以20KW三相交错LLC双向DCDC变换器为例进行说明。如图7所示，其中，各路采集单元为谐振电感的自耦电感，设计需求为：DCDC变换器的输入电压和输出电压额定值均为750V，充电方向和放电方向满载功率均为20KW。对于谐振腔参数设定：因为正向充电电压、功率相等，因此，对应第一三相桥电路10的谐振腔例如称为初级谐振腔与对应第二三相桥电路30的谐振腔例如称为次级谐振腔的参数一致，假设电路谐振频率为150KHZ，根据三相交错LLC电路的相关计算公式可以得到：初级谐振电容C2＝C3＝C4＝次级谐振电容C5＝C6＝C7＝80nF，初级谐振电感L1＝L2＝L3＝次级谐振电感L4＝L5＝L6＝14μH，自耦电感与谐振电感匝比为100:1，三相变压单元22匝比T1＝T2＝T3＝1：1，三相变压单元22的初级线圈的感量T 1-1＝T 2-1＝T 3-1＝次级线圈的感量＝T 1-2＝T 2-2＝T 3-2＝70μH，根据对电流、电压需求以及散热要求等的考虑，开关管Q1-Q12选用1200V/40mΩ碳化硅MOS(metal oxide semiconductor，金属-氧化物-半导体)管，具体地如图7所示。
以第一初级LC单元为例，其他谐振电感采用相同原理电路类推。设流经第一电感L1的电流为Ir，则谐振电感的自耦电感的感应限流为Ir/100，经过电阻R1之后峰值电平Vsense(peak)＝1.414*Ir/10。Vsense经过电压跟随器U1B以及RC滤波后输出AD信号Isense至控制器40；Vref为硬件保护基准电压，假设Ir峰值电流大于30A时触发保护，则Vref＝3V。
图8是根据本公开的另一个实施例的20KW三相交错LLC双向DCDC变换器的电路图，如图8所示，其中，各路采集单元为独立外设的电流互感器，设计需求为：DCDC变换器的输入电压和输出电压额定值均为750V，充电方向和放电方向满载功率均为20KW。对于谐振腔参数设定：因为正向充电电压、功率相等，因此，对应第一三相桥电路10的谐振腔例如称为初级谐振腔与对应第二三相桥电路30的谐振腔例如称为次级谐振腔的参数一致，假设电路谐振频率为150KHZ，根据三相交错LLC电路的相关计算公式可以得到：初级谐振电容 C2＝C3＝C4＝次级谐振电容C5＝C6＝C7＝80nF，初级谐振电感L1＝L2＝L3＝次级谐振电感L4＝L5＝L6＝14μH，自耦电感与谐振电感匝比为100:1，三相变压单元22匝比T1＝T2＝T3＝1：1，三相变压单元22的初级线圈的感量T 1-1＝T 2-1＝T 3-1＝次级线圈的感量＝T 1-2＝T 2-2＝T 3-2＝70μH，根据对电流、电压需求以及散热要求等的考虑，开关管Q1-Q12选用1200V/40mΩ碳化硅MOS管，具体地如图8所示。
仍然以第一初级LC单元为例，其他谐振电感采用相同原理电路类推。设流经第一电感L1的电流为Ir，则谐振电感的自耦电感的感应限流为Ir/100，经过电阻R1之后峰值电平Vsense(peak)＝1.414*Ir/10。Vsense经过电压跟随器U1B以及RC滤波后输出AD信号Isense至控制器40；Vref为硬件保护基准电压，假设Ir峰值电流大于30A时触发保护，则Vref＝3V。
本公开实施例的DCDC变换器100，与普通三相全桥DCDC变换器相比，在变压次级侧增加三路谐振单元，第二三相桥电路30采用可控开关管。其中，双向谐振，可以实现能量双向传输，且双向传输均工作于软开关模式；构成三相交错LLC，可以实现更大功率转换，相较于普通三相交错LLC，可以节省功率开关管，并且，三相变压单元22采用Y型接法，可以实现三相桥电路的自动均流，避免功率分布不均，以及基于本公开实施例的DCDC变换器100的电路结构，输出纹波电流更小，更小的纹波电流可以节省输出滤波电容，更加有利于降低成本和减小产品体积。
以及，本公开实施例的DCDC变换器100，每一路的谐振电感增加一路自耦电感，此时，谐振电感既起到了交错谐振的作用，同时也与自耦电感构成电流互感器，以实现对谐振电感的电流信号的检测，无需额外增加电流检测器件，成本低；或者，通过在每一路的谐振电感增加独立的电流互感器，来实现对谐振电感的电流信号的检测。直接采集谐振电感的电流信号，精度高，响应更加快速，并且采用软硬件两重保护，可靠性高，谐振腔的电流信号经过处理后传输给控制器40的AD采样口，控制器40根据AD值对系统功率进行调配，同时，当谐振腔电流严重过流时，谐振腔电流限号触发硬件快速比较器后直接输出过流锁保护信号，控制器40检测到该信号后直接关断对三相桥开关管的驱动，避免系统损坏，通过软硬件两重保护，使得过流保护功能既快又稳。
基于上述方面实施例的DCDC变换器，下面参照附图描述根据本公开实施例的车载充电机。
图9是根据本公开实施例的车载充电机的框图，如图9所示，本公开实施例的车载充电机1000包括三相PFC电路200和上面实施例的DCDC变换器100，三相PFC电路200起到功率因数校正的作用，DCDC变换器100实现能量的可控隔离传输，DCDC变换器100的具体结构和工作过程参照上面实施例说明。
根据本公开实施例的车载充电机1000，通过采用上述方面实施例的DCDC变换器100， 可以实现大功率充放电，输出纹波电流小，过流保护功能响应快速且可靠。
图10是根据本公开实施例的电动车辆的框图，如图10所示，本公开实施例的电动车辆10000包括上述方面实施例的车载充电机1000。
根据本公开实施例的电动车辆10000，通过安装上述方面实施例的车载充电机1000，可以实现大功率充放电，输出纹波电流小，过流保护功能响应快速且可靠。
在本说明书的描述中，参考术语“一个实施例”、“一些实施例”、“示例”、“具体示例”、或“一些示例”等的描述意指结合该实施例或示例描述的具体特征、结构、材料或者特点包含于本公开的至少一个实施例或示例中。在本说明书中，对上述术语的示意性表述不必须针对的是相同的实施例或示例。而且，描述的具体特征、结构、材料或者特点可以在任一个或多个实施例或示例中以合适的方式结合。此外，在不相互矛盾的情况下，本领域的技术人员可以将本说明书中描述的不同实施例或示例以及不同实施例或示例的特征进行结合和组合。
尽管上面已经示出和描述了本公开的实施例，可以理解的是，上述实施例是示例性的，不能理解为对本公开的限制，本领域的普通技术人员在本公开的范围内可以对上述实施例进行变化、修改、替换和变型。

Claims (21)

  1. 一种DCDC变换器，其特征在于，包括第一调整模块、谐振模块、第二调整模块、电流检测模块和控制器，其中，
    所述第一调整模块，用于在外界对车辆的电池模块充电时对DCDC变换器的输入信号的频率进行调节，或者，用于在所述电池模块对外界放电时对所述谐振模块的输出信号进行整流；
    所述谐振模块，用于在外界对车辆的电池模块进行充电时对所述第一调整模块的输出信号进行谐振，或者，用于在所述电池模块对外界放电时对所述第二调整模块的输出信号进行谐振；
    所述第二调整模块，用于在车辆的电池模块对外界放电时对所述电池模块的输出信号的频率进行调节，或者，用于在外界对所述电池模块充电时对所述谐振模块的输出信号进行整流；
    电流检测模块，所述电流检测模块用于检测所述谐振模块的电流信号；
    控制器，所述控制器分别与所述第一调整模块的控制端和所述第二调整模块的控制端相连，用于在所述电流信号大于电流阈值时对所述第一调整模块和所述第二调整模块进行控制以降低输出功率。
  2. 如权利要求1所述的DCDC变换器，其特征在于，所述谐振模块包括N路初级LC单元、N相变压单元和N路次级LC单元，其中，N为大于1的正整数。
  3. 如权利要求1或2所述的DCDC变换器，其特征在于，所述谐振模块包括三路初级LC单元、三相变压单元和三路次级LC单元，其中，
    在所述DCDC变换器对所述电池模块充电时，所述三路初级LC单元和所述三相变压单元用于对所述第一调整模块的输出信号进行谐振以产生高频电流；
    在所述DCDC变换器对所述电池模块放电时，所述三路次级LC单元和所述三相变压单元用于对所述第二调整模块的输出信号进行谐振以产生高频电流。
  4. 如权利要求3所述的DCDC变换器，其特征在于，所述第一调整模块包括第一三相桥电路，所述第二调整模块包括第二三相桥电路，其中，
    每一路初级LC单元的一端与所述第一三相桥电路中对应相桥臂的相线连接点相连，所述三相变压单元的初级线圈的同名端分别与对应初级LC单元的另一端相连，所述三相变压单元的初级线圈的异名端连接在一起，所述三相变压单元的次级线圈的同名端分别与对应次级LC单元的一端相连，所述三相变压单元的次级线圈的异名端连接在一起；
    所述第二三相桥电路的每一相桥臂的相线连接点与对应次级LC单元的另一端相连；
    所述控制器分别与所述第一三相桥电路的开关管的控制端和所述第二三相桥电路的开关管的控制端相连。
  5. 如权利要求4所述的DCDC变换器，其特征在于，所述第一三相桥电路包括：
    第一一相桥臂，所述第一一相桥臂电路包括第一开关管和第二开关管，所述第一开关管的一端与所述第二开关管的一端相连，所述第一开关管的一端与所述第二开关管的一端之间具有第一相线连接点；
    第一二相桥臂，所述第一二相桥臂包括第三开关管和第四开关管，所述第三开关管的一端与所述第四开关管的一端相连，所述第三开关管的一端与所述第四开关管的一端之间具有第二相线连接点；
    第一三相桥臂，所述第一三桥臂包括第五开关管和第六开关管，所述第五开关管的一端与所述第六开关管的一端相连，所述第五开关管的一端与所述第六开关管的一端之间具有第三相线连接点；
    所述第一开关管的另一端、所述第三开关管的另一端和所述第五开关管的另一端连接在一起以形成所述第一三相桥电路的第一端点，所述第二开关管的另一端、所述第四开关管的另一端和所述第六开关管的另一端连接在一起以形成所述第一三相桥电路的第二端点。
  6. 如权利要求5所述的DCDC变换器，其特征在于，所述第一三相桥电路还包括：
    第一电容，所述第一电容的一端与所述第一三相桥电路的第一端点相连，所述第一电容的另一端与所述第一三相桥电路的第二端点相连。
  7. 如权利要求5或6所述的DCDC变换器，其特征在于，所述三路初级LC单元包括：
    第一初级LC单元，所述第一初级LC单元包括第二电容和第一电感，所述第二电容的一端与所述第一相线连接点相连，所述第二电容的另一端与所述第一电感的一端相连，所述第一电感的另一端与对应相变压单元的初级线圈的同名端相连；
    第二初级LC单元，所述第二初级LC单元包括第三电容和第二电感，所述第三电容的一端与所述第二相线连接点相连，所述第三电容的另一端与所述第二电感的一端相连，所述第二电感的另一端与对应相变压单元的初级线圈的同名端相连；
    第三初级LC单元，所述第三初级LC单元包括第四电容和第三电感相连，所述第四电容的一端与所述第三相线连接点相连，所述第四电容的另一端与所述第三电感的一端相连，所述第三电感的另一端与对应相变压单元的初级线圈的同名端相连。
  8. 如权利要求7所述的DCDC变换器，其特征在于，所述三相变压单元包括：
    第一相变压单元，所述第一相变压单元包括第一初级线圈和第一次级线圈，所述第一初级线圈的同名端与所述第一电感的另一端相连，所述第一次级线圈的同名端与对应次级 LC单元的一端相连；
    第二相变压单元，所述第二相变压单元包括第二初级线圈和第二次级线圈，所述第二初级线圈的同名端与所述第二电感的另一端相连，所述第二次级线圈的同名端与对应次级LC单元的一端相连；
    第三相变压单元，所述第三相变压单元包括第三初级线圈和第三次级线圈，所述第三初级线圈的同名端与所述第三电感的另一端相连，所述第三次级线圈的同名端与对应次级LC单元的一端相连；
    所述第一初级线圈的异名端、所述第二初级线圈的异名端和所述第三初级线圈的异名端连接在一起，所述第一次级线圈的异名端、所述第二次级线圈的异名端和所述第三次级线圈的异名端连接在一起。
  9. 如权利要求8所述的DCDC变换器，其特征在于，所述第二三相桥电路包括：
    第二一相桥臂，所述第二一相桥臂包括第七开关管和第八开关管，所述第七开关管的一端与所述第八开关管的一端相连，所述第七开关管的一端与所述第八开关管的一端之间具有第四相线连接点；
    第二二相桥臂，所述第二二相桥臂包括第九开关管和第十开关管，所述第九开关管的一端与所述第十开关管的一端相连，所述第九开关管的一端与所述第十开关管的一端之间具有第五相线连接点；
    第二三相桥臂，所述第二三相桥臂包括第十一开关管和第十二开关管，所述第十一开关管的一端与所述第十二开关管的一端相连，所述第十一开关管的一端与所述第十二开关管的一端之间具有第六相线连接点；
    所述第七开关管的另一端，所述第九开关管的另一端和所述第十一开关管的另一端连接在一起以形成所述第二三相桥电路的第一端点，所述第八开关管的另一端、所述第十开关管的另一端和所述第十二开关管的另一端连接在一起以形成所述第二三相桥电路的第二端点。
  10. 如权利要求9所述的DCDC变换器，其特征在于，所述第二三相桥电路还包括：
    第五电容，所述第五电容的一端与所述第二三相桥电路的第一端点相连，所述第五电容的另一端与所述第二三相桥电路的第二端点相连。
  11. 如权利要求9或10所述的DCDC变换器，其特征在于，所述三路次级LC单元包括：
    第一次级LC单元，所述第一次级LC单元包括第四电感和第六电容，所述第四电感的一端与所述第一次级线圈的同名端相连，所述第四电感的另一端与所述第六电容的一端相连，所述第六电容的另一端与所述第四相线连接点相连；
    第二次级LC单元，所述第二次级LC单元包括第五电感和第七电容，所述第五电感的 一端与所述第二次级线圈的同名端相连，所述第五电感的另一端与所述第七电容的一端相连，所述第七电容的另一端与所述第五相线连接点相连；
    第三次级LC单元，所述第三次级LC单元包括第六电感和第八电容，所述第六电感的一端与所述第三次线圈的同名端相连，所述第六电感的另一端与所述第八电容的一端相连，所述第八电容的另一端与所述第六相线连接点相连。
  12. 如权利要求11所述的DCDC变换器，其特征在于，所述电流检测模块包括：
    第一采集单元，所述第一采集单元用于采集所述第一电感的电流信号；
    第二采集单元，所述第二采集单元用于采集所述第二电感的电流信号；
    第三采集单元，所述第三采集单元用于采集所述第三电感的电流信号；
    第四采集单元，所述第四采集单元用于采集所述第四电感的电流信号；
    第五采集单元，所述第五采集单元用于采集所述第五电感的电流信号；
    第六采集单元，所述第六采集单元用于采集所述第六电感的电流信号。
  13. 如权利要求11或12所述的DCDC变换器，其特征在于，所述第一采集单元、所述第二采集单元、所述第三采集单元、所述第四采集单元、所述第五采集单元和所述第六采集单元分别为自耦电感或电流互感器。
  14. 如权利要求12或13所述的DCDC变换器，其特征在于，所述电流检测模块还包括：
    N个转换单元，在所述N个转换单元中，第N转换单元与第N采集单元相连，所述第N转换单元用于对所述第N采集单元采集的电流信号进行转换，其中，N＝1,2,3……6。
  15. 如权利要求14所述的DCDC变换器，其特征在于，所述第N转换单元包括：
    第N整流电路，所述第N整流电路用于将第N采集单元采集的电流信号进行整流，得到整流信号；
    第N电压转换电路，所述第N电压转换电路用于将所述整流信号转换为电压信号；
    第N电压跟随器电路，所述第N电压跟随器电路用于将所述电压信号转换为AD信号；
    所述控制器用于在所述AD信号大于预设AD值时对所述第一三相桥电路和所述第二三相桥电路的开关管进行控制以降低输出功率。
  16. 如权利要求15所述的DCDC变换器，其特征在于，
    所述第N整流电路包括第一二极管、第二二极管、第三二极管和第四二极管，所述第一二极管的一端与所述第二二极管的一端相连，所述第一二极管的一端与所述第二二极管的一端之间具有第一输入节点，所述第一输入节点与对应采集单元的第一输出端相连，所述第三二极管的一端与所述第四二极管的一端相连，所述第三二极管的一端与所述第四二极管的一端之间具有第二输入节点，所述第二输入节点与对应采集单元的第二输出端相连，所述第一二极管的另一端与所述第三二极管的另一端连接在一起以形成第一整流输出端， 所述第二二极管的另一端与所述第四二极管的另一端连接在一起并与接地端相连；
    所述第N电压转换电路包括第一电阻，所述第一电阻的一端与所述第一整流输出端相连，所述第一电阻的另一端与所述接地端相连；
    所述第N电压跟随器电路包括第二电阻、电压跟随器、第三电阻和第九电容，所述第二电阻的一端与所述第一电阻的一端相连，所述电压跟随器的正向输入端与所述第二电阻的另一端相连，所述电压跟随器的输出端与所述第三电阻的一端相连，所述电压跟随器的输出端与所述电压跟随器的负向输入端相连，所述第三电阻的另一端与所述控制器相连，所述第九电容的一端连接于所述第三电阻与所述控制器之间，所述第九电容的另一端连接接地端。
  17. 如权利要求16所述的DCDC变换器，其特征在于，所述第N转换单元还包括：
    第N比较电路，所述第N比较电路用于在所述电流信号超过跳变阈值时输出停止信号至所述控制器，所述控制器在检测到所述停止信号时关断对所述第一三相桥电路和所述第二三相桥电路的开关管的驱动。
  18. 如权利要求17所述的DCDC变换器，其特征在于，所述第N比较电路包括：
    第四电阻、第五电阻和第十电容，所述第四电阻的一端与所述第一电阻的一端相连，所述第四电阻的另一端与所述第五电阻的一端相连，所述第十电容的一端连接在所述第四电阻的另一端与所述第五电阻的一端之间，所述第十电容的另一端连接接地端；
    比较器，所述比较器的第一输入端与所述第五电阻的另一端相连，所述比较器的第二输入端通过第六电阻与基准电压输入端相连，所述比较器的第三端与所述接地端相连，所述比较器的第四端与预设电源相连，所述比较器的输出端通过第七电阻与所述控制器相连；
    第十一电容和第十二电容，所述第十一电容的一端分别与所述比较器的第四端和所述预设电源相连，所述第十一电容的另一端与所述接地端相连，所述第十二电容的一端连接于所述第七电阻和所述控制器之间，所述第十二电容的另一端与所述接地端相连。
  19. 如权利要求15-18中任一项所述的DCDC变换器，其特征在于，所述控制器在AD信号大于预设AD值时对所述第一三相桥电路和所述第二三相桥电路的开关管进行控制用于，
    在外界对所述电池模块充电时，控制所述第一一相桥臂的开关管、所述第一二相桥臂的开关管和所述第一三相桥臂的开关管的占空比减小以降低输出功率；
    或者，在所述电池模块对外界放电时，控制所述第二相桥臂的开关管、所述第二二相桥臂的开关管和所述第二三相桥臂的开关管的占空比减小以降低输出功率。
  20. 一种车载充电机，其特征在于，包括三相PFC电路和如权利要求1-19任一项所述的DCDC变换器。
  21. 一种电动车辆，其特征在于，包括如权利要求20所述的车载充电机。
PCT/CN2019/084328 2018-04-26 2019-04-25 Dcdc变换器、车载充电机和电动车辆 Ceased WO2019206230A1 (zh)

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