WO2021082220A1 - 一种三相并网逆变器的控制方法、系统及三相并网逆变器 - Google Patents

一种三相并网逆变器的控制方法、系统及三相并网逆变器 Download PDF

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Publication number
WO2021082220A1
WO2021082220A1 PCT/CN2019/126250 CN2019126250W WO2021082220A1 WO 2021082220 A1 WO2021082220 A1 WO 2021082220A1 CN 2019126250 W CN2019126250 W CN 2019126250W WO 2021082220 A1 WO2021082220 A1 WO 2021082220A1
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Prior art keywords
target
inductor
current
inductor current
turn
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PCT/CN2019/126250
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English (en)
French (fr)
Inventor
祁飚杰
吴坚
杨永春
罗宇浩
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Altenergy Power System Inc
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Altenergy Power System Inc
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Priority to BR112022004122-5A priority Critical patent/BR112022004122B1/pt
Priority to MX2022002799A priority patent/MX2022002799A/es
Priority to EP19950673.4A priority patent/EP4054070A4/en
Priority to US17/432,935 priority patent/US11770065B2/en
Publication of WO2021082220A1 publication Critical patent/WO2021082220A1/zh
Anticipated expiration legal-status Critical
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/01—Arrangements for reducing harmonics or ripples
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/38—Arrangements for feeding a single network from two or more generators or sources in parallel; Arrangements for feeding already energised networks from additional generators or sources in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0043—Converters switched with a phase shift, i.e. interleaved
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H02M1/126—Arrangements for reducing harmonics from AC input or output using passive filters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current

Definitions

  • the invention relates to the field of solar photovoltaic grid-connected systems, in particular to a control method and system of a three-phase grid-connected inverter, and a three-phase grid-connected inverter.
  • the three-phase three-leg grid-connected inverter is the more commonly used inverter.
  • FIG. 1 is a schematic structural diagram of a three-phase three-leg grid-connected inverter in the prior art. It can be seen from Figure 1 that the three-phase three-leg grid-connected inverter does not form a filter loop, so that the harmonics cannot be filtered out, which makes the quality of the grid-connected current waveform poor at low power.
  • the method of increasing the inductance value of the inductors L1, L2, L3 is usually adopted, but the larger the inductance value, the inverse of the parallel connection in the system Inverter equipment is more prone to resonance and cannot be applied to photovoltaic micro-inverters.
  • the existing three-phase three-leg grid-connected inverter usually works in the inductor current continuous mode, that is, the current of the inductors L1, L2, and L3 does not drop to zero during a switching period, resulting in three-phase three-leg paralleling. The switching loss of the grid inverter is relatively large.
  • the purpose of the present invention is to provide a control method and system for a three-phase grid-connected inverter, and a three-phase grid-connected inverter, which can filter out the harmonics in the circuit and realize high-quality grid-connected current at low power. That is, there is no need to increase the inductance value, so that the parallel inverter equipment in the system can achieve stable operation, which is more suitable for photovoltaic micro-inverters.
  • the three-phase three-leg grid-connected inverter of the present application works in the inductor current discontinuous mode, thereby reducing the switching loss of the three-phase three-leg grid-connected inverter.
  • the present invention provides a three-phase grid-connected inverter control method, which is applied to a three-phase three-phase three-phase three-phase three-phase three-phase three-phase three-phase three-phase three-phase grid-connected inverter.
  • the control method includes:
  • the two inductor currents in the same direction are controlled in the inductor current discontinuous mode, so that the fundamental components of the two inductor currents in the same direction are sinusoidal in the power grid cycle. wave.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle to realize the interleaving of the two inductor currents in the same direction in the inductor current discontinuous mode. control.
  • control method further includes:
  • the target inductor peak current is multiplied by a positive coefficient ⁇ , and the product result is used as the target inductor peak current corresponding to the target inductor current.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • T is one For the entire switching period in the interval, D is the turn-on time ratio of the entire switching period, I is the amplitude of the inductor current, ⁇ is the angular frequency of the inductor current, t is the time, L is the inductance, U dc is the DC side voltage, U ac Is the AC side line voltage;
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle to realize the interleaving of the two inductor currents in the same direction in the inductor current discontinuous mode. control.
  • the control method further includes:
  • the target turn-on time ratio is multiplied by a positive coefficient ⁇ , and the product result is used as the target turn-on time ratio corresponding to the target inductor current in the entire switching period.
  • it also includes:
  • the phases of the two inductive currents in the same direction are shifted, so that there is a phase difference between the inductive current and the grid voltage during the power grid cycle.
  • the present invention also provides a three-phase grid-connected inverter control system, which is applied to a three-phase filter capacitor with one end connected to the output inductor of the corresponding bridge arm and the other end connected to the negative electrode of the DC input bus.
  • the control system includes:
  • the period division module is used to divide a power grid period into a plurality of equal intervals in advance; wherein the inductance current corresponding to each interval is two inductance currents in the same direction, and the third inductance current is in reverse;
  • the interleaved control module is used to control two inductive currents in the same direction in the inductive current discontinuous mode in any interval of each power grid cycle, so as to meet the requirements of the two inductive currents in the same direction during the power grid cycle.
  • the fundamental components are all sine waves.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle to realize the interleaving of the two inductor currents in the same direction in the inductor current discontinuous mode. control.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • T is one For the entire switching period in the interval, D is the turn-on time ratio of the entire switching period, I is the amplitude of the inductor current, ⁇ is the angular frequency of the inductor current, t is the time, L is the inductance, U dc is the DC side voltage, U ac Is the AC side line voltage;
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle to realize the interleaving of the two inductor currents in the same direction in the inductor current discontinuous mode. control.
  • the present invention also provides a three-phase grid-connected inverter, which includes six switch tubes, three output inductors and three filter capacitors; among them:
  • the first end of the first switch tube, the third switch tube, and the fifth switch tube are all connected to the positive pole of the DC input bus, and the second end of the second switch tube, the fourth switch tube, and the sixth switch tube are all connected to the DC input bus.
  • Negative; the second terminal of the first switch tube is connected to the first terminal of the second switch tube and the common terminal is connected to the first terminal of the first output inductor.
  • the second terminal of the third switch tube is connected to the first terminal of the fourth switch tube.
  • the common terminal is connected with the first terminal of the second output inductor, the second terminal of the fifth switch tube is connected with the first terminal of the sixth switch tube, and the common terminal is connected with the first terminal of the third output inductor;
  • the second end of the output inductor is connected to the first end of the first filter capacitor and the common end is connected to the phase A line of the power grid, the second end of the second output inductor is connected to the first end of the second filter capacitor and the common end is connected to the phase B of the power grid
  • the second end of the third output inductor is connected to the first end of the third filter capacitor and the common end is connected to the phase C line of the power grid; the second ends of the first filter capacitor, the second filter capacitor and the third filter capacitor are connected to the DC input The negative pole of the busbar;
  • control method of the three-phase grid-connected inverter adopts any of the above-mentioned control methods of the three-phase grid-connected inverter.
  • the invention provides a control method of a three-phase grid-connected inverter, which is applied to a three-phase three-leg grid-connected inverter.
  • This application improves the structure of the three-phase three-leg grid-connected inverter, and connects the filter capacitor to the negative electrode of the DC input bus to form a filter loop, so as to filter out the harmonics in the circuit, and achieve high quality under low power Grid-connected current, that is, there is no need to increase the inductance value, so that the parallel inverter equipment in the system can achieve stable operation, which is more suitable for photovoltaic micro-inverters.
  • the three-phase three-leg grid-connected inverter of the present application works in the inductor current discontinuous mode, that is, the inductor current drops to zero in one switching period, thereby reducing the cost of the three-phase three-leg grid-connected inverter. Switching loss.
  • the invention also provides a control system of the three-phase grid-connected inverter and the three-phase grid-connected inverter, which have the same beneficial effects as the above-mentioned control method.
  • Fig. 1 is a schematic structural diagram of a three-phase three-leg grid-connected inverter in the prior art
  • FIG. 2 is a flowchart of a control method of a three-phase grid-connected inverter provided by an embodiment of the present invention
  • FIG. 3 is a schematic structural diagram of a three-phase three-leg grid-connected inverter provided by an embodiment of the present invention
  • FIG. 4 is a schematic diagram of a division of a power grid cycle according to an embodiment of the present invention.
  • FIG. 5 is a schematic diagram of an inductor current waveform in zone 1 in a power grid period according to an embodiment of the present invention
  • FIG. 6 is a schematic diagram of inductor current control in zone 1 within a power grid period according to an embodiment of the present invention
  • FIG. 7 is a schematic diagram of a peak inductor current waveform of a phase in a half power grid period according to an embodiment of the present invention.
  • FIG. 8 is a schematic diagram of a waveform of a duty cycle of a phase in a half power grid period according to an embodiment of the present invention.
  • the core of the present invention is to provide a three-phase grid-connected inverter control method, system and three-phase grid-connected inverter, which can filter out the harmonics in the circuit and realize high-quality grid-connected current under low power. That is, there is no need to increase the inductance value, so that the parallel inverter equipment in the system can achieve stable operation, which is more suitable for photovoltaic micro-inverters. Moreover, the three-phase three-leg grid-connected inverter of the present application works in the inductor current discontinuous mode, thereby reducing the switching loss of the three-phase three-leg grid-connected inverter.
  • FIG. 2 is a flowchart of a control method of a three-phase grid-connected inverter according to an embodiment of the present invention.
  • the control method of the three-phase grid-connected inverter is applied to a three-phase three-leg grid-connected inverter including a filter capacitor with one end connected to the output inductance of the corresponding bridge arm and the other end connected to the negative electrode of the DC input bus.
  • the control method includes :
  • Step S1 Divide a power grid period into a plurality of equal intervals in advance; wherein, the inductor current corresponding to each interval has two inductor currents in the same direction, and the third inductor current is in the opposite direction.
  • this application improves the structure of the traditional three-phase three-leg grid-connected inverter (please refer to FIG. 3, which is The embodiment of the invention provides a structural schematic diagram of a three-phase three-leg grid-connected inverter).
  • the first switching tube Q1 and the second switching tube Q2 constitute the first of the three-phase three-leg grid-connected inverter.
  • One bridge arm, the third switching tube Q3 and the fourth switching tube Q4 constitute the second bridge arm of the three-phase three-arm grid-connected inverter, the fifth switching tube Q5 and the sixth switching tube Q6 constitute a three-phase three-arm parallel
  • the third bridge arm of the grid inverter; the midpoints of the three bridge arms are connected in series with an output inductor and a filter capacitor; one end of the three filter capacitors C1, C2, C3 is connected to the output inductance of the corresponding bridge arm, and the other One end is connected to the negative pole of the DC input bus (specifically, the negative pole of the DC input bus and the other end of the filter capacitor are grounded to connect the two) to form a filter loop, which can filter out the harmonics in the circuit, and achieve low power Quality grid-connected current, that is, no need to increase the inductance value, so that the parallel inverter equipment in the system can achieve stable operation, which is more suitable for photovoltaic micro-inverters.
  • the three-phase inductor current of the three-phase three-leg grid-connected inverter has symmetry, that is, the cumulative sum of the three-phase inductor current is 0, so directly controlling two of the inductor currents can achieve indirect control of the third inductor current the goal of.
  • the inductor current i L2 of the second output inductor L2 flows through the first output inductor L1, the second output inductor L2, and the AC side Vab ;
  • the inductor current i L3 of the third output inductor L3 flows through the first output inductor L1, the third output inductor L3, and the AC side Vca; controlling the second output inductor L2
  • the inductor current i L2 and the grid B phase voltage are the same phase as the B phase inductor current
  • the third output inductor L3 inductor current i L3 and the grid C phase voltage are the same phase as the C phase inductor current, flowing through the inductance of the first output inductor L1
  • the current i L1 -(i L2 + i L3 ) becomes the A-phase inductor current, that is, controlling the designated two-phase inductor current
  • this application divides a power grid period into multiple equal intervals in advance, as shown in Figure 4, where the inductor current corresponding to each interval has the following characteristics: two inductor currents are in the same direction, and the third inductor current Reverse. In any interval, the two inductor currents in the same direction can be directly controlled to achieve the purpose of indirect control of the reverse inductor current.
  • Step S2 In any interval of each power grid cycle, the two inductor currents in the same direction are controlled in the inductor current discontinuous mode to satisfy the fundamental wave components of the two inductor currents in the same direction during the power grid period. All are sine waves.
  • step S1 the power grid period is divided according to the zero-crossing points of the three-phase inductor current, and a power grid period is divided into 6 intervals, and each interval controls two inductor currents in the same direction.
  • Table 1 below shows the inductor current controlled in each area code
  • Table 2 shows the working switch tubes corresponding to the inductor current controlled in each area code.
  • the same output inductor must be used to control the two-phase inductor current in each interval. Since the output inductor of this application works in discontinuous mode, in order to ensure the integrity of the inductor current of each phase, it is necessary to wait for the inductor current of one phase to continue.
  • phase inductor current that is, the two inductor currents in the same direction in each interval
  • interleaved control that is, the two pairs of switch tubes in each interval work in a staggered manner, so as to finally satisfy: in the power grid cycle,
  • the fundamental components of the two inductor currents in the same direction are both sine waves (the fundamental components of the two inductor currents directly controlled are sine waves, and the fundamental components of the indirectly controlled inductor currents are also sine waves.
  • the three inductor current waveforms are shown in Figure 5, i L1 ⁇ i L3 ⁇ i L1 ⁇ i L3 ..., the dotted line is the fundamental wave component).
  • the three-phase three-leg grid-connected inverter of the present application works in the inductor current discontinuous mode, that is, the inductor current drops to zero in one switching period, thereby reducing the three-phase three-leg grid-connected inverter Switching loss.
  • the invention provides a control method of a three-phase grid-connected inverter, which is applied to a three-phase three-leg grid-connected inverter.
  • This application improves the structure of the three-phase three-leg grid-connected inverter, and connects the filter capacitor to the negative electrode of the DC input bus to form a filter loop, so as to filter out the harmonics in the circuit, and achieve high quality under low power Grid-connected current, that is, there is no need to increase the inductance value, so that the parallel inverter equipment in the system can achieve stable operation, which is more suitable for photovoltaic micro-inverters.
  • the three-phase three-leg grid-connected inverter of the present application works in the inductor current discontinuous mode, that is, the inductor current drops to zero in one switching period, thereby reducing the cost of the three-phase three-leg grid-connected inverter. Switching loss.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle, so as to achieve interleaved control of the two inductor currents in the same direction in the inductor current discontinuous mode.
  • the inductor current in the present application is in discontinuous mode and the output current waveform changes sinusoidally, then the present application can calculate the peak change of the inductor current to adopt analog control and use the peak inductor current as a reference value to control the switching tube. Can produce the required inductor current.
  • FIG. 6 is a schematic diagram of the inductor current control in zone 1 in a power grid period according to an embodiment of the present invention.
  • Ton is the turn-on time
  • Toff is the turn-off time
  • T is the entire switching period in an interval
  • D is the turn-on time ratio
  • Dp is the turn-off time ratio
  • U dc is the DC side voltage
  • U ac is the AC side line voltage
  • ⁇ I Peak inductor current
  • L is the inductance inductance
  • the target switch tube corresponding to the target inductor current is controlled to turn on (for example, i L1 corresponding to zone 1
  • the fourth switching tube Q4 and the first switching tube Q1 are controlled to be turned on)
  • the relationship is obtained according to the peak current of the inductor
  • Obtain the target inductor peak current corresponding to the target inductor current at this time obtain the actual current value of the target inductor current, and when the actual current value reaches its corresponding target inductor peak current, control the target switch to turn off (for example, corresponding to zone 1 the control I L1, obtaining a first output inductor L1 flows through the actual current value, when the actual value reaches the target current corresponding to the peak inductor current, the control of the fourth switching transistor Q4 and the first switching transistor Q1 is turned off);
  • the other target inductor current ends, the other target in
  • FIG. 7 is a schematic diagram of an inductor peak current waveform of a certain phase in a half power grid period according to an embodiment of the present invention. It can be seen from Fig. 7 that the U ac of the first 60 degrees and the back 60 degrees corresponds to different line voltages, and the 60 degrees in the middle is composed of the other two phases, so there is no ⁇ I for control.
  • control method further includes:
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • T is the entire switching cycle in an interval
  • D is the turn-on time ratio of the entire switching cycle
  • I is the inductor current amplitude
  • ⁇ is the inductor current angular frequency
  • t is the time
  • L is the inductance
  • U dc is the DC side voltage
  • U ac is the AC side line voltage
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle, so as to achieve interleaved control of the two inductor currents in the same direction in the inductor current discontinuous mode.
  • this application can also calculate the duty cycle change, so as to use digital control to directly control the switch tube according to the duty cycle to generate the required inductor current.
  • the target switch tube When the actual turn-on time (timing time) of the target switch tube reaches its corresponding target turn-on time, the target switch tube is controlled to turn off; when the target inductor current continues to flow, the two inductor currents in the same direction are Another target inductor current (called the second target inductor current) is controlled by the same principle; when the freewheeling of the second target inductor current ends, the first target inductor current is controlled by the same principle, and the cycle reciprocates to the end of the corresponding interval. In the corresponding interval, the interleaved control of two inductor currents in the same direction is realized in the inductor current discontinuous mode.
  • FIG. 8 is a schematic diagram of a duty cycle waveform of a phase in a half power grid period according to an embodiment of the present invention. It can be seen from Fig. 8 that the U ac of the first 60 degrees and the back 60 degrees corresponds to different line voltages, and the 60 degrees in the middle is composed of the other two phases, so there is no D for control.
  • the control method also includes:
  • T In order to reduce the ripple, make T change with I; from (15): T ⁇ I; T can change in the same proportion with I, so that the coefficients of change of I and T are the same as ⁇ ;
  • the power of the full bridge can be controlled.
  • it further includes:
  • the phases of the two inductive currents in the same direction are moved, so that there is a phase difference between the inductive current and the grid voltage during the power grid cycle.
  • the phase of the inductor current is not related to the phase of the grid voltage, as long as the phase of the two inductor currents in the same direction is moved (the phase of the third inductor current changes accordingly), the difference between the inductor current and the grid voltage can be achieved.
  • the purpose of the different phase difference between the two can realize the power factor change between 0 and 1.
  • the present application can move the phases of the two inductor currents in the same direction to meet the current power factor demand.
  • the present invention also provides a three-phase grid-connected inverter control system, which is applied to a three-phase three-arm grid-connected inverter that includes a filter capacitor with one end connected to the output inductance of the corresponding bridge arm and the other end connected to the negative electrode of the DC input bus.
  • the control system includes:
  • the period division module is used to divide a power grid period into a plurality of equal intervals in advance; wherein the inductance current corresponding to each interval is two inductance currents in the same direction, and the third inductance current is in the opposite direction;
  • the interleaved control module is used to control two inductive currents in the same direction in the inductive current discontinuous mode in any interval of each power grid cycle, so as to meet the requirements of the two inductive currents in the same direction during the power grid cycle.
  • the fundamental components are all sine waves.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle, so as to realize the interleaved control of the two inductor currents in the same direction in the inductor current discontinuous mode.
  • the process of controlling two inductor currents in the same direction in the inductor current discontinuous mode includes:
  • T is the entire switching cycle in an interval
  • D is the turn-on time ratio of the entire switching cycle
  • I is the inductor current amplitude
  • ⁇ is the inductor current angular frequency
  • t is the time
  • L is the inductance
  • U dc is the DC side voltage
  • U ac is the AC side line voltage
  • the other target inductor current of the two inductor currents in the same direction is controlled in the same principle, so as to realize the interleaved control of the two inductor currents in the same direction in the inductor current discontinuous mode.
  • the present invention also provides a three-phase grid-connected inverter, which includes six switch tubes, three output inductors and three filter capacitors; among them:
  • the first end of the first switch tube, the third switch tube, and the fifth switch tube are all connected to the positive pole of the DC input bus, and the second end of the second switch tube, the fourth switch tube, and the sixth switch tube are all connected to the DC input bus.
  • Negative; the second terminal of the first switch tube is connected to the first terminal of the second switch tube and the common terminal is connected to the first terminal of the first output inductor.
  • the second terminal of the third switch tube is connected to the first terminal of the fourth switch tube.
  • the common terminal is connected with the first terminal of the second output inductor, the second terminal of the fifth switch tube is connected with the first terminal of the sixth switch tube, and the common terminal is connected with the first terminal of the third output inductor;
  • the second end of the output inductor is connected to the first end of the first filter capacitor and the common end is connected to the phase A line of the power grid, the second end of the second output inductor is connected to the first end of the second filter capacitor and the common end is connected to the phase B of the power grid
  • the second end of the third output inductor is connected to the first end of the third filter capacitor and the common end is connected to the phase C line of the power grid; the second ends of the first filter capacitor, the second filter capacitor and the third filter capacitor are connected to the DC input The negative pole of the busbar;
  • control method of the three-phase grid-connected inverter adopts any of the above-mentioned control methods of the three-phase grid-connected inverter.

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  • Inverter Devices (AREA)

Abstract

一种三相并网逆变器，及其控制系统和控制方法。该逆变器为三相三桥臂并网逆变器，使滤波电容连接直流输入母线的负极以构成滤波回路，从而可滤除电路中的谐波，实现了小功率下高质量的并网电流，即无需增大电感值，从而使系统中并联的逆变器设备实现稳定工作，较适用于光伏微型逆变器。而且，三相三桥臂并网逆变器工作在电感电流断续模式，即在一个开关周期内，电感电流降至0，从而降低了三相三桥臂并网逆变器的开关损耗。

Description

一种三相并网逆变器的控制方法、系统及三相并网逆变器
本申请要求于2019年10月30日提交至中国专利局、申请号为201911045352.8、发明名称为“一种三相并网逆变器的控制方法、系统及三相并网逆变器”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本发明涉及太阳能光伏并网系统领域，特别是涉及一种三相并网逆变器的控制方法、系统及三相并网逆变器。
背景技术
在太阳能光伏并网系统中，三相三桥臂并网逆变器是较为常用的逆变器。请参照图1，图1为现有技术中的一种三相三桥臂并网逆变器的结构示意图。从图1中可以看出，三相三桥臂并网逆变器因未构成滤波回路而导致谐波无法被滤除，使得在低功率下并网电流波形的质量较差。现有技术中，为了抑制三相三桥臂并网逆变器中的谐波大小，通常采用增大电感L1、L2、L3的电感值的方式，但电感值越大，系统中并联的逆变器设备越容易发生谐振，无法适用于光伏微型逆变器。而且，现有的三相三桥臂并网逆变器通常工作在电感电流连续模式，即在一个开关周期内，电感L1、L2、L3的电流不降至0，导致三相三桥臂并网逆变器的开关损耗较大。
因此，如何提供一种解决上述技术问题的方案是本领域的技术人员目前需要解决的问题。
发明内容
本发明的目的是提供一种三相并网逆变器的控制方法、系统及三相并网逆变器，可滤除电路中的谐波，实现了小功率下高质量的并网电流，即无需增大电感值，从而使系统中并联的逆变器设备实现稳定工作，较适用于光伏微型逆变器。而且，本申请的三相三桥臂并网逆变器工作在电感电流断续模式，从而降低了三相三桥臂并网逆变器的开关损耗。
为解决上述技术问题，本发明提供了一种三相并网逆变器的控制方法，应用于包含一端连接对应桥臂的输出电感、另一端连接直流输入母线的负极的滤波电容的三相三桥臂并网逆变器，所述控制方法包括：
预先将一电网周期划分为多个相等的区间；其中，每个区间对应的电感电流均为两个电感电流同向、第三个电感电流反向；
在每个电网周期的任一区间内，在电感电流断续模式下对两个同向的电感电流进行控制，以满足在电网周期内，两个同向的电感电流的基波分量均为正弦波。
优选地，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
根据预设电感峰值电流求取关系式
Figure PCTCN2019126250-appb-000001
求取所述目标电感电流此时对应的目标电感峰值电流；其中，ΔI为电感峰值电流，T为一区间内的整个开关周期，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
获取所述目标电感电流的实际电流值，并当所述实际电流值到达其对应的目标电感峰值电流时，控制所述目标开关管关断；
当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
优选地，在求取所述目标电感电流此时对应的目标电感峰值电流之后，在所述实际电流值到达其对应的目标电感峰值电流之前，所述控制方法还包括：
将所述目标电感峰值电流乘以一个正系数α，并将乘积结果作为所述目标电感电流对应的目标电感峰值电流。
优选地，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
根据预设开通时间比求取关系式
Figure PCTCN2019126250-appb-000002
求取所述目标电感电流在整个开关周期内对应的目标开通时间比，并根据所述目标开通时间比求取所述目标电感电流在整个开关周期内对应的目标开通时间；其中，T为一区间内的整个开关周期，D为整个开关周期的开通时间比，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
当所述目标开关管的实际开通时间到达其对应的目标开通时间时，控制所述目标开关管关断；
当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
优选地，在求取所述目标电感电流在整个开关周期内对应的目标开通时间比之后，在根据所述目标开通时间比求取所述目标电感电流在整个开关周期内对应的目标开通时间之前，所述控制方法还包括：
将所述目标开通时间比乘以一个正系数α，并将乘积结果作为所述目标电感电流在整个开关周期内对应的目标开通时间比。
优选地，还包括：
根据功率因数需求量对两个同向的电感电流的相位进行移动，以使在电网周期内，电感电流与电网电压之间存在相位差。
为解决上述技术问题，本发明还提供了一种三相并网逆变器的控制系统，应用于包含一端连接对应桥臂的输出电感、另一端连接直流输入母线的负极的滤波电容的三相三桥臂并网逆变器，所述控制系统包括：
周期分区模块，用于预先将一电网周期划分为多个相等的区间；其中，每个区间对应的电感电流均为两个电感电流同向、第三个电感电流反向；
交错控制模块，用于在每个电网周期的任一区间内，在电感电流断续模式下对两个同向的电感电流进行控制，以满足在电网周期内，两个同向的电感电流的基波分量均为正弦波。
优选地，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
根据预设电感峰值电流求取关系式
Figure PCTCN2019126250-appb-000003
求取所述目标电感电流此时对应的目标电感峰值电流；其中，ΔI为电感峰值电流，T为一区间内的整个开关周期，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
获取所述目标电感电流的实际电流值，并当所述实际电流值到达其对应的目标电感峰值电流时，控制所述目标开关管关断；
当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
优选地，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
根据预设开通时间比求取关系式
Figure PCTCN2019126250-appb-000004
求取所述目标电感电流在整个开关周期内对应的目标开通时间比，并根据所述目标开通时间比求取所述目标电感电流在整个开关周期内对应的目标开通 时间；其中，T为一区间内的整个开关周期，D为整个开关周期的开通时间比，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
当所述目标开关管的实际开通时间到达其对应的目标开通时间时，控制所述目标开关管关断；
当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
为解决上述技术问题，本发明还提供了一种三相并网逆变器，包括六个开关管、三个输出电感及三个滤波电容；其中：
第一开关管、第三开关管及第五开关管的第一端均连接直流输入母线的正极，第二开关管、第四开关管及第六开关管的第二端均连接直流输入母线的负极；第一开关管的第二端与第二开关管的第一端连接且公共端与第一输出电感的第一端连接，第三开关管的第二端与第四开关管的第一端连接且公共端与第二输出电感的第一端连接，第五开关管的第二端与第六开关管的第一端连接且公共端与第三输出电感的第一端连接；第一输出电感的第二端与第一滤波电容的第一端连接且公共端连接电网A相线，第二输出电感的第二端与第二滤波电容的第一端连接且公共端连接电网B相线，第三输出电感的第二端与第三滤波电容的第一端连接且公共端连接电网C相线；第一滤波电容、第二滤波电容及第三滤波电容的第二端连接直流输入母线的负极；
其中，所述三相并网逆变器的控制方法采用上述任一种三相并网逆变器的控制方法。
本发明提供了一种三相并网逆变器的控制方法，应用于三相三桥臂并网逆变器。本申请对三相三桥臂并网逆变器的结构进行改进，使滤波电容连接直流输入母线的负极以构成滤波回路，从而可滤除电路中的谐波，实现了小功率下高质量的并网电流，即无需增大电感值，从而使系统中并联的逆变器设备实现稳定工作，较适用于光伏微型逆变器。而且，本申请的 三相三桥臂并网逆变器工作在电感电流断续模式，即在一个开关周期内，电感电流降至0，从而降低了三相三桥臂并网逆变器的开关损耗。
本发明还提供了一种三相并网逆变器的控制系统及三相并网逆变器，与上述控制方法具有相同的有益效果。
附图说明
为了更清楚地说明本发明实施例中的技术方案，下面将对现有技术和实施例中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图。
图1为现有技术中的一种三相三桥臂并网逆变器的结构示意图；
图2为本发明实施例提供的一种三相并网逆变器的控制方法的流程图；
图3为本发明实施例提供的一种三相三桥臂并网逆变器的结构示意图；
图4为本发明实施例提供的一种电网周期的分区原理图；
图5为本发明实施例提供的一种电网周期内1区的电感电流波形示意图；
图6为本发明实施例提供的一种电网周期内1区的电感电流控制原理图；
图7为本发明实施例提供的一种半个电网周期内某一相的电感峰值电流波形示意图；
图8为本发明实施例提供的一种半个电网周期内某一相的占空比波形示意图。
具体实施方式
本发明的核心是提供一种三相并网逆变器的控制方法、系统及三相并网逆变器，可滤除电路中的谐波，实现了小功率下高质量的并网电流，即无需增大电感值，从而使系统中并联的逆变器设备实现稳定工作，较适用 于光伏微型逆变器。而且，本申请的三相三桥臂并网逆变器工作在电感电流断续模式，从而降低了三相三桥臂并网逆变器的开关损耗。
为使本发明实施例的目的、技术方案和优点更加清楚，下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。
请参照图2，图2为本发明实施例提供的一种三相并网逆变器的控制方法的流程图。
该三相并网逆变器的控制方法，应用于包含一端连接对应桥臂的输出电感、另一端连接直流输入母线的负极的滤波电容的三相三桥臂并网逆变器，控制方法包括：
步骤S1：预先将一电网周期划分为多个相等的区间；其中，每个区间对应的电感电流均为两个电感电流同向、第三个电感电流反向。
具体地，首先对本申请的三相三桥臂并网逆变器的结构进行介绍：本申请对传统三相三桥臂并网逆变器的结构进行改进(请参照图3，图3为本发明实施例提供的一种三相三桥臂并网逆变器的结构示意图)，图3中，第一开关管Q1和第二开关管Q2构成三相三桥臂并网逆变器的第一桥臂，第三开关管Q3和第四开关管Q4构成三相三桥臂并网逆变器的第二桥臂，第五开关管Q5和第六开关管Q6构成三相三桥臂并网逆变器的第三桥臂；三个桥臂的中点均串接一个输出电感和一个滤波电容；三个滤波电容C1、C2、C3的一端一一连接对应桥臂的输出电感、另一端连接直流输入母线的负极(具体是直流输入母线的负极和滤波电容的另一端均接地实现二者连接)，以构成滤波回路，从而可滤除电路中的谐波，实现了小功率下高质量的并网电流，即无需增大电感值，从而使系统中并联的逆变器设备实现稳定工作，较适用于光伏微型逆变器。
考虑到三相三桥臂并网逆变器的三相电感电流具有对称性，即三相电感电流累加和为0，所以直接控制其中两个电感电流，即可达到间接控制 第三个电感电流的目的。参照图3可知，当第一开关管Q1、第四开关管Q4开通(工作)时，第二输出电感L2的电感电流i L2流过第一输出电感L1、第二输出电感L2、交流侧Vab；当第一开关管Q1、第六开关管Q6开通时，第三输出电感L3的电感电流i L3流过第一输出电感L1、第三输出电感L3、交流侧Vca；控制第二输出电感L2的电感电流i L2与电网B相电压同相位作为B相电感电流，第三输出电感L3的电感电流i L3与电网C相电压同相位作为C相电感电流，流过第一输出电感L1的电感电流i L1＝-(i L2+i L3)成为A相电感电流，即控制指定的两相电感电流，第三相电感电流自然形成，为另两相电感电流之和的相反数。
基于此，本申请提前将一电网周期划分为多个相等的区间，如图4所示，其中，每一个区间对应的电感电流都有如下特点：两个电感电流同向，第三个电感电流反向。则在任一区间内，直接控制同向的两个电感电流，即可达到间接控制反向的电感电流的目的。
步骤S2：在每个电网周期的任一区间内，在电感电流断续模式下对两个同向的电感电流进行控制，以满足在电网周期内，两个同向的电感电流的基波分量均为正弦波。
具体地，由步骤S1可知：根据三相电感电流的过零点划分电网周期，将一电网周期划分为6个区间，每个区间控制同向的两个电感电流。下表1表示每个区号内控制的电感电流，表2表示每个区号内控制的电感电流对应的工作的开关管。
表1
区号 1 2 3 4 5 6
控制对象 i L1、i L3 i L2、i L3 i L1、i L2 i L1、i L3 i L2、i L3 i L1、i L2
表2
Figure PCTCN2019126250-appb-000005
在每个区间内控制两相电感电流时都要使用同一输出电感，由于本申请的输出电感工作在断续模式，所以为保证每一相电感电流续流的完整，需等待一相电感电流续流结束后再开始控制另一相电感电流，即各区间内同向的两个电感电流采用交错控制，也即各区间内的两对开关管交错工作，以最终满足于：在电网周期内，两个同向的电感电流的基波分量均为正弦波(直接控制的两个电感电流的基波分量为正弦波，则间接控制的电感电流的基波分量也为正弦波，以1区为例，三个电感电流波形如图5所示，i L1→i L3→i L1→i L3…，虚线为其基波分量)。可见，本申请的三相三桥臂并网逆变器工作在电感电流断续模式，即在一个开关周期内，电感电流降至0，从而降低了三相三桥臂并网逆变器的开关损耗。
本发明提供了一种三相并网逆变器的控制方法，应用于三相三桥臂并网逆变器。本申请对三相三桥臂并网逆变器的结构进行改进，使滤波电容连接直流输入母线的负极以构成滤波回路，从而可滤除电路中的谐波，实现了小功率下高质量的并网电流，即无需增大电感值，从而使系统中并联的逆变器设备实现稳定工作，较适用于光伏微型逆变器。而且，本申请的三相三桥臂并网逆变器工作在电感电流断续模式，即在一个开关周期内，电感电流降至0，从而降低了三相三桥臂并网逆变器的开关损耗。
在上述实施例的基础上：
作为一种可选地实施例，在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制目标电感电流对应的目标开关管开通；
根据预设电感峰值电流求取关系式
Figure PCTCN2019126250-appb-000006
求取目标电感电流此时对应的目标电感峰值电流；其中，ΔI为电感峰值电流， T为一区间内的整个开关周期，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
获取目标电感电流的实际电流值，并当实际电流值到达其对应的目标电感峰值电流时，控制目标开关管关断；
当目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
具体地，本申请的电感电流是断续模式而输出的电流波形是按正弦变化，则本申请可计算电感电流峰值变化，以采用模拟控制，用电感峰值电流作为参考值控制开关管，就能产生需要的电感电流。
请参照图6，图6为本发明实施例提供的一种电网周期内1区的电感电流控制原理图。Ton为开通时间，Toff为关断时间，T为一区间内的整个开关周期，D为开通时间比，Dp为关断时间比，U dc为直流侧电压，U ac是交流侧线电压，ΔI为电感峰值电流，L为电感感量；则：
Figure PCTCN2019126250-appb-000007
Figure PCTCN2019126250-appb-000008
每个开关周期的电感峰值电流：ΔI；每个开关周期的电感平均电流：Isinωt，令
Figure PCTCN2019126250-appb-000009
(1)、(2)代入(3)，得到：
Figure PCTCN2019126250-appb-000010
则电感峰值电流求取关系式：
Figure PCTCN2019126250-appb-000011
基于此，在对两个同向的电感电流中的一目标电感电流(称为第一目标电感电流)进行控制时，控制目标电感电流对应的目标开关管开通(如 对1区对应的i L1进行控制，则控制第四开关管Q4和第一开关管Q1开通)；根据电感峰值电流求取关系式
Figure PCTCN2019126250-appb-000012
求取目标电感电流此时对应的目标电感峰值电流；获取目标电感电流的实际电流值，并当实际电流值到达其对应的目标电感峰值电流时，控制目标开关管关断(如对1区对应的i L1进行控制，则获取流经第一输出电感L1的实际电流值，当实际电流值到达其对应的目标电感峰值电流时，控制第四开关管Q4和第一开关管Q1关断)；当目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流(称为第二目标电感电流)进行同原理控制(如对1区对应的电感电流进行控制，则i L1续流结束后，对i L3进行同原理控制)；当第二目标电感电流续流结束后，再对第一目标电感电流进行同原理控制，循环往复至对应区间结束，从而在对应区间内实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
请参照图7，图7为本发明实施例提供的一种半个电网周期内某一相的电感峰值电流波形示意图。从图7可以看出，前60度和后60度的U ac对应不同的线电压，而中间的60度是其它两相合成的，也就没有用于控制的ΔI。
作为一种可选地实施例，在求取目标电感电流此时对应的目标电感峰值电流之后，在实际电流值到达其对应的目标电感峰值电流之前，控制方法还包括：
将目标电感峰值电流乘以一个正系数α，并将乘积结果作为目标电感电流对应的目标电感峰值电流。
本申请在此先对本实施例不作详细介绍，与后续实施例共同进行介绍。
作为一种可选地实施例，在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制目标电感电流对应的目标开关管开通；
根据预设开通时间比求取关系式
Figure PCTCN2019126250-appb-000013
求取目标电感电流在整个开关周期内对应的目标开通时间比，并根据目标开通时间比求取目标电感电流在整个开关周期内对应的目标开通时间；其中，T为一区间内的整个开关周期，D为整个开关周期的开通时间比，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
当目标开关管的实际开通时间到达其对应的目标开通时间时，控制目标开关管关断；
当目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
具体地，本申请还可计算占空比变化，以采用数字控制，直接根据占空比控制开关管，就能产生需要的电感电流。
由(1)、(2)得：
Figure PCTCN2019126250-appb-000014
Figure PCTCN2019126250-appb-000015
Figure PCTCN2019126250-appb-000016
Figure PCTCN2019126250-appb-000017
令
Figure PCTCN2019126250-appb-000018
(1)、(9)代入(3)，得到：
Figure PCTCN2019126250-appb-000019
Figure PCTCN2019126250-appb-000020
则开通时间比求取关系式：
Figure PCTCN2019126250-appb-000021
基于此，在对两个同向的电感电流中的一目标电感电流(称为第一目标电感电流)进行控制时，控制目标电感电流对应的目标开关管开通；根据开通时间比求取关系式
Figure PCTCN2019126250-appb-000022
求取目标电感电流在整个开关周期内对应的目标开通时间比，并根据目标开通时间比求取目标电感电流在整个开关周期内对应的目标开通时间Ton＝D×T；从目标开关管开通时开始计时，当目标开关管的实际开通时间(计时时间)到达其对应的目标开通时间时，控制目标开关管关断；当目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流(称为第二目标电感电流)进行同原理控制；当第二目标电感电流续流结束后，再对第一目标电感电流进行同原理控制，循环往复至对应区间结束，从而在对应区间内实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
请参照图8，图8为本发明实施例提供的一种半个电网周期内某一相的占空比波形示意图。从图8可以看出，前60度和后60度的U ac对应不同的线电压，而中间的60度是其它两相合成的，也就没有用于控制的D。
作为一种可选地实施例，在求取目标电感电流在整个开关周期内对应的目标开通时间比之后，在根据目标开通时间比求取目标电感电流在整个开关周期内对应的目标开通时间之前，控制方法还包括：
将目标开通时间比乘以一个正系数α，并将乘积结果作为目标电感电流在整个开关周期内对应的目标开通时间比。
进一步地，由于两个同向的电感电流间隔轮番控制，则
Figure PCTCN2019126250-appb-000023
由(9)得：
Figure PCTCN2019126250-appb-000024
Figure PCTCN2019126250-appb-000025
(12)代入(14)，得
Figure PCTCN2019126250-appb-000026
为减小纹波，使T随I变化；由(15)得：T∝I；T可随I同比例变化，令I和T的变化系数同为α；
则
Figure PCTCN2019126250-appb-000027
Figure PCTCN2019126250-appb-000028
Figure PCTCN2019126250-appb-000029
通过调节变化系数α，能够控制全桥的功率。
作为一种可选地实施例，还包括：
根据功率因数需求量对两个同向的电感电流的相位进行移动，以使在电网周期内，电感电流与电网电压之间存在相位差。
进一步地，由于电感电流的相位与电网电压的相位没有关联，所以只要移动两个同向的电感电流的相位(第三个电感电流的相位随之变化)，就能达到电感电流与电网电压之间不同相位差的目的，也就能够实现功率因 数在0～1之间变化。基于此，本申请可对两个同向的电感电流的相位进行移动，以满足当前的功率因数需求量。
本发明还提供了一种三相并网逆变器的控制系统，应用于包含一端连接对应桥臂的输出电感、另一端连接直流输入母线的负极的滤波电容的三相三桥臂并网逆变器，控制系统包括：
周期分区模块，用于预先将一电网周期划分为多个相等的区间；其中，每个区间对应的电感电流均为两个电感电流同向、第三个电感电流反向；
交错控制模块，用于在每个电网周期的任一区间内，在电感电流断续模式下对两个同向的电感电流进行控制，以满足在电网周期内，两个同向的电感电流的基波分量均为正弦波。
作为一种可选地实施例，在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制目标电感电流对应的目标开关管开通；
根据预设电感峰值电流求取关系式
Figure PCTCN2019126250-appb-000030
求取目标电感电流此时对应的目标电感峰值电流；其中，ΔI为电感峰值电流，T为一区间内的整个开关周期，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
获取目标电感电流的实际电流值，并当实际电流值到达其对应的目标电感峰值电流时，控制目标开关管关断；
当目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
作为一种可选地实施例，在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
在对两个同向的电感电流中的一目标电感电流进行控制时，控制目标电感电流对应的目标开关管开通；
根据预设开通时间比求取关系式
Figure PCTCN2019126250-appb-000031
求取目标电感电流在整个开关周期内对应的目标开通时间比，并根据目标开通时间比求取目标电感电流在整个开关周期内对应的目标开通时间；其中，T为一区间内的整个开关周期，D为整个开关周期的开通时间比，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
当目标开关管的实际开通时间到达其对应的目标开通时间时，控制目标开关管关断；
当目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
本申请提供的控制系统的介绍请参考上述控制方法的实施例，本申请在此不再赘述。
本发明还提供了一种三相并网逆变器，包括六个开关管、三个输出电感及三个滤波电容；其中：
第一开关管、第三开关管及第五开关管的第一端均连接直流输入母线的正极，第二开关管、第四开关管及第六开关管的第二端均连接直流输入母线的负极；第一开关管的第二端与第二开关管的第一端连接且公共端与第一输出电感的第一端连接，第三开关管的第二端与第四开关管的第一端连接且公共端与第二输出电感的第一端连接，第五开关管的第二端与第六开关管的第一端连接且公共端与第三输出电感的第一端连接；第一输出电感的第二端与第一滤波电容的第一端连接且公共端连接电网A相线，第二输出电感的第二端与第二滤波电容的第一端连接且公共端连接电网B相 线，第三输出电感的第二端与第三滤波电容的第一端连接且公共端连接电网C相线；第一滤波电容、第二滤波电容及第三滤波电容的第二端连接直流输入母线的负极；
其中，三相并网逆变器的控制方法采用上述任一种三相并网逆变器的控制方法。
本申请提供的三相并网逆变器(如图3所示)的介绍请参考上述控制方法的实施例，本申请在此不再赘述。
还需要说明的是，在本说明书中，诸如第一和第二等之类的关系术语仅仅用来将一个实体或者操作与另一个实体或操作区分开来，而不一定要求或者暗示这些实体或操作之间存在任何这种实际的关系或者顺序。而且，术语“包括”、“包含”或者其任何其他变体意在涵盖非排他性的包含，从而使得包括一系列要素的过程、方法、物品或者设备不仅包括那些要素，而且还包括没有明确列出的其他要素，或者是还包括为这种过程、方法、物品或者设备所固有的要素。在没有更多限制的情况下，由语句“包括一个……”限定的要素，并不排除在包括所述要素的过程、方法、物品或者设备中还存在另外的相同要素。
对所公开的实施例的上述说明，使本领域专业技术人员能够实现或使用本发明。对这些实施例的多种修改对本领域的专业技术人员来说将是显而易见的，本文中所定义的一般原理可以在不脱离本发明的精神或范围的情况下，在其他实施例中实现。因此，本发明将不会被限制于本文所示的这些实施例，而是要符合与本文所公开的原理和新颖特点相一致的最宽的范围。

Claims (10)

  1. 一种三相并网逆变器的控制方法，其特征在于，应用于包含一端连接对应桥臂的输出电感、另一端连接直流输入母线的负极的滤波电容的三相三桥臂并网逆变器，所述控制方法包括：
    预先将一电网周期划分为多个相等的区间；其中，每个区间对应的电感电流均为两个电感电流同向、第三个电感电流反向；
    在每个电网周期的任一区间内，在电感电流断续模式下对两个同向的电感电流进行控制，以满足在电网周期内，两个同向的电感电流的基波分量均为正弦波。
  2. 如权利要求1所述的三相并网逆变器的控制方法，其特征在于，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
    在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
    根据预设电感峰值电流求取关系式
    Figure PCTCN2019126250-appb-100001
    求取所述目标电感电流此时对应的目标电感峰值电流；其中，ΔI为电感峰值电流，T为一区间内的整个开关周期，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
    获取所述目标电感电流的实际电流值，并当所述实际电流值到达其对应的目标电感峰值电流时，控制所述目标开关管关断；
    当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
  3. 如权利要求2所述的三相并网逆变器的控制方法，其特征在于，在求取所述目标电感电流此时对应的目标电感峰值电流之后，在所述实际电流值到达其对应的目标电感峰值电流之前，所述控制方法还包括：
    将所述目标电感峰值电流乘以一个正系数α，并将乘积结果作为所述目标电感电流对应的目标电感峰值电流。
  4. 如权利要求1所述的三相并网逆变器的控制方法，其特征在于，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
    在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
    根据预设开通时间比求取关系式
    Figure PCTCN2019126250-appb-100002
    求取所述目标电感电流在整个开关周期内对应的目标开通时间比，并根据所述目标开通时间比求取所述目标电感电流在整个开关周期内对应的目标开通时间；其中，T为一区间内的整个开关周期，D为整个开关周期的开通时间比，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
    当所述目标开关管的实际开通时间到达其对应的目标开通时间时，控制所述目标开关管关断；
    当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
  5. 如权利要求4所述的三相并网逆变器的控制方法，其特征在于，在求取所述目标电感电流在整个开关周期内对应的目标开通时间比之后，在根据所述目标开通时间比求取所述目标电感电流在整个开关周期内对应的目标开通时间之前，所述控制方法还包括：
    将所述目标开通时间比乘以一个正系数α，并将乘积结果作为所述目标电感电流在整个开关周期内对应的目标开通时间比。
  6. 如权利要求1-5任一项所述的三相并网逆变器的控制方法，其特征在于，还包括：
    根据功率因数需求量对两个同向的电感电流的相位进行移动，以使在电网周期内，电感电流与电网电压之间存在相位差。
  7. 一种三相并网逆变器的控制系统，其特征在于，应用于包含一端连接对应桥臂的输出电感、另一端连接直流输入母线的负极的滤波电容的三相三桥臂并网逆变器，所述控制系统包括：
    周期分区模块，用于预先将一电网周期划分为多个相等的区间；其中，每个区间对应的电感电流均为两个电感电流同向、第三个电感电流反向；
    交错控制模块，用于在每个电网周期的任一区间内，在电感电流断续模式下对两个同向的电感电流进行控制，以满足在电网周期内，两个同向的电感电流的基波分量均为正弦波。
  8. 如权利要求7所述的三相并网逆变器的控制系统，其特征在于，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
    在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
    根据预设电感峰值电流求取关系式
    Figure PCTCN2019126250-appb-100003
    求取所述目标电感电流此时对应的目标电感峰值电流；其中，ΔI为电感峰值电流，T为一区间内的整个开关周期，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
    获取所述目标电感电流的实际电流值，并当所述实际电流值到达其对应的目标电感峰值电流时，控制所述目标开关管关断；
    当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
  9. 如权利要求7所述的三相并网逆变器的控制系统，其特征在于，所述在电感电流断续模式下对两个同向的电感电流进行控制的过程，包括：
    在对两个同向的电感电流中的一目标电感电流进行控制时，控制所述目标电感电流对应的目标开关管开通；
    根据预设开通时间比求取关系式
    Figure PCTCN2019126250-appb-100004
    求取所述目标电感电流在整个开关周期内对应的目标开通时间比，并根据所述目标开通时间比求取所述目标电感电流在整个开关周期内对应的目标开通时间；其中，T为一区间内的整个开关周期，D为整个开关周期的开通时间比，I为电感电流幅值，ω为电感电流角频率，t为时间，L为电感感量，U dc为直流侧电压，U ac为交流侧线电压；
    当所述目标开关管的实际开通时间到达其对应的目标开通时间时，控制所述目标开关管关断；
    当所述目标电感电流续流结束后，对两个同向的电感电流中的另一目标电感电流进行同原理控制，以实现在电感电流断续模式下对两个同向的电感电流进行交错控制。
  10. 一种三相并网逆变器，其特征在于，包括六个开关管、三个输出电感及三个滤波电容；其中：
    第一开关管、第三开关管及第五开关管的第一端均连接直流输入母线的正极，第二开关管、第四开关管及第六开关管的第二端均连接直流输入母线的负极；第一开关管的第二端与第二开关管的第一端连接且公共端与第一输出电感的第一端连接，第三开关管的第二端与第四开关管的第一端连接且公共端与第二输出电感的第一端连接，第五开关管的第二端与第六开关管的第一端连接且公共端与第三输出电感的第一端连接；第一输出电感的第二端与第一滤波电容的第一端连接且公共端连接电网A相线，第二输出电感的第二端与第二滤波电容的第一端连接且公共端连接电网B相线，第三输出电感的第二端与第三滤波电容的第一端连接且公共端连接电网C相线；第一滤波电容、第二滤波电容及第三滤波电容的第二端连接直流输入母线的负极；
    其中，所述三相并网逆变器的控制方法采用如权利要求1-6任一项所述的三相并网逆变器的控制方法。
PCT/CN2019/126250 2019-10-30 2019-12-18 一种三相并网逆变器的控制方法、系统及三相并网逆变器 Ceased WO2021082220A1 (zh)

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