WO2021179937A1 - 电源电路及充电设备 - Google Patents

电源电路及充电设备 Download PDF

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Publication number
WO2021179937A1
WO2021179937A1 PCT/CN2021/078536 CN2021078536W WO2021179937A1 WO 2021179937 A1 WO2021179937 A1 WO 2021179937A1 CN 2021078536 W CN2021078536 W CN 2021078536W WO 2021179937 A1 WO2021179937 A1 WO 2021179937A1
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WO
WIPO (PCT)
Prior art keywords
circuit
voltage
output
power supply
power conversion
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2021/078536
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English (en)
French (fr)
Inventor
江森龙
邱治维
张加亮
田晨
张俊
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Guangdong Oppo Mobile Telecommunications Corp Ltd
Original Assignee
Guangdong Oppo Mobile Telecommunications Corp Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Guangdong Oppo Mobile Telecommunications Corp Ltd filed Critical Guangdong Oppo Mobile Telecommunications Corp Ltd
Priority to EP21768050.3A priority Critical patent/EP4120507A4/en
Publication of WO2021179937A1 publication Critical patent/WO2021179937A1/zh
Priority to US17/941,689 priority patent/US12267018B2/en
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/06—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries for charging batteries from AC mains by converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries
    • H02J7/90—Regulation of charging or discharging current or voltage
    • H02J7/933—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/005—Conversion of DC power input into DC power output using Cuk converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/06—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K3/00—Circuits for generating electric pulses; Monostable, bistable or multistable circuits
    • H03K3/02—Generators characterised by the type of circuit or by the means used for producing pulses
    • H03K3/53—Generators characterised by the type of circuit or by the means used for producing pulses by the use of an energy-accumulating element discharged through the load by a switching device controlled by an external signal and not incorporating positive feedback
    • H03K3/57—Generators characterised by the type of circuit or by the means used for producing pulses by the use of an energy-accumulating element discharged through the load by a switching device controlled by an external signal and not incorporating positive feedback the switching device being a semiconductor device
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Details of circuit arrangements for charging or discharging batteries or supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries
    • H02J7/40—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries characterised by the exchange of charge or discharge related data
    • H02J7/42—Circuit arrangements for charging or discharging batteries or for supplying loads from batteries characterised by the exchange of charge or discharge related data with electronic devices having internal batteries, e.g. mobile phones

Definitions

  • the present disclosure relates to the field of charging, in particular to a power supply circuit and charging equipment.
  • charging devices are required to have different levels of voltage output capabilities.
  • the voltage output by the charging device needs to be a continuously adjustable direct current.
  • the charging equipment is usually equipped with a pulse transformer, so as to modulate the voltage on the primary side of the pulse transformer through the PWM control chip, so as to adjust the voltage at the output end of the pulse transformer.
  • the turns ratio of the pulse transformer is generally fixed, to achieve a continuously adjustable DC output at the output of the pulse transformer, the power supply voltage needs to be within a certain range. Therefore, this solution has higher requirements for the power supply. Once the power supply voltage fluctuates greatly or the power supply voltage is too low or too high, the voltage adjustable range at the output end of the pulse transformer will be limited.
  • One purpose of the present disclosure is to improve the adaptability of the charging device to different power supply sources, so as to ensure the adjustable range of the output voltage.
  • the present disclosure provides a power supply circuit including:
  • the transformer circuit includes a pulse transformer and a switch control circuit; the primary winding of the pulse transformer is connected to the power source and connected to the switch control circuit, and the switch control circuit is used to modulate the voltage on the primary winding into a pulse voltage ;
  • the first power conversion circuit the input terminal of the first power conversion circuit is connected to the secondary winding of the transformer, and is used to connect the transformer to the transformer when the voltage output by the secondary winding exceeds the first preset voltage range.
  • the voltage on the secondary winding is transformed into the first preset voltage range and then output.
  • a charging device which includes a power inlet and a power circuit, where the power inlet is used to access a power source.
  • the first power conversion circuit by arranging the first power conversion circuit on the secondary side of the transformer circuit, when the power supply voltage is too high or too low or the equipment to be powered requires a higher or lower power supply voltage, the first power conversion circuit can be A power conversion circuit can correspondingly convert the voltage on the secondary winding of the pulse transformer to meet the power supply requirements of the equipment to be powered. Therefore, the technical solution of the present disclosure improves the adaptability to different power supply sources to ensure the adjustable range of the output voltage.
  • Fig. 1 is a block diagram showing a circuit structure of a power supply circuit according to an embodiment
  • FIG. 2 is a block diagram showing the circuit structure of a power supply circuit according to another embodiment
  • Fig. 3 is a circuit diagram of the power supply circuit shown in an example according to Fig. 2;
  • Fig. 4 shows the corresponding interval of the preset voltage range on the secondary side voltage waveform of the pulse transformer according to an example
  • Fig. 5 shows the corresponding interval of the preset voltage range on the secondary side voltage waveform of the pulse transformer according to another example
  • Fig. 6 is a schematic circuit diagram of a power supply circuit according to another embodiment
  • FIG. 7 is a circuit diagram of the power supply circuit according to an example of FIG. 6;
  • Fig. 8 is a circuit diagram of a power supply circuit according to another embodiment
  • Fig. 9 is a circuit diagram of a power supply circuit according to another embodiment.
  • FIG. 10 is a circuit diagram of the power supply circuit shown in an example according to FIG. 9;
  • Fig. 11 is a circuit diagram of a power supply circuit according to another embodiment.
  • Fig. 12 is a circuit diagram of a power supply circuit according to another embodiment.
  • FIG. 13 is a circuit diagram of the power supply circuit according to an example of FIG. 12;
  • FIG. 14 is a circuit diagram of the power supply circuit according to another example of FIG. 12;
  • FIG. 15 is a circuit diagram of the power supply circuit according to another example of FIG. 12.
  • the terms “installed”, “connected”, “connected”, “fixed” and other terms should be understood in a broad sense, for example, it may be a fixed connection or a detachable connection. , Or integrated; it can be mechanically connected, or electrically connected, or can communicate with each other; it can be directly connected, or indirectly connected through an intermediate medium, it can be the internal communication of two components or the interaction between two components.
  • installed e.g., it may be a fixed connection or a detachable connection. , Or integrated; it can be mechanically connected, or electrically connected, or can communicate with each other; it can be directly connected, or indirectly connected through an intermediate medium, it can be the internal communication of two components or the interaction between two components.
  • first and second are only used for descriptive purposes, and cannot be understood as indicating or implying relative importance or implicitly indicating the number of indicated technical features. Thus, the features defined with “first” and “second” may explicitly or implicitly include one or more of these features. In the description of the present disclosure, “plurality” means at least two, such as two, three, etc., unless otherwise specifically defined.
  • the present disclosure proposes a power supply circuit and a charging device.
  • the charging device may be a charging device, an adapter, etc., for powering electronic devices.
  • the electronic device here can be a smart terminal or a mobile terminal device equipped with a battery-powered system.
  • the electronic device can also include, but is not limited to, such as laptops, mobile phones, e-book readers, smart wearable devices, mobile power sources (such as power banks, travel chargers), e-cigarettes, wireless mice, wireless keyboards, wireless headphones, Bluetooth speakers, etc. Rechargeable electronic equipment with charging function.
  • the charging device includes a power inlet and a power circuit.
  • the power inlet is used to access an AC power source.
  • the charging device converts the AC power into a charging voltage and/or charging current allowed or required by the electronic device.
  • the charging device can work in a voltage following manner. That is, the adapter and the electronic device to be charged perform two-way communication.
  • the adapter adjusts its output voltage and current according to the required charging voltage and charging current feedback from the electronic device, so that the output voltage and current can be directly loaded on the battery of the electronic device , To charge the battery, the electronic device does not need to adjust the charging voltage and charging current again.
  • the normal charging mode means that the adapter outputs a relatively small current value (usually less than 2.5A) or uses a relatively small power (usually less than 15W) to charge the battery in the charging device. In the normal charging mode, it usually takes several hours to fully charge a large capacity battery (such as a 3000 mAh capacity battery).
  • Fast charging mode means that the adapter can output relatively large current (usually greater than 2.5A, such as 4.5A, 5A or even higher) or relatively large power (usually greater than or equal to 15W) to treat the battery in the charging device Charge.
  • the charging speed of the adapter in the fast charging mode is faster, and the charging time required to fully charge the battery of the same capacity can be significantly shortened.
  • FIG. 1 is a circuit structure block diagram of a power supply circuit according to an embodiment.
  • the power supply circuit includes a pulse transformer circuit 1 and a first power conversion circuit 2.
  • the pulse transformer circuit 1 includes a pulse transformer 11 and a switch control circuit 12; the primary winding of the pulse transformer 11 is connected to the power supply and is connected to the switch control circuit 12, and the switch control circuit 12 is used to connect the primary winding
  • the input terminal of the first power conversion circuit 2 is connected to the secondary winding of the pulse transformer, and is used to convert the output voltage of the secondary winding beyond the first preset voltage range.
  • the voltage on the secondary winding of the pulse transformer is transformed into the first preset voltage range and then output.
  • the power source connected to the primary winding of the pulse transformer is an externally connected power source.
  • the direct current power input directly into the primary winding of the pulse transformer winding is chopped and modulated by the pulse transformer to obtain the required voltage on the secondary winding of the pulse transformer.
  • the power supply circuit further includes a rectifier circuit 3; the input end of the rectifier circuit 3 is connected to an AC power source to rectify the AC power; the output end of the rectifier circuit 3 is connected to the first winding of the primary winding of the pulse transformer.
  • the second end of the primary winding of the pulse transformer is connected to the switch control circuit 12.
  • FIG. 2 is a circuit block diagram of a power supply circuit according to an embodiment.
  • Fig. 3 is a circuit diagram of the power supply circuit according to an example of Fig. 2.
  • the rectifier circuit 3 can be a diode rectifier circuit 3, a full-bridge or a half-bridge rectifier circuit 3 to perform full-wave rectification of the AC power supply. According to different conduction devices selected, the rectifier circuit 3 can be an uncontrollable rectifier circuit 3, a semi-controlled rectifier circuit 3, or a fully-controlled rectifier circuit 3. In the uncontrollable rectifier circuit 3, multiple uncontrollable rectifier diodes cooperate to complete the rectification.
  • the semi-controlled rectifier circuit 3 is composed of a mixture of controllable elements and diodes to complete rectification.
  • all rectifier components are controllable (MOS tube, SCR, GTR, GTO, etc.), and the average value and polarity of the output DC voltage of the fully-controlled rectifier circuit 3 can be controlled by the control components. The conduction condition is adjusted.
  • a diode rectifier circuit 3 can be provided.
  • the rectifier diodes in the full-bridge or half-bridge rectifier circuit 3 are replaced by MOS tubes to reduce the loss of electrical energy in the rectifier circuit 3. In this case, the output voltage of the rectifier circuit 3 is increased.
  • the DC power formed by the AC power after being processed by the rectifier circuit 3 is roughly a continuous steamed bread wave.
  • the frequency of the steamed bread wave is roughly 100HZ.
  • a filter circuit can be provided after the rectifier circuit 3 to further smooth the steamed bread wave.
  • the pulse transformer T1 chops and modulates the incoming line of the direct current power supply to obtain the required voltage on the secondary winding of the pulse transformer T1.
  • the pulse transformer T1 circuit 1 includes a pulse transformer T1, an AC-DC power management chip, and a second feedback circuit; the AC-DC power management chip has a switch control terminal SW and a power supply terminal Vin; the primary winding of the pulse transformer T1 The first end of is connected to the output end of the rectifier circuit 3, and the second end of the primary winding is connected to the switch control end SW121 of the AC-DC power management chip.
  • the AC-DC power management chip integrates a switch tube electrically connected to the primary winding of the pulse transformer T1 and a drive circuit that drives the switch tube to turn on and off. By controlling the on or off of the switch tube, the timing of the pulse transformer T1 primary winding to the secondary winding is controlled.
  • the frequency of the switching tube is relatively high (usually above 100k), so through the fast switching of the switching tube, the voltage on the primary coil of the pulse transformer T1 presents a pulsed square wave.
  • the pulse transformer T1 secondary winding outputs a constant voltage, and the specific voltage value is determined by the frequency of the output signal from the SW terminal on the AC-DC power management chip.
  • the switch can also exist independently of the AC-DC power management chip.
  • the first power conversion circuit 2 mentioned in the above embodiment is connected to the secondary winding of the pulse transformer T1, and is used to connect the secondary winding when the voltage output by the secondary winding exceeds the first preset voltage range
  • the voltage on the secondary winding of the pulse transformer T1 is transformed into the first preset voltage range and then output.
  • the above-mentioned preset first voltage range and preset second voltage range are described together.
  • the preset first voltage range has an upper limit value V1 and a lower limit value V2.
  • the voltage difference between the upper limit value V1 and the lower limit value V2 determines the size of the preset first voltage range.
  • the upper limit V1 and the lower limit V2 of the preset first voltage range are different, and there is a relatively obvious voltage difference between the two, as long as the voltage of the secondary winding of the pulse transformer T1 is in the preset first voltage range.
  • the part outside a voltage range can be adjusted to be within the preset first voltage range.
  • the upper limit value V1 and the lower limit value V2 of the preset first voltage range are set to be the same or close to the same.
  • the preset first voltage range can be regarded as a specific preset voltage V3. Therefore, the first power conversion circuit 2 is required to adjust the wavelength band different from the preset voltage value to the preset voltage V3.
  • the setting of the preset first voltage range in FIG. 5 can make the output voltage of the power supply circuit more stable and accurate.
  • the first preset voltage range is a specific voltage value, and at this time, the upper limit and the lower limit of the first preset voltage range are the same.
  • the description of the upper limit value V1 and the lower limit value V2 of the preset voltage is still used for description in conjunction with related embodiments.
  • the first power conversion circuit 2 includes a boosting unit 21, and the boosting unit 21 is used to ensure that the output voltage of the pulse transformer T1 circuit 1 is less than or equal to the first preset voltage. At the lower limit of the range, the voltage on the secondary winding of the pulse transformer T1 that is below the lower limit of the first preset voltage range is increased.
  • the boost unit 21 When the voltage output by the secondary winding of the pulse transformer T1 is lower than the lower limit value V2 of the preset voltage range, the boost unit 21 will start to work to reduce the voltage output by the secondary winding of the pulse transformer T1 below the lower limit of the preset voltage range. The part of the limit value V2 is raised.
  • the boosting unit 21 can boost the voltage output by the secondary winding of the pulse transformer T1 to a specific value, or boost the voltage output by the secondary winding of the pulse transformer T1 according to a specific multiple.
  • the boosting unit 21 includes at least one of a BOOST circuit, a BUCK/BOOST circuit, a charge pump circuit, or a CUK circuit. It is understandable that both the BUCK/BOOST circuit and the charge pump circuit can implement the boost or step-down function as required.
  • any one of BOOST circuit, BUCK/BOOST circuit, charge pump circuit, or CUK circuit, or at least two cascades can be used to increase the boost amplitude.
  • the boosting unit 21 is an uncontrollable circuit. By selecting components such as resistors, capacitors, and inductances with appropriate parameters, the work start threshold can be adjusted. When the work start threshold is set to the lower limit V2 of the preset voltage range Once the output voltage of the rectifier circuit 3 drops to the lower limit value V2 of the preset voltage range, the boost unit 21 will be triggered to work.
  • the boosting unit 21 is a controllable circuit.
  • the unidirectional conduction device included in the boost unit 21 is a MOS transistor; the boost unit 21 and the buck unit 22 also include a first trigger circuit for controlling the MOS transistor to be turned on and off, so that the first trigger circuit
  • the MOS tube can be turned on and off to trigger the boosting unit 21 to work or stop working.
  • FIG. 7 is a circuit diagram of a power supply circuit according to another embodiment.
  • the diode can be replaced with a MOS tube in the BOOST circuit 21, thereby making the BOOST circuit a controllable circuit.
  • the MOS tube has a small voltage drop
  • replacing the diode in the BOOST circuit with a MOS tube can also reduce the power loss of the BOOST circuit, which is beneficial to increase the output voltage of the BOOST circuit.
  • the diodes in the BUCK/BOOST circuit and the charge pump circuit can also be replaced by MOS tubes.
  • the boost unit 21 further includes a first trigger circuit for controlling the MOS tube to turn on and off; the first trigger circuit is used to control the voltage in the boost unit
  • the MOS tube controls the boost unit to start or stop working.
  • a first capacitor C1 may be provided at the input end of the boosting unit 21, and the first end of the first capacitor C1 is connected to the input end of the first power conversion circuit 2 , The second end of the first capacitor C1 is grounded.
  • the first capacitor C1 increases the voltage on the secondary winding of the pulse transformer T1 through energy storage, thereby supporting the stability of the boost unit 21, and because the voltage at the input end of the second power conversion circuit increases, the second power conversion circuit is increased.
  • a voltage value output from the output terminal of the power conversion circuit 2 helps to stabilize the output voltage of the secondary winding of the pulse transformer T1 above a fixed value, so that the output voltage of the boost unit 21 is further improved.
  • the voltage on the primary winding of the corresponding pulse transformer T1 is also high. Since the turns ratio of the pulse transformer T1 is fixed, the secondary of the pulse transformer T1 is caused. The minimum voltage on the winding is correspondingly higher.
  • the first power conversion circuit 2 further includes a step-down unit 22; the step-down unit 22 is used when the output voltage of the pulse transformer T1 circuit 1 is greater than or equal to the first preset voltage When the upper limit of the range, the voltage on the secondary winding of the pulse transformer T1 circuit 1 that is above the upper limit of the first preset voltage range is reduced; wherein, the upper limit of the first preset voltage range is The limit value is less than the maximum value of the output voltage of the pulse transformer T1 circuit 1.
  • the step-down unit 22 can reduce the voltage output by the secondary winding of the pulse transformer T1 to a specific value, or reduce the voltage output by the secondary winding of the pulse transformer T1 according to a specific multiple.
  • the step-down unit 22 includes at least one of a BUCK circuit, a BUCK/BOOST circuit, a charge pump circuit, or a CUK circuit.
  • any one of BOOST circuit, BUCK/BOOST circuit, charge pump circuit or CUK circuit, or at least two cascades can be used to increase the voltage drop amplitude.
  • the step-down unit 22 is an uncontrollable circuit. By selecting components such as resistors, capacitors, and inductors with appropriate parameters, the working start threshold of the step-down unit 22 can be adjusted, and the working start threshold is set to be within the preset voltage range. At the upper limit value V1, once the output voltage of the rectifier circuit 3 rises to the upper limit value V1 of the preset voltage range, the step-down unit 22 will be triggered to work.
  • the step-down unit 22 is a controllable circuit.
  • the unidirectional conduction device included in the step-down unit 22 is a MOS transistor; the step-down unit 22 and the step-down unit 22 also include a second trigger circuit for controlling the turn-on and turn-off of the MOS transistor, so that the first trigger circuit
  • the MOS tube can be turned on and off to trigger the step-down unit 22 to work or stop working. Therefore, in this example, the step-down unit further includes a second trigger circuit for controlling the turn-on and turn-off of the MOS transistor; the second trigger circuit controls the MOS transistor in the step-down unit. The step-down unit starts or stops working.
  • the diode can be replaced with a MOS tube in the BUCK circuit, thereby making the BUCK circuit a controllable circuit.
  • the MOS tube has a small voltage drop
  • replacing the diode in the BUCK circuit with a MOS tube can also reduce the power loss of the BUCK circuit.
  • the diodes in the BUCK/BOOST circuit and the charge pump circuit can also be replaced by MOS tubes.
  • the start and stop time of the step-down unit 22 can be flexibly set according to needs, so that the step-down unit 22 can better cooperate with the operation of the pulse transformer T1.
  • the voltage on the secondary winding of the pulse transformer T1 may be different according to the selected pulse transformer T1 and the power supply. Therefore, in the solution of the present disclosure, the voltage on the secondary winding of the pulse transformer T1 may be selected. Only the step-up unit 21 or the step-down unit 22 is used, and the step-up unit 21 and the step-down unit 22 can also be used at the same time to adjust the voltage value on the secondary winding of the pulse transformer T1 to within the second preset voltage range.
  • FIG. 9 is a circuit diagram of a power supply circuit according to another embodiment.
  • the first power conversion circuit 2 uses the boosting unit 21 and the bucking unit 22 at the same time, and the boosting unit 21 and the bucking unit 22 are connected in parallel.
  • the boosting unit 21 may be a circuit with only a boosting function, such as a BOOST circuit, or a BUCK/BOOST circuit, a charge pump circuit, etc. that integrates boosting and bucking functions.
  • the step-up unit 21 is a BOOST circuit
  • the step-down unit 22 is a BUK circuit.
  • the boost unit 21 is a BOOST circuit
  • the buck unit 22 is a BUCK/BOOST circuit
  • the boost unit 21 is a BUCK/BOOST circuit
  • the buck unit 22 is a BUK circuit.
  • the corresponding circuit operation can be selected according to the output voltage of the rectifier circuit 3. .
  • the efficiency of the BUK circuit is higher, and when the voltage of 100V is reduced by 50V, the efficiency of the BUCK/BOOST circuit is higher. Therefore, when the output voltage range of the rectifier circuit 3 is about 100V, the BUCK/BOOST circuit can be selected to work.
  • the first power conversion circuit 2 includes at least one of a BUCK/BOOST circuit or a charge pump circuit; the BUCK/BOOST circuit includes a boost unit 21 and a buck unit 22; and the charge pump circuit includes a boost unit 21 and the step-down unit 22; in the case that the first power conversion circuit 2 includes a BUCK/BOOST circuit and a charge pump circuit, the BUCK/BOOST circuit and the charge pump circuit are connected in parallel.
  • the first power conversion circuit 2 may include only a BUCK/BOOST circuit, only a charge pump circuit, or both a BUCK/BOOST circuit and a charge pump circuit, and the two are connected in parallel.
  • the first power conversion circuit 2 since the first power conversion circuit 2 includes both a boosting unit 21 and a step-down unit 22, the ability to adapt to the power source is improved. For example, when the device to be charged supports PD charging, the charging voltage required by the device to be charged will change during the charging process. Therefore, the first power conversion circuit 2 can increase the voltage of the secondary winding of the pulse transformer T1 or decrease the voltage of the secondary winding of the pulse transformer T1 according to the voltage required by the device to be charged, so as to provide the voltage required by the device to be charged.
  • the power supply circuit further includes an output control circuit 5, the output control circuit 5 includes a feedback circuit and a PWM control chip; the PWM control chip includes Feedback receiving end and control end; one end of the feedback circuit is connected to the output end of the first power conversion circuit 2, and the other end of the feedback circuit is connected to the feedback receiving end of the PWM control chip; the PWM control The control terminal of the chip is connected to the first power conversion circuit 2 to control the output voltage of the first power conversion circuit 2; the PWM control chip is used to adjust the output of the control terminal according to the feedback result of the feedback circuit , To stabilize the output voltage of the first power supply circuit.
  • the feedback circuit makes the first power conversion circuit 2 a closed loop operating circuit.
  • the booster circuit and the bucker circuit generally have a switch tube for adjusting the output voltage.
  • the PWM control chip adjusts the duty cycle of the switch tube to adjust the output voltage of the boost circuit and the buck circuit. When the PWM control chip receives the feedback voltage of the feedback circuit is too large, it will adjust the duty cycle of the switch tube to reduce the output voltage of the first power conversion circuit 2. Similarly, when the PWM control chip receives that the feedback voltage of the feedback circuit is too small, it will adjust the duty cycle of the switch tube to increase the output voltage of the first power conversion circuit 2. This ensures that the output voltage of the first power conversion circuit 2 is stable.
  • the feedback loop is longer.
  • the device to be charged needs to communicate with the AC-DC power management chip in the adapter, and the AC-DC power management chip needs to obtain output voltage information through a feedback stage.
  • the signal transmission path in the adjustment loop is: the device to be charged sends the desired voltage -> signal isolation conversion chip -> AC-DC power management chip -> adjusts the duty cycle of the PWM signal -> obtains the sampling voltage from the pulse transformer T1 feedback winding -> Adjust the duty cycle of the PWM signal -> get the output stable voltage. It can be seen that the feedback loop is longer and the real-time performance of voltage adjustment is poor.
  • the adjustment accuracy is poor, and the feedback voltage signal is returned through the dedicated feedback winding, but the pulse transformer T1 has defects such as leakage inductance and magnetic leakage.
  • the primary winding, secondary winding, and feedback winding cannot ideally realize the proportional relationship strictly determined by the turns ratio.
  • the output voltage of the secondary winding is controlled by returning the sampled voltage signal through the dedicated feedback winding, and the voltage regulation accuracy is poor.
  • the overall circuit occupies a large volume.
  • the control circuit (such as AC-DC power management chip) is mainly on the primary side of the pulse transformer T1, but the primary side voltage is relatively high, so the components on the primary side of the pulse transformer T1 require a higher withstand voltage
  • the packaging of high withstand voltage devices is usually larger, resulting in a larger overall circuit volume.
  • a resistor divider is often used on the secondary output side, and the voltage feedback signal of the secondary winding of the pulse transformer T1 is transmitted to the AC-DC power management chip through a comparator and an optocoupler to regulate the pulse transformer T1.
  • optocouplers need to be used as primary and secondary side signal isolation devices, and the feedback signal is used to return to the control chip. The path is long, and the speed of the optocoupler cannot meet the higher response requirements of the power supply circuit.
  • an output control circuit 5 with a feedback circuit and a PWM control chip is provided on the secondary side of the pulse transformer T1, and the feedback circuit directly uses the voltage on the secondary winding of the pulse transformer T1 to make the PWM control chip
  • the output voltage of the first power conversion circuit 2 is adjusted according to the feedback result. Therefore, in this embodiment, the feedback loop does not need to return the feedback signal to the primary side of the pulse transformer T1, but can be directly transmitted on the secondary side of the pulse transformer T1. Therefore, the signal transmission loop is greatly shortened and the voltage adjustment is real-time.
  • the device to be charged can directly communicate with the secondary circuit of the pulse transformer T1 to achieve Voltage adjustment request, etc., without using optocouplers and other devices to return feedback signals or voltage adjustment signals to the primary side; therefore, the technical solution of this embodiment further saves high and low voltage communication devices and improves the response sensitivity of the feedback loop.
  • the feedback signal of the AC-DC power management chip may not be connected to the feedback signal, that is, the AC-DC power management chip does not need to adjust the voltage on the secondary winding of the pulse transformer T1 according to the feedback signal.
  • the PWM control chip further includes a communication terminal; the communication terminal is used to communicate with the device to be powered to receive the The power supply voltage required by the device to be powered; the PWM control chip is used to control the output voltage of the first power supply circuit according to the communication result with the device to be powered.
  • the device to be charged When the device to be charged and the charging device support the PD charging protocol and the private charging protocol, during the charging process, the device to be charged communicates with the PWM control chip, and the device to be charged will send the required charging voltage and charging current to the PWM control chip.
  • the PWM control chip further controls the first power conversion circuit 2 to adjust the output voltage to meet the charging requirements of the device to be charged.
  • FIG. 12 is a circuit diagram of a power supply circuit according to another embodiment.
  • the power supply circuit is provided to further include the second power conversion circuit 4.
  • the input terminal of the second power conversion circuit 4 is connected to the output terminal of the rectifier circuit 3, and the output terminal of the second power conversion circuit is connected to the primary winding of the pulse transformer T1; the second power conversion circuit is used for When the voltage output by the rectifier circuit 3 exceeds the preset second voltage range, the voltage output by the rectifier circuit 3 is adjusted to fall within the preset second voltage range.
  • the explanation of the second preset voltage range can refer to the explanation of the first preset voltage range mentioned above.
  • the second power conversion circuit can replace the filter circuit mentioned in the above embodiment.
  • the filter circuit needs to use an inductor with a larger inductance value and a capacitor with a larger capacitance value, so the volume of the inductance and capacitor in the filter circuit is relatively large. Therefore, in order to reduce the size of the charging device and facilitate the miniaturization of the charging device, the second power conversion circuit is used in this embodiment to adjust the output voltage of the rectifier circuit 3. Due to the circuit structure of the second power conversion circuit, it can be used Inductances with smaller inductance values and capacitors with smaller capacitances are beneficial to reduce the volume of inductances and capacitors, which in turn are beneficial to reduce the volume of charging equipment.
  • the voltage waveform output by the rectifier circuit 3 is roughly a steamed bread wave, and the voltage amplitude varies between the highest voltage and the lowest voltage, and the lowest voltage may be close to 0V. It can be understood that when the voltage output by the rectifier circuit 3 is close to 0V, the primary winding of the pulse transformer T1 cannot start to work, which makes the secondary output of the pulse transformer T1 unstable.
  • the second power conversion circuit includes a boosting unit 21, and the boosting unit 21 is used to boost the rectifying circuit when the output voltage of the rectifying circuit 3 is less than or equal to the lower limit V2 of the preset second voltage range 3.
  • the output voltage wherein, the lower limit value V2 of the preset second voltage range is greater than the minimum operating voltage of the pulse transformer T1 circuit 1.
  • the minimum operating voltage of the pulse transformer T1 circuit 1 used varies. Those skilled in the art can know the minimum operating voltage of the pulse transformer T1 circuit 1 used through experience or through experiments. The lowest operating voltage of the pulse transformer T1 and the AC-DC power management chip is generally the lowest operating voltage of the pulse transformer T1 circuit 1.
  • the boost unit 21 When the voltage output by the rectifier circuit 3 is lower than the lower limit of the preset second voltage range, the boost unit 21 will start to work to reduce the voltage output by the rectifier circuit 3 below the lower limit of the preset second voltage range. Part of the elevation.
  • the primary side boosting unit 41 can boost the voltage output by the rectifier circuit 3 to a specific value, or boost the voltage output by the rectifier circuit 3 according to a specific multiple.
  • the boosting unit 21 includes one or more of a primary-side boosting unit 41, a plurality of cascaded primary-side boosting units 41, a BUCK/BOOST circuit, and a charge pump circuit. It is understandable that both the BUCK/BOOST circuit and the charge pump circuit can implement the boost or step-down function as required.
  • the primary side boosting unit 41 of one unit may be a BOOST circuit. When multiple primary side boosting units 41 are cascaded, the boosting amplitude can be increased.
  • the boosting unit 21 is an uncontrollable circuit. By selecting components such as resistors, capacitors, and inductances with appropriate parameters, the work start threshold can be adjusted, and the work start threshold is set to the lower limit of the preset second voltage range. At this time, once the output voltage of the rectifier circuit 3 drops to the lower limit of the preset second voltage range, the boost unit 21 will be triggered to work.
  • the boosting unit 21 is a controllable circuit.
  • the unidirectional conduction device included in the boost unit 21 is a MOS tube; the boost unit 21 and the primary side boost unit 41 further include a first trigger circuit for controlling the MOS tube to be turned on and off, thereby first triggering The circuit can be turned on and off by the MOS tube, thereby triggering the boosting unit 21 to work or stop working.
  • the diode can be replaced with a MOS tube in the BOOST circuit, thereby making the BOOST circuit a controllable circuit.
  • the MOS tube has a small voltage drop
  • replacing the diode in the BOOST circuit with a MOS tube can also reduce the power loss of the BOOST circuit, which is beneficial to increase the output voltage of the BOOST circuit.
  • the diodes in the BUCK/BOOST circuit and the charge pump circuit can also be replaced by MOS tubes.
  • the start and stop time of the boost unit 21 can be flexibly set according to needs, so that the boost unit 21 can better cooperate with the rectifier circuit 3 and the pulse transformer T1 circuit 1. , So that the voltage processed by the boosting unit 21 can fully meet the working voltage of the pulse transformer T1 circuit 1.
  • a second capacitor C2 may be provided at the input end of the primary side boost unit 41.
  • the first end of the second capacitor C2 is connected to the second power conversion circuit.
  • the input terminal is connected, and the second terminal of the second capacitor C2 is grounded.
  • the second capacitor C2 increases the voltage at the input terminal of the second power conversion circuit by storing energy, thereby supporting the stability of the primary side boost unit 41, and because the voltage at the input terminal of the second power conversion circuit increases,
  • the voltage value output from the output terminal of the second power conversion circuit is beneficial to stabilize the input voltage of the primary winding of the pulse transformer T1 above a fixed value and reduce the working dead zone of the pulse transformer T1.
  • the second power conversion circuit further includes a primary side step-down unit 42; the primary side step-down unit 42 is used for when the output voltage of the rectifier circuit 3 is greater than or equal to the upper limit of the preset second voltage range, The output voltage of the rectifier circuit 3 is reduced; wherein the upper limit of the preset second voltage range is less than the maximum value of the output voltage of the rectifier circuit 3.
  • the primary side step-down unit 42 When the voltage output by the rectifier circuit 3 is higher than the lower limit of the preset second voltage range, the primary side step-down unit 42 will start to work to increase the voltage output by the rectifier circuit 3 higher than the upper limit of the preset second voltage range The value part is raised.
  • the primary side boosting unit 41 can reduce the voltage output by the rectifier circuit 3 to a specific value, or the voltage output by the rectifier circuit 3 can be reduced by a specific multiple.
  • the primary side step-down unit 42 includes one or more of a unit primary side step-down unit 42, a plurality of cascaded primary side step-down units 42, a BUCK/BOOST circuit, and a charge pump circuit.
  • the primary side step-down unit 42 of one unit may be a BUCK circuit.
  • the primary side step-down unit 42 is an uncontrollable circuit. By selecting components such as resistors, capacitors, and inductances with appropriate parameters, the working start threshold of the primary side step-down unit 42 can be adjusted, and the working start threshold is set to a preset value. When the upper limit value V1 of the second voltage range is set, once the output voltage of the rectifier circuit 3 rises to the upper limit value V1 of the preset second voltage range, the primary side step-down unit 42 will be triggered to work.
  • the primary side step-down unit 42 is a controllable circuit.
  • the unidirectional conduction device included in the primary side step-down unit 42 is a MOS transistor; the primary side step-down unit 42 and the primary side step-down unit 42 also include a second trigger circuit for controlling the turn-on and turn-off of the MOS transistor.
  • the first trigger circuit can trigger the primary side step-down unit 42 to work or stop working by turning on and off the MOS transistor.
  • the diode can be replaced with a MOS tube in the BUCK circuit, thereby making the BUCK circuit a controllable circuit.
  • the MOS tube has a small voltage drop
  • replacing the diode in the BUCK circuit with a MOS tube can also reduce the power loss of the BUCK circuit.
  • the diodes in the BUCK/BOOST circuit and the charge pump circuit can also be replaced by MOS transistors.
  • the start and stop time of the primary side step-down unit 42 can be flexibly set according to needs, so that the primary side step-down unit 42 can interact with the rectifier circuit 3 and the pulse transformer T1. Circuit 1 is better matched.
  • the output waveform of the rectifier circuit 3 may be correspondingly different. Therefore, in the solution of the present disclosure, only the primary side boost unit 41 or the primary side step-up unit 41 can be selected according to the output waveform of the rectifier circuit 3.
  • the voltage unit 42 may also use the primary side boost unit 41 and the primary side step-down unit 42 at the same time to preset the output voltage value adjustment value of the rectifier circuit 3 within the second voltage range.
  • the power circuit is divided into a forward circuit and a flyback circuit.
  • the pulse transformer T1 can be a forward pulse transformer T1 or a flyback pulse transformer T1.
  • the forward pulse transformer T1 has higher requirements for voltage stability on the primary winding of the pulse transformer T1.
  • the voltage on the primary winding of the pulse transformer T1 is relatively stable through the arrangement of the step-up unit 21 and the primary-side step-down unit 42, which is suitable for both the forward pulse transformer T1 and the flyback pulse transformer T1.
  • the pulse transformer T1 adopts the forward pulse transformer T1 the stability of the output voltage on the negative winding of the pulse transformer T1 can be improved, and the power output capability can be improved, so that the power supply circuit can be used in high-power applications.
  • the power supply circuit uses the boosting unit 21 and the primary side buck unit 42 at the same time, and the boosting unit 21 and the primary side buck unit 42 are connected in parallel.
  • the boosting unit 21 may be a circuit with only a boosting function, such as a BOOST circuit, or a BUCK/BOOST circuit, a charge pump circuit, etc. that integrates boosting and bucking functions.
  • the step-up unit 21 is a BOOST circuit
  • the primary side step-down unit 42 is a BUK circuit.
  • the boost unit 21 is a BOOST circuit
  • the primary side buck unit 42 is a BUCK/BOOST circuit
  • the boost unit 21 is a BUCK/BOOST circuit
  • the primary side buck unit 42 is a BUK Circuit.
  • the corresponding circuit operation can be selected according to the output voltage of the rectifier circuit 3. .
  • the efficiency of the BUK circuit is higher, and when the voltage of 100V is reduced by 50V, the efficiency of the BUCK/BOOST circuit is higher. Therefore, when the output voltage range of the rectifier circuit 3 is about 100V, the BUCK/BOOST circuit can be selected to work.
  • the second power conversion circuit includes at least one of a BUCK/BOOST circuit or a charge pump circuit; the BUCK/BOOST circuit includes a boost unit 21 and a primary side buck unit 42; and the charge pump circuit includes a boost
  • the unit 21 is connected to the primary side step-down unit 42; when the second power conversion circuit includes a BUCK/BOOST circuit and a charge pump circuit, the BUCK/BOOST circuit and the charge pump circuit are connected in parallel.
  • the second power conversion circuit may include only the BUCK/BOOST circuit, only the charge pump circuit, or both the BUCK/BOOST circuit and the charge pump circuit, and the two are connected in parallel.
  • a second power conversion circuit is provided to adjust the voltage output by the rectifier circuit 3 to fall within the preset second voltage range when the voltage output by the rectifier circuit 3 exceeds the preset second voltage range, thereby effectively reducing or Eliminate the working dead zone of the pulse transformer T1 circuit 1, so that the secondary power conversion can obtain sufficient voltage supply at every moment, so that the pulse transformer T1 circuit 1 can output a continuous and stable voltage to supply the first power conversion circuit 2 Work to improve the accuracy of the output voltage of the power supply circuit.
  • the first power conversion circuit 2 and the second power conversion circuit have multiple coordination modes.
  • the primary side boost unit 41 of the second power conversion can be used to cooperate with the boost unit 21 of the first power conversion circuit 2 , In order to improve the overall boost range of the power supply circuit.
  • the primary side step-down unit 42 of the second power conversion can be used to cooperate with the step-down unit 22 of the first power conversion circuit 2 , In order to improve the overall voltage reduction range of the power supply circuit.
  • the primary side step-down unit 42 of the second power conversion can be used to cooperate with the step-down unit 22 of the first power conversion circuit 2 , In order to improve the overall voltage reduction range of the power supply circuit.
  • the primary side boosting unit 41 of the second power conversion can be used to cooperate with the step-down unit 22 of the first power conversion circuit 2.
  • the primary side step-up unit 41 raises the primary side voltage of the pulse transformer T1 first, so that the secondary side voltage of the pulse transformer T1 is also raised accordingly, and the step-up unit only requires the step-down unit 22 of the first power conversion circuit 2 to work. That is, the voltage on the secondary side of the pulse transformer T1 can be converted to the required voltage of the device to be charged. Therefore, in this example, there is no need to provide the boosting unit 21 in the first power conversion circuit 2, thereby simplifying the circuit structure.
  • the primary side step-down unit 42 of the second power conversion can be used to cooperate with the step-up unit 21 of the first power conversion circuit 2.
  • the primary side step-down unit 42 first reduces the voltage on the primary side of the pulse transformer T1, so that the voltage on the secondary side of the pulse transformer T1 is also reduced accordingly, and is raised to the point where only the step-up unit 21 of the first power conversion circuit 2 is required to work.
  • the voltage on the secondary side of the pulse transformer T1 is transformed to the required voltage of the device to be charged. Therefore, in this example, there is no need to provide the step-down unit 22 in the first power conversion circuit 2, thereby simplifying the circuit structure.

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Abstract

本公开提供了一种电源电路及充电设备。电源电路包括脉冲变压器电路、第一电源变换电路。脉冲变压器电路包括脉冲变压器以及开关控制电路；所述脉冲变压器的初级绕组供电源连接，且与所述开关控制电路连接，所述开关控制电路用于将所述初级绕组上的电压调制成为脉冲电压；所述第一电源变换电路的输入端与所述脉冲变压器的次级绕组连接，用于在所述次级绕组输出的电压超出第一预设电压范围时，将所述脉冲变压器的次级绕组上的电压变换至所述第一预设电压范围内后输出。公开的能够提高充电设备与不同供电电源的适配性，以保证输出电压的可调范围。

Description

电源电路及充电设备
交叉引用
本公开要求于2020年3月12日提交的申请号为202010172177.5名称为“电源电路及充电设备”的中国专利申请的优先权，该中国专利申请的全部内容通过引用全部并入本文。
技术领域
本公开涉及充电领域，特别涉及一种电源电路及充电设备。
背景技术
随着充电技术的发展，需要充电设备具有不同等级的电压输出能力。例如当充电设备为一个支持PD协议的手机充电时，需要充电设备输出的电压为连续可调的直流电。
相关技术中，充电设备内通常配有脉冲变压器，以通过PWM控制芯片脉冲变压器初级侧的电压进行脉冲调制，从而调节脉冲变压器输出端的电压。然而由于脉冲变压器的匝数比一般是固定的，因此要实现脉冲变压器输出端输出连续可调的直流电，则需要供电电源电压在一定的范围内，因此这种方案对供电电源的要求较高，一旦供电电源电压发生较大波动或电源电压过低、过高，则将造成脉冲变压器输出端的电压可调范围受限。
在所述背景技术部分公开的上述信息仅用于加强对本公开的背景的理解，因此它可以包括不构成对本领域普通技术人员已知的现有技术的信息。
公开内容
本公开的一个目的在于提高充电设备与不同供电电源的适配性，以保证输出电压的可调范围。
为解决上述技术问题，本公开采用如下技术方案：
根据本公开的一个方面，本公开提供一种电源电路，包括：
变压器电路，包括脉冲变压器以及开关控制电路；所述脉冲变压器的初级绕组与电源连接，且与所述开关控制电路连接，所述开关控制电路用于将所述初级绕组上的电压调制成为脉冲电压；
第一电源变换电路，所述第一电源变换电路的输入端与所述变压器的次级绕组连接，用于在所述次级绕组输出的电压超出第一预设电压范围时，将所述变压器的次级绕组上的电压变换至所述第一预设电压范围内后输出。
根据本公开的另一个方面公开一种充电设备，包括电源接入口，以及电源电路，所述 电源接入口用于接入电源。
本公开技术方案中，通过在变压器电路的次级侧设置第一电源变换电路，能够在因电源电压过高、过低或者待供电设备所需求较高、较低的供电电压时，所述第一电源变换电路能够将脉冲变压器次级绕组上的电压进行相应变换以满足待供电设备的供电需求。由此本公开技术方案提高了与不同供电电源的适配性，以保证输出电压的可调范围。
应当理解的是，以上的一般描述和后文的细节描述仅是示例性的，并不能限制本公开。
附图说明
通过参照附图详细描述其示例实施例，本公开的上述和其它目标、特征及优点将变得更加显而易见。
图1是根据一实施例示出的电源电路的电路结构框图；
图2是根据另一实施例示出的电源电路的电路结构框图；
图3是根据图2一示例示出的电源电路的电路图；
图4是根据一示例示出的预设电压范围在脉冲变压器次级侧电压波形上所对应区间；
图5是根据另一示例示出的预设电压范围在脉冲变压器次级侧电压波形上所对应区间；
图6是根据另一实施例示出的电源电路的电路示意图；
图7是根据图6一示例示出的电源电路的电路示意图；
图8是根据另一实施例示出的电源电路的电路示意图；
图9是根据另一实施例示出的电源电路的电路示意图；
图10是根据图9一示例示出的电源电路的电路示意图；
图11是根据另一实施例示出的电源电路的电路示意图；
图12是根据另一实施例示出的电源电路的电路示意图；
图13是根据图12一示例示出的电源电路的电路示意图；
图14是根据图12另一示例示出的电源电路的电路示意图；
图15是根据图12另一示例示出的电源电路的电路示意图。
具体实施方式
现在将参考附图更全面地描述示例实施方式。然而，示例实施方式能够以多种形式实施，且不应被理解为限于在此阐述的范例；相反，提供这些实施方式使得本公开将更加全面和完整，并将示例实施方式的构思全面地传达给本领域的技术人员。附图仅为本公开的示意性图解，并非一定是按比例绘制。图中相同的附图标记表示相同或类似的部分，因而 将省略对它们的重复描述。
此外，所描述的特征、结构或特性可以以任何合适的方式结合在一个或更多实施方式中。在下面的描述中，提供许多具体细节从而给出对本公开的实施方式的充分理解。然而，本领域技术人员将意识到，可以实践本公开的技术方案而省略所述特定细节中的一个或更多，或者可以采用其它的方法、组元、装置、步骤等。在其它情况下，不详细示出或描述公知结构、方法、装置、实现、材料或者操作以避免喧宾夺主而使得本公开的各方面变得模糊。
在本公开中，除非另有明确的规定和限定，术语“安装”、“相连”、“连接”、“固定”等术语应做广义理解，例如，可以是固定连接，也可以是可拆卸连接，或成一体；可以是机械连接，也可以是电连接或可以互相通讯；可以是直接相连，也可以通过中间媒介间接相连，可以是两个元件内部的连通或两个元件的相互作用关系。对于本领域的普通技术人员而言，可以根据具体情况理解上述术语在本公开中的具体含义。
此外，术语“第一”、“第二”仅用于描述目的，而不能理解为指示或暗示相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括一个或者更多个该特征。在本公开的描述中，“多个”的含义是至少两个，例如两个，三个等，除非另有明确具体的限定。
以下结合本说明书的附图，对本公开的较佳实施方式予以进一步地详尽阐述。
本公开提出一种电源电路与充电设备，充电设备可以是充电设备、适配器等，以用于为电子设备供电。在此电子设备可以是配置有电池供电系统的智能终端、移动终端设备。该电子设备还可以包括但不限于诸如笔记本电脑、手机、电子书阅读器、智能穿戴设备、移动电源(如充电宝、旅充)、电子烟、无线鼠标、无线键盘、无线耳机、蓝牙音箱等具有充电功能的可充电电子设备。
充电设备包括电源接入口，以及电源电路，电源接入口用于接入交流电源，充电设备将交流电源转换成电子设备所允许或所需求的充电电压和/或充电电流。
充电设备可以采用电压跟随的方式工作。即适配器和待充电的电子设备进行双向通信，适配器根据电子设备反馈所需的充电电压和充电电流，从而调整自身输出的电压和电流，使得输出的电压和电流可以直接加载到电子设备的电池上，为电池充电，电子设备无需再次再调整充电电压和充电电流。
对电子设备的电池的充电模式大致有“普通充电模式”、“快速充电模式”。普通充电模式是指适配器输出相对较小的电流值(通常小于2.5A)或者以相对较小的功率(通常小于15W)来对待充电设备中的电池进行充电。在普通充电模式下想要完全充满一较大容量电池(如3000毫安时容量的电池)，通常需要花费数个小时的时间。快速充电模式则是指适配器能够输出相对较大的电流(通常大于2.5A，比如4.5A，5A甚至更高)或者以相对较大的功率(通常大于等于15W)来对待充电设备中的电池进行充电。相较于普通充电模式而言，适配器在快速充电模式下的充电速度更快，完全充满相同容量电池所需要的 充电时间能够明显缩短。
请参阅图1，图1是根据一实施例示出的电源电路的电路结构框图。在本实施例中，电源电路设置在充电设备内部。电源电路包括脉冲变压器电路1、第一电源变换电路2。脉冲变压器电路1包括脉冲变压器11以及开关控制电路12；所述脉冲变压器11的初级绕组供电源连接，且与所述开关控制电路12连接，所述开关控制电路12用于将所述初级绕组上的电压调制成为脉冲电压；所述第一电源变换电路2的输入端与所述脉冲变压器的次级绕组连接，用于在所述次级绕组输出的电压超出第一预设电压范围时，将所述脉冲变压器的次级绕组上的电压变换至所述第一预设电压范围内后输出。
与脉冲变压器的初级绕组连接的电源为外部接入的电源。例如直接在脉冲变压器绕组的初级绕组输入的直流电源，利用脉冲变压器对该直流电源进线斩波调制，从而在脉冲变压器次级绕组上获得所需要的电压。在一实施例中，所述电源电路还包括整流电路3；所述整流电路3的输入端供交流电源连接，以整流所述交流电源；整流电路3的输出端与脉冲变压器初级绕组的第一端连接，脉冲变压器初级绕组的第二端与开关控制电路12连接。
请参阅图2和图3，图2是根据一实施例示出的电源电路的电路框图。图3是根据图2一示例示出的电源电路的电路图。整流电路3可以为二极管整流电路3，全桥、半桥整流电路3以对交流电源进行全波整流。根据所选用的导通器件的不同，整流电路3可以是不可控整流电路3、半控式整流电路3、全控式整流电路3。在不可控整流电路3中完全是由多个不可控的整流二极管配合以完成整流。半控整流电路3由可控元件和二极管混合组成，以完成整流。在全控式整流电路3中，所有的整流元件都是可控的(MOS管、SCR、GTR、GTO等)，全控式整流电路3输出直流电压的平均值及极性可以通过控制元件的导通状况而得到调节。
在本实施例中，可以设置二极管整流电路3，全桥、或半桥整流电路3中的整流二极管采用MOS管来替换，以减小电能在整流电路3中的损耗，在同样的输入电能的情况下，抬高整流电路3的输出电压。
交流电能在经过整流电路3的处理后所形成的直流电能大致为连续的馒头波，在一示例中，馒头波的频率大致为100HZ。在整流电路3后还可以设置滤波电路，以进一步平滑馒头波。脉冲变压器T1对该直流电源进线斩波调制，从而在脉冲变压器T1次级绕组上获得所需要的电压。
在一实施例中，脉冲变压器T1电路1包括脉冲变压器T1、AC-DC电源管理芯片、第二反馈电路；AC-DC电源管理芯片具有开关控制端SW、供电端Vin；脉冲变压器T1的初级绕组的第一端与整流电路3的输出端连接，初级绕组的第二端与AC-DC电源管理芯片的开关控制端SW121连接。在该实施例中，AC-DC电源管理芯片内集成了与脉冲变压器T1初级绕组电连接的开关管以及驱动该开关管导通关断的驱动电路。通过控制该开关管的导通或关断，以控制脉冲变压器T1初级绕组向次级绕组传输电能的时机。开关管 的频率较高(通常为100k以上)，因此通过开关管的快速切换，脉冲变压器T1初级线圈上的电压呈现为脉冲方波。脉冲变压器T1次级绕组输出恒定的电压，具体的电压值大小由AC-DC电源管理芯片上的SW端输出信号的频率决定。在另一实施例中，该开关也可以独立于AC-DC电源管理芯片而存在。
在下述实施例中，将对第一电源变换电路2的实施例进行说明。
在上述实施例中所提到的第一电源变换电路2与所述脉冲变压器T1的次级绕组连接，用于在所述次级绕组输出的电压超出第一预设电压范围时，将所述脉冲变压器T1的次级绕组上的电压变换至所述第一预设电压范围内后输出。在一并对上述预设第一电压范围和预设第二电压范围(统称为预设第二电压范围)进行说明。
请参阅图4和图5。在图4和图5中分别体现了预设第一电压范围的两个实施例。预设第一电压范围具有上限值V1和下限值V2，当上限值V1和下限值V2之间的电压差值决定了预设第一电压范围的大小。在图4中，预设第一电压范围的上限值V1、下限值V2不相同，且两者之间具有一较为明显的电压差，只要脉冲变压器T1次级绕组电压位于该预设第一电压范围之外的部分调整到预设第一电压范围之内即可。在图4中，设置预设第一电压范围的上限值V1、下限值V2相同或接近相同，此时可以将预设第一电压范围看做一特定的预设电压V3。因此需要第一电源变换电路2将与预设电压值不同的波段调整至该预设电压V3。很明显，图5中预设第一电压范围的设置方式能够使得电源电路的输出的电压更为稳定精准。
由于第一电源变换电路2的输出端即为整个电源电路的输出端，精准稳定的输出能够更好的配合待供电设备的充电需求。因此，在一实施例中，第一预设电压范围为一特定的电压值，此时第一预设电压范围的上限值和下限值相同。在下述实施例中，为了便于理解，仍旧以预设电压的上限值V1、下限值V2的表述结合相关实施例进行说明。
请参阅图6，在一实施例中，当电源的电压较低时，相应的脉冲变压器T1初级绕组上的电压也较低，由于脉冲变压器T1的匝数比固定，因此造成脉冲变压器T1次级绕组上的最高电压也相应较低。因此本实施例中，设置所述第一电源变换电路2包括升压单元21，所述升压单元21用于在所述脉冲变压器T1电路1的输出电压小于或等于所述第一预设电压范围的下限值时，升高位于第一预设电压范围的下限值之下的所述脉冲变压器T1次级绕组上的电压。
当脉冲变压器T1次级绕组输出的电压低于预设电压范围的下限值V2时，升压单元21会开始工作，以将脉冲变压器T1次级绕组输出的电压低于预设电压范围的下限值V2的部分进行抬高。
升压单元21可以将脉冲变压器T1次级绕组输出的电压提升到一个特定值，也可以脉冲变压器T1次级绕组输出的电压按照特定的倍数抬升。将升压单元21包括BOOST电路、BUCK/BOOST电路、电荷泵电路或CUK电路中的至少一个。可以理解的是，BUCK/BOOST电路、电荷泵电路均是可以根据需要来实现升压或降压功能。在此可以采用BOOST电路、 BUCK/BOOST电路、电荷泵电路或CUK电路中的任意一个，或者至少两个级联，以增大升压幅度。
在一示例中，升压单元21为不可控电路，通过选择合适参数的电阻、电容、电感等元器件，能够调节工作启动阈值，工作启动阈值设定为预设电压范围的下限值V2时，一旦整流电路3的输出电压降低至预设电压范围的下限值V2，便会触发升压单元21工作。
在另一示例中升压单元21为可控电路。升压单元21中所包括的单向导通器件为MOS管；升压单元21与降压单元22还包括用于控制MOS管导通和关断的第一触发电路，由此第一触发电路便可以通过MOS管的导通和关断，从而触发升压单元21工作或停止工作。
请参阅图7，图7是根据另一实施例示出的电源电路的电路示意图。以升压单元21为BOOST电路为例，在BOOST电路21中可以将二极管替换成MOS管，由此使得BOOST电路为可控电路。另一方面，由于MOS管具有较小的压降，因此将BOOST电路中的二极管替换为MOS管还可以减小BOOST电路的电能损耗，有利于提高BOOST电路输出电压。对于其他的升压单元21，例如BUCK/BOOST电路、电荷泵电路中的二极管也可以采用MOS管进行替换。
当升压单元21为可控电路时，可以根据需要灵活的设置升压单元21的开始工作和停止工作的时间，使得升压单元21能够与脉冲变压器T1的工作更好的配合，以使得经过升压单元21处理后的电压能够完全满足脉冲变压器T1电路1的工作电压。因此在一实施例中，所述升压单元21还包括用于控制所述MOS管导通和关断的第一触发电路；所述第一触发电路用于通过控制所述升压单元中的MOS管以控制所述升压单元开始或停止工作。
在一实施例中，为了进一步升压单元21输出的电压，可以在升压单元21的输入端设置第一电容C1，第一电容C1的第一端与第一电源变换电路2的输入端连接，第一电容C1的第二端接地。第一电容C1通过储能从而升高脉冲变压器T1次级绕组上的电压，从而支持了升压单元21工作的稳定性，并且由于第二电源变换电路输入端的电压升高，从而升高了第一电源变换电路2输出端输出的电压值，有利于将脉冲变压器T1的次级绕组的输出电压稳定在一个定值之上，从而使得升压单元21的输出电压进一步得到提高。
请参阅图8，在一实施例中，当电源的电压较高时，相应的脉冲变压器T1初级绕组上的电压也较高，由于脉冲变压器T1的匝数比固定，因此造成脉冲变压器T1次级绕组上的最低电压也相应较高。因此本实施例中，所述第一电源变换电路2还包括降压单元22；所述降压单元22用于在所述脉冲变压器T1电路1的输出电压大于或等于所述第一预设电压范围的上限值时，降低位于所述第一预设电压范围的上限值之上的所述脉冲变压器T1电路1次级绕组上的电压；其中，所述第一预设电压范围的上限值小于所述脉冲变压器T1电路1输出电压的最大值。
降压单元22可以将脉冲变压器T1次级绕组输出的电压降低到一个特定值，也可以脉冲变压器T1次级绕组输出的电压按照特定的倍数降低。降压单元22包括BUCK电路、BUCK/BOOST电路、电荷泵电路或CUK电路中的至少一个。在此可以采用BOOST电路、 BUCK/BOOST电路、电荷泵电路或CUK电路中任意一个，或至少两个级联，以增大降压幅度。
在一示例中，降压单元22为不可控电路，通过选择合适参数的电阻、电容、电感等元器件，能够调节降压单元22的工作启动阈值，工作启动阈值设定为预设电压范围的上限值V1时，一旦整流电路3的输出电压升高至预设电压范围的上限值V1，便会触发降压单元22工作。
在另一示例中降压单元22为可控电路。降压单元22中所包括的单向导通器件为MOS管；降压单元22与降压单元22还包括用于控制MOS管导通和关断的第二触发电路，由此第一触发电路便可以通过MOS管的导通和关断，从而触发降压单元22工作或停止工作。因此在该示例中，所述降压单元还包括用于控制所述MOS管导通和关断的第二触发电路；所述第二触发电路通过控制所述降压单元中MOS管以控制所述降压单元开始或停止工作。
以降压单元22为BUCK电路为例，在BUCK电路中可以将二极管替换成MOS管，由此使得BUCK电路为可控电路。另一方面，由于MOS管具有较小的压降，因此将BUCK电路中的二极管替换为MOS管还可以减小BUCK电路的电能损耗。对于其他的降压单元22，例如BUCK/BOOST电路、电荷泵电路中的二极管也可以采用MOS管进行替换。
当降压单元22为可控电路时，可以根据需要灵活的设置降压单元22的开始工作和停止工作的时间，使得降压单元22能够与脉冲变压器T1的工作更好的配合。
可以理解的是，根据选用的脉冲变压器T1以及供电电源的不同，脉冲变压器T1次级绕组上的电压可能会有相应的不同，因此本公开方案中可以根据脉冲变压器T1次级绕组上的电压选择仅使用升压单元21或降压单元22，也可以同时使用升压单元21和降压单元22，以将脉冲变压器T1次级绕组上的电压值调整值第二预设电压范围内。
请参阅图9，图9是根据另一实施例示出的电源电路的电路示意图。在一实施例中，第一电源变换电路2同时使用升压单元21和降压单元22，且升压单元21、降压单元22并联连接。升压单元21可以是仅具有升压功能的电路，例如BOOST电路，也可以是集成了升压和降压功能的BUCK/BOOST电路、电荷泵电路等。
在第一示例中，升压单元21为BOOST电路，降压单元22为BUK电路。在第二示例中，升压单元21为BOOST电路，降压单元22为BUCK/BOOST电路；在第三示例中，升压单元21为BUCK/BOOST电路，降压单元22为BUK电路。
在第二示例、第三示例为中，由于BOOST电路和BUCK/BOOST电路、BUK电路和BUCK/BOOST电路的最优工作电压范围不同，因此可以根据整流电路3的输出电压来选择相应的电路工作。例如在将200V电压降为50V的时候，BUK电路的效率更高，当100V电压降50V的时候，BUCK/BOOST电路的效率更高。因此当整流电路3的输出电压范围在100V左右时，可以选择BUCK/BOOST电路工作。
请参阅图10。在另一实施例中，第一电源变换电路2包括BUCK/BOOST电路，或电荷泵电路至少其中之一；BUCK/BOOST电路包括升压单元21与降压单元22；电荷泵电 路包括升压单元21与降压单元22；在第一电源变换电路2包括BUCK/BOOST电路和电荷泵电路的情况下，BUCK/BOOST电路和电荷泵电路并联。
在此有三种情况，第一电源变换电路2可以仅包括BUCK/BOOST电路或仅包括电荷泵电路、或同时包括BUCK/BOOST电路、电荷泵电路，且两者并联连接。
在该实施例中，由于第一电源变换电路2同时包括有升压单元21和降压单元22，以提高与电源的适配能力。例如当待充电设备支持PD充电时，在充电过程中，待充电设备所需求的充电电压会发生改变。因此第一电源变换电路2可以根据待充电设备所需求的电压来上调脉冲变压器T1次级绕组的电压或下调脉冲变压器T1次级绕组的电压，从而为待充电设备提供其所需要的电压。
请参阅图11。为了进一步稳定第一电源变换电路2的输出电压，在一实施例中，所述电源电路还包括输出控制电路5，所述输出控制电路5包括反馈电路以及PWM控制芯片；所述PWM控制芯片包括反馈接收端、控制端；所述反馈电路的一端与所述第一电源变换电路2的输出端连接，所述反馈电路的另一端与所述PWM控制芯片的反馈接收端连接；所述PWM控制芯片的控制端与所述第一电源变换电路2连接，以控制所述第一电源变换电路2的输出电压；所述PWM控制芯片用于根据所述反馈电路的反馈结果调节所述控制端的输出，以稳定所述第一电源电路的输出电压。
反馈电路使得第一电源变换电路2成为闭环工作电路。本领域技术人员可以理解的是，升压电路、降压电路内部一般都具有调节输出电压的开关管。PWM控制芯片正是通过调节开关管的占空比，以对应调节升压电路、降压电路的输出电压。当PWM控制芯片接收到反馈电路的反馈电压偏大，则会调节开关管的占空比，以使第一电源变换电路2的输出电压降低。同样的，当PWM控制芯片接收到到反馈电路的反馈电压偏小，则会调节开关管的占空比，以使第一电源变换电路2的输出电压升高。由此来保证第一电源变换电路2的输出电压稳定。
相关技术中，通常在脉冲变压器T1的初级侧设置单独的一个绕组，以获取脉冲变压器T1上的电压反馈，AC-DC电源管理芯片通过该电压反馈以调制脉冲变压器T1初级绕组上的电压，以使得脉冲变压器T1次级绕组输出电压稳定。然而，这种电压反馈方式在连续调压时有以下问题：
反馈回路较长。待充电设备需要与适配器内的AC-DC电源管理芯片通信，AC-DC电源管理芯片要通过反馈级来获取输出电压信息。调整回路中信号传输路径为：待充电设备发送期望电压->信号隔离转换芯片->AC-DC电源管理芯片->调整PWM信号的占空比->从脉冲变压器T1反馈绕组获取采样电压->调整PWM信号的占空比->得到输出稳定电压。可见，反馈回路较长，电压调整的实时性较差。
调节精度较差，通过专用的反馈绕组回传反馈电压信号，但是脉冲变压器T1存在漏感漏磁等缺陷，初级绕组、次级绕组、反馈绕组并不能理想的实现严格由匝比决定的比例关系，通过专用的反馈绕组回传采样电压信号去控制次级绕组的输出电压，电压调节精度 较差。
整体电路占用体积较大。在整个电源电路中，起控制作用的电路(如AC-DC电源管理芯片)主要在脉冲变压器T1的初级侧，然而初级侧电压较高，因此脉冲变压器T1初级侧的器件需要较高的耐压能力，然而高耐压器件的封装通常较大，从而造成电路整体体积较大。
相关技术中，还常在次级输出侧用电阻分压，通过比较器与光耦传回脉冲变压器T1次级绕组的电压反馈信号至AC-DC电源管理芯片的方式，对脉冲变压器T1进行调控。然而在这种方案中，需要使用光耦作为初级、次级侧信号隔离器件，反馈采用信号回传给控制芯片路径较长，且光耦的速度不能满足更高响应要求的电源电路中。
在本公开一实施例中，是通过在脉冲变压器T1次级侧设置具有反馈电路以及PWM控制芯片的输出控制电路5，反馈电路直接采用脉冲变压器T1次级绕组上的电压，以使得PWM控制芯片根据反馈结果调整第一电源变换电路2的输出电压。因此本实施例中，反馈回路无需将反馈信号回传至脉冲变压器T1初级侧，而直接在脉冲变压器T1次级侧传输即可，因此信号传输回路大大缩短、电压调整实时性强。
并且，由于脉冲变压器T1次级电路与初级电路之间具有隔离效果，并且由于脉冲变压器T1次级电路的工作电压较低，因而待充电设备可以直接与脉冲变压器T1次级侧电路进行通信，实现调压请求等，而无需使用光耦等器件回传反馈信号或调压信号至初级侧；因此本实施例技术方案进一步节省高低压通信器件，提高反馈环路响应灵敏度。
可以理解的是，在该实施例中，AC-DC电源管理芯片的反馈端可以不接入反馈信号，即AC-DC电源管理芯片无需根据反馈信号调节脉冲变压器T1次级绕组上的电压。
进一步的，为了实现第一电源变换电路2的输出端连续可调，在一实施例中，所述PWM控制芯片还包括通信端；所述通信端用于与待供电设备通信，以接收所述待供电设备需要的供电电压；所述PWM控制芯片用于根据与所述待供电设备的通信结果控制所述第一电源电路的输出电压。
当待充电设备以及充电设备支持PD充电协议以及私有充电协议时，在充电过程中，待充电设备与PWM控制芯片进行通信，待充电设备会发送所需要的充电电压、充电电流至PWM控制芯片，PWM控制芯片进而控制第一电源变换电路2调整输出电压，以满足待充电设备的充电需求。
请参阅图12，图12是根据另一实施例示出的电源电路的电路示意图。基于上述实施例中，本公开中为了提高电源电路输出电压的调整范围，设置所述电源电路还包括第二电源变换电路4。所述第二电源变换电路4的输入端与所述整流电路3的输出端连接，所述第二电源变换电路的输出端与所述脉冲变压器T1初级绕组连接；所述第二电源变换电路用于在所述整流电路3输出的电压超出预设第二电压范围时，调节所述整流电路3输出的电压至所述预设第二电压范围内。第二预设电压范围的解释可以参照上述第一预设电压范 围的解释。
第二电源变换电路可以代替上述实施例中所提到的滤波电路。滤波电路需要用到电感值较大的电感以及容值较大的电容，因此滤波电路内电感和电容的体积较大。因此为了减小充电设备的体积，便于实现充电设备的小型化，本实施例中使用第二电源变换电路以对整流电路3的输出电压进行调整，由于第二电源变换电路的电路架构，能够使用电感值较小的电感以及容值较小的电容，从而有利于减小电感、电容的体积，进而有利于减小充电设备的体积。
以下将结合上述实施例，对第二电源变换电路的实施例进行说明。
由上述实施例中可知，整流电路3输出的电压波形大致为馒头波，电压幅值在最高电压和最低电压之间变动，其最低电压可能会将近0V。可以理解的是，整流电路3输出的电压在将近0V时，脉冲变压器T1初级绕组无法启动工作，使得脉冲变压器T1次级输出不稳定。
请参阅图13。在一实施例中，第二电源变换电路包括升压单元21，升压单元21用于在整流电路3的输出电压小于或等于预设第二电压范围的下限值V2时，升高整流电路3的输出电压。其中，预设第二电压范围的下限值V2大于脉冲变压器T1电路1的最低工作电压。
可以理解的是，根据所采用的脉冲变压器T1电路1的不同，其最低工作电压会有不同。本领域技术人员通过经验或通过试验能够获知所采用的脉冲变压器T1电路1的最低工作电压。脉冲变压器T1与AC-DC电源管理芯片的最低工作电压大体为脉冲变压器T1电路1的最低工作电压。
当整流电路3输出的电压低于预设第二电压范围的下限值时，升压单元21会开始工作，以将整流电路3输出的电压低于预设第二电压范围的下限值的部分进行抬高。
初级侧升压单元41可以将整流电路3输出的电压提升到一个特定值，也可以整流电路3输出的电压按照特定的倍数抬升。将升压单元21包括一个单元初级侧升压单元41、多个级联的单元初级侧升压单元41、BUCK/BOOST电路、电荷泵电路中的一个或多个。可以理解的是，BUCK/BOOST电路、电荷泵电路均是可以根据需要来实现升压或降压功能。在此一个单元初级侧升压单元41可以为BOOST电路，当多个初级侧升压单元41级联时，能够增大升压幅度。
在一示例中，升压单元21为不可控电路，通过选择合适参数的电阻、电容、电感等元器件，能够调节工作启动阈值，工作启动阈值设定为预设第二电压范围的下限值时，一旦整流电路3的输出电压降低至预设第二电压范围的下限值，便会触发升压单元21工作。
在另一示例中升压单元21为可控电路。升压单元21中所包括的单向导通器件为MOS管；升压单元21与初级侧升压单元41还包括用于控制MOS管导通和关断的第一触发电路，由此第一触发电路便可以通过MOS管的导通和关断，从而触发升压单元21工作或停止工作。
以升压单元21为BOOST电路为例，在BOOST电路中可以将二极管替换成MOS管，由此使得BOOST电路为可控电路。另一方面，由于MOS管具有较小的压降，因此将BOOST电路中的二极管替换为MOS管还可以减小BOOST电路的电能损耗，有利于提高BOOST电路输出电压。对于其他的升压单元21，例如BUCK/BOOST电路、电荷泵电路中的二极管也可以采用MOS管进行替换。
当升压单元21为可控电路时，可以根据需要灵活的设置升压单元21的开始工作和停止工作的时间，使得升压单元21能够与整流电路3、脉冲变压器T1电路1更好的配合，以使得经过升压单元21处理后的电压能够完全满足脉冲变压器T1电路1的工作电压。
在一实施例中，为了进一步初级侧升压单元41输出的电压，可以在初级侧升压单元41的输入端设置第二电容C2，第二电容C2的第一端与第二电源变换电路的输入端连接，第二电容C2的第二端接地。第二电容C2通过储能从而升高第二电源变换电路输入端的电压，从而支持了初级侧升压单元41工作的稳定性，并且由于第二电源变换电路输入端的电压升高，从而升高了第二电源变换电路输出端输出的电压值，有利于将脉冲变压器T1的初级绕组的输入电压稳定在一个定值之上，减小脉冲变压器T1的工作死区。
请参阅图14。进一步的，为了进一步提高脉冲变压器T1初级侧电压的稳定性。在一实施例中，第二电源变换电路还包括初级侧降压单元42；初级侧降压单元42用于在整流电路3的输出电压大于或等于预设第二电压范围的上限值时，降低整流电路3的输出电压；其中，预设第二电压范围的上限值小于整流电路3输出电压的最大值。
当整流电路3输出的电压高于预设第二电压范围的下限值时，初级侧降压单元42会开始工作，以将整流电路3输出的电压高于预设第二电压范围的上限值的部分进行抬高。
初级侧升压单元41可以将整流电路3输出的电压降低到一个特定值，也可以整流电路3输出的电压按照特定的倍数降低。初级侧降压单元42包括一个单元初级侧降压单元42、多个级联的单元初级侧降压单元42、BUCK/BOOST电路、电荷泵电路中的一个或多个。在此一个单元初级侧降压单元42可以为BUCK电路，当多个初级侧升压单元41级联时，能够增大降压幅度。
在一示例中，初级侧降压单元42为不可控电路，通过选择合适参数的电阻、电容、电感等元器件，能够调节初级侧降压单元42的工作启动阈值，工作启动阈值设定为预设第二电压范围的上限值V1时，一旦整流电路3的输出电压升高至预设第二电压范围的上限值V1，便会触发初级侧降压单元42工作。
在另一示例中初级侧降压单元42为可控电路。初级侧降压单元42中所包括的单向导通器件为MOS管；初级侧降压单元42与初级侧降压单元42还包括用于控制MOS管导通和关断的第二触发电路，由此第一触发电路便可以通过MOS管的导通和关断，从而触发初级侧降压单元42工作或停止工作。
以初级侧降压单元42为BUCK电路为例，在BUCK电路中可以将二极管替换成MOS管，由此使得BUCK电路为可控电路。另一方面，由于MOS管具有较小的压降，因此将 BUCK电路中的二极管替换为MOS管还可以减小BUCK电路的电能损耗。对于其他的初级侧降压单元42，例如BUCK/BOOST电路、电荷泵电路中的二极管也可以采用MOS管进行替换。
当初级侧降压单元42为可控电路时，可以根据需要灵活的设置初级侧降压单元42的开始工作和停止工作的时间，使得初级侧降压单元42能够与整流电路3、脉冲变压器T1电路1更好的配合。
可以理解的是，根据选用的整流电路3不同，整流电路3输出波形可能会有相应的不同，因此本公开方案中可以根据整流电路3输出波形选择仅使用初级侧升压单元41或初级侧降压单元42，也可以同时使用初级侧升压单元41和初级侧降压单元42，以将整流电路3的输出电压值调整值预设第二电压范围内。
一般的，电源电路分为正激式电路和反激式电路，相应的，脉冲变压器T1可以是正激式脉冲变压器T1或反激式脉冲变压器T1。其中，正激式脉冲变压器T1对脉冲变压器T1初级绕组上电压稳定性的要求较高。在该实施例中，通过升压单元21和初级侧降压单元42的设置，使得脉冲变压器T1初级绕组上的电压较为稳定，从而均适用于正激式脉冲变压器T1和反激式脉冲变压器T1。当脉冲变压器T1采用正激式脉冲变压器T1时，能够提高脉冲变压器T1负极绕组上输出电压的稳定性，并且能够提高功率输出能力，使得电源电路能够用于大功率的应用场合。
请参阅图14。在一实施例中，电源电路同时使用升压单元21和初级侧降压单元42，且升压单元21、初级侧降压单元42并联连接。升压单元21可以是仅具有升压功能的电路，例如BOOST电路，也可以是集成了升压和降压功能的BUCK/BOOST电路、电荷泵电路等。
在第一示例中，升压单元21为BOOST电路，初级侧降压单元42为BUK电路。在第二示例中，升压单元21为BOOST电路，初级侧降压单元42为BUCK/BOOST电路；在第三示例中，升压单元21为BUCK/BOOST电路，初级侧降压单元42为BUK电路。
在第二示例、第三示例为中，由于BOOST电路和BUCK/BOOST电路、BUK电路和BUCK/BOOST电路的最优工作电压范围不同，因此可以根据整流电路3的输出电压来选择相应的电路工作。例如在将200V电压降为50V的时候，BUK电路的效率更高，当100V电压降50V的时候，BUCK/BOOST电路的效率更高。因此当整流电路3的输出电压范围在100V左右时，可以选择BUCK/BOOST电路工作。
在另一实施例中，第二电源变换电路包括BUCK/BOOST电路，或电荷泵电路至少其中之一；BUCK/BOOST电路包括升压单元21与初级侧降压单元42；电荷泵电路包括升压单元21与初级侧降压单元42；在第二电源变换电路包括BUCK/BOOST电路和电荷泵电路的情况下，BUCK/BOOST电路和电荷泵电路并联。
在此有三种情况，第二电源变换电路可以仅包括BUCK/BOOST电路或仅包括电荷泵电路、或同时包括BUCK/BOOST电路、电荷泵电路，且两者并联连接。
本公开技术方案通过设置第二电源变换电路，以在整流电路3输出的电压超出预设第二电压范围时，调节整流电路3输出的电压至预设第二电压范围内，从而有效减小或消除脉冲变压器T1电路1的工作死区，使得二级电源变换在每个时刻都能获得足够的电压供应，进而可以满足脉冲变压器T1电路1能够输出连续稳定的电压，供应第一电源变换电路2工作，以提高电源电路输出电压的精准性。
请参阅图15。第一电源变换电路2与第二电源变换电路有多种配合方式。
在一示例中，当电源电压较低时，或者待供电设备需要较高的供电电压时，可以使用第二电源变换的初级侧升压单元41与第一电源变换电路2的升压单元21配合，以提高电源电路的整体升压幅度。
在一示例中，当电源电压较高时，或者待供电设备需要较低的供电电压时，可以使用第二电源变换的初级侧降压单元42与第一电源变换电路2的降压单元22配合，以提高电源电路的整体降压幅度。
在一示例中，当电源电压较高时，或者待供电设备需要较低的供电电压时，可以使用第二电源变换的初级侧降压单元42与第一电源变换电路2的降压单元22配合，以提高电源电路的整体降压幅度。
在一示例中，可以使用第二电源变换的初级侧升压单元41与第一电源变换电路2的降压单元22配合。初级侧升压单元41将脉冲变压器T1初级侧电压先进行抬高，从而使得脉冲变压器T1次级侧电压也相应抬高，并抬高至仅需要第一电源变换电路2的降压单元22工作即能够将脉冲变压器T1次级侧电压变换至待充电设备的需求电压。因此本示例无需在第一电源变换电路2内设置升压单元21，从而简化电路结构。
在另一示例中，可以使用第二电源变换的初级侧降压单元42与第一电源变换电路2的升压单元21配合。初级侧降压单元42将脉冲变压器T1初级侧电压先进行降低，从而使得脉冲变压器T1次级侧电压也相应降低，并抬高至仅需要第一电源变换电路2的升压单元21工作即能够将脉冲变压器T1次级侧电压变换至待充电设备的需求电压。因此本示例无需在第一电源变换电路2内设置降压单元22，从而简化电路结构。
虽然已参照几个典型实施方式描述了本公开，但应当理解，所用的术语是说明和示例性、而非限制性的术语。由于本公开能够以多种形式具体实施而不脱离发明的精神或实质，所以应当理解，上述实施方式不限于任何前述的细节，而应在随附权利要求所限定的精神和范围内广泛地解释，因此落入权利要求或其等效范围内的全部变化和改型都应为随附权利要求所涵盖。

Claims (20)

  1. 一种电源电路，其特征在于，包括：
    变压器电路，包括脉冲变压器以及开关控制电路；所述脉冲变压器的初级绕组与电源连接，且与所述开关控制电路连接，所述开关控制电路用于将所述初级绕组上的电压调制成为脉冲电压；
    第一电源变换电路，所述第一电源变换电路的输入端与所述变压器的次级绕组连接，用于在所述次级绕组输出的电压超出第一预设电压范围时，将所述变压器的次级绕组上的电压变换至所述第一预设电压范围内后输出。
  2. 根据权利要求1所述的电源电路，其特征在于，所述第一电源变换电路包括升压单元，所述升压单元用于在所述变压器电路的输出电压小于或等于所述第一预设电压范围的下限值时，升高位于第一预设电压范围的下限值之下的所述脉冲变压器次级绕组上的电压。
  3. 根据权利要求2所述的电源电路，其特征在于，所述升压单元包括：BOOST电路、BUCK/BOOST电路、电荷泵电路或CUK电路中的至少一个。
  4. 根据权利要求2所述的电源电路，其特征在于，所述电源电路还包括第一电容，所述第一电容的第一端与所述第一电源变换电路的输入端连接，所述第一电容的第二端接地，所述第一电容用于升高所述第一电源变换电路输入端的电压。
  5. 根据权利要求2所述的电源电路，其特征在于，所述第一电源变换电路还包括降压单元；所述降压单元用于在所述变压器电路的输出电压大于或等于所述第一预设电压范围的上限值时，降低位于所述第一预设电压范围的上限值之上的所述脉冲变压器次级绕组上的电压；
    其中，所述第一预设电压范围的上限值小于所述变压器电路输出电压的最大值。
  6. 根据权利要求5所述的电源电路，其特征在于，所述降压单元包括BUCK电路、BUCK/BOOST电路、电荷泵电路或CUK电路中的至少一个。
  7. 根据权利要求5所述的电源电路，其特征在于，所述升压单元中所包括的单向导通器件为MOS管；所述升压单元还包括用于控制所述MOS管导通和关断的第一触发电路；所述第一触发电路用于通过控制所述升压单元中的MOS管以控制所述升压单元开始或停止工作；
    所述降压单元中所包括的单向导通器件为MOS管；所述降压单元还包括用于控制所述MOS管导通和关断的第二触发电路；所述第二触发电路通过控制所述降压单元中MOS管以控制所述降压单元开始或停止工作。
  8. 根据权利要求1至7任意一项所述的电源电路，其特征在于，所述电源电路还包括输出控制电路，所述输出控制电路包括反馈电路以及PWM控制芯片；所述PWM控制芯片包括反馈接收端、控制端；
    所述反馈电路的一端与所述第一电源变换电路的输出端连接，所述反馈电路的另一端与所述PWM控制芯片的反馈接收端连接；所述PWM控制芯片的控制端与所述第一电源变换电路连接，以控制所述第一电源变换电路的输出电压；
    所述PWM控制芯片用于根据所述反馈电路的反馈结果调节所述控制端的输出，以稳定所述第一电源电路的输出电压。
  9. 根据权利要求8所述的电源电路，其特征在于，所述PWM控制芯片还包括通信端；所述通信端用于与待供电设备通信，以接收所述待供电设备需要的供电电压；
    所述PWM控制芯片用于根据与所述待供电设备的通信结果控制所述第一电源电路的输出电压。
  10. 根据权利要求1所述的电源电路，其特征在于，所述电源电路还包括第二电源变换电路和整流电路；
    所述整流电路的输入端供交流电源连接，以整流所述交流电源；
    所述第二电源变换电路的输入端与所述整流电路的输出端连接，所述第二电源变换电路的输出端与所述变压器初级绕组连接；
    所述第二电源变换电路用于在所述整流电路输出的电压超出预设第二电压范围时，调节所述整流电路输出的电压至所述预设第二电压范围内。
  11. 根据权利要求10所述的电源电路，其特征在于，所述开关控制电路包括AC-DC电源管理芯片；所述AC-DC电源管理芯片具有开关控制端；
    所述脉冲变压器的初级绕组的第一端与所述第二电源变换电路的输出端连接，所述初级绕组的第二端与所述AC-DC电源管理芯片的开关控制端连接，以调制所述初级绕组上的电压。
  12. 一种充电设备，其特征在于，包括电源接入口，和电源电路，所述电源接入口用于接入电源；所述电源电路包括：
    变压器电路，包括脉冲变压器以及开关控制电路；所述脉冲变压器的初级绕组与电源连接，且与所述开关控制电路连接，所述开关控制电路用于将所述初级绕组上的电压调制成为脉冲电压；
    第一电源变换电路，所述第一电源变换电路的输入端与所述变压器的次级绕组连接，用于在所述次级绕组输出的电压超出第一预设电压范围时，将所述变压 器的次级绕组上的电压变换至所述第一预设电压范围内后输出。
  13. 根据权利要求12所述的充电设备，其特征在于，所述第一电源变换电路包括升压单元，所述升压单元用于在所述变压器电路的输出电压小于或等于所述第一预设电压范围的下限值时，升高位于第一预设电压范围的下限值之下的所述脉冲变压器次级绕组上的电压。
  14. 根据权利要求13所述的充电设备，其特征在于，所述电源电路还包括第一电容，所述第一电容的第一端与所述第一电源变换电路的输入端连接，所述第一电容的第二端接地，所述第一电容用于升高所述第一电源变换电路输入端的电压。
  15. 根据权利要求13所述的充电设备，其特征在于，所述第一电源变换电路还包括降压单元；所述降压单元用于在所述变压器电路的输出电压大于或等于所述第一预设电压范围的上限值时，降低位于所述第一预设电压范围的上限值之上的所述脉冲变压器次级绕组上的电压；
    其中，所述第一预设电压范围的上限值小于所述变压器电路输出电压的最大值。
  16. 根据权利要求15所述的充电设备，其特征在于，所述升压单元中所包括的单向导通器件为MOS管；所述升压单元还包括用于控制所述MOS管导通和关断的第一触发电路；所述第一触发电路用于通过控制所述升压单元中的MOS管以控制所述升压单元开始或停止工作；
    所述降压单元中所包括的单向导通器件为MOS管；所述降压单元还包括用于控制所述MOS管导通和关断的第二触发电路；所述第二触发电路通过控制所述降压单元中MOS管以控制所述降压单元开始或停止工作。
  17. 根据权利要求12至16任意一项所述的充电设备，其特征在于，所述电源电路还包括输出控制电路，所述输出控制电路包括反馈电路以及PWM控制芯片；所述PWM控制芯片包括反馈接收端、控制端；
    所述反馈电路的一端与所述第一电源变换电路的输出端连接，所述反馈电路的另一端与所述PWM控制芯片的反馈接收端连接；所述PWM控制芯片的控制端与所述第一电源变换电路连接，以控制所述第一电源变换电路的输出电压；
    所述PWM控制芯片用于根据所述反馈电路的反馈结果调节所述控制端的输出，以稳定所述第一电源电路的输出电压。
  18. 根据权利要求17所述的充电设备，其特征在于，所述PWM控制芯片还包括通信端；所述通信端用于与待供电设备通信，以接收所述待供电设备需要的 供电电压；
    所述PWM控制芯片用于根据与所述待供电设备的通信结果控制所述第一电源电路的输出电压。
  19. 根据权利要求12所述的充电设备，其特征在于，所述电源电路还包括第二电源变换电路和整流电路；
    所述整流电路的输入端供交流电源连接，以整流所述交流电源；
    所述第二电源变换电路的输入端与所述整流电路的输出端连接，所述第二电源变换电路的输出端与所述变压器初级绕组连接；
    所述第二电源变换电路用于在所述整流电路输出的电压超出预设第二电压范围时，调节所述整流电路输出的电压至所述预设第二电压范围内。
  20. 根据权利要求19所述的充电设备，其特征在于，所述开关控制电路包括AC-DC电源管理芯片；所述AC-DC电源管理芯片具有开关控制端；
    所述脉冲变压器的初级绕组的第一端与所述第二电源变换电路的输出端连接，所述初级绕组的第二端与所述AC-DC电源管理芯片的开关控制端连接，以调制所述初级绕组上的电压。
PCT/CN2021/078536 2020-03-12 2021-03-01 电源电路及充电设备 Ceased WO2021179937A1 (zh)

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