WO2024051773A1 - 基站天线和基站 - Google Patents

基站天线和基站 Download PDF

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Publication number
WO2024051773A1
WO2024051773A1 PCT/CN2023/117447 CN2023117447W WO2024051773A1 WO 2024051773 A1 WO2024051773 A1 WO 2024051773A1 CN 2023117447 W CN2023117447 W CN 2023117447W WO 2024051773 A1 WO2024051773 A1 WO 2024051773A1
Authority
WO
WIPO (PCT)
Prior art keywords
antenna
frequency selection
base station
antenna array
conductive component
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2023/117447
Other languages
English (en)
French (fr)
Inventor
肖伟宏
道坚丁九
刘旭
白雪
张玉禄
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Huawei Technologies Co Ltd
Original Assignee
Huawei Technologies Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Huawei Technologies Co Ltd filed Critical Huawei Technologies Co Ltd
Priority to EP23862467.0A priority Critical patent/EP4576433A4/en
Publication of WO2024051773A1 publication Critical patent/WO2024051773A1/zh
Priority to US19/073,318 priority patent/US20250239781A1/en
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/06—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using refracting or diffracting devices, e.g. lens
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0013—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/246—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for base stations
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/1242—Rigid masts specially adapted for supporting an aerial
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/526—Electromagnetic shields
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/02—Refracting or diffracting devices, e.g. lens, prism
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/307—Individual or coupled radiating elements, each element being fed in an unspecified way
    • H01Q5/314—Individual or coupled radiating elements, each element being fed in an unspecified way using frequency dependent circuits or components, e.g. trap circuits or capacitors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/378—Combination of fed elements with parasitic elements
    • H01Q5/392—Combination of fed elements with parasitic elements the parasitic elements having dual-band or multi-band characteristics
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/40—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements
    • H01Q5/42—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements using two or more imbricated arrays
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W88/00—Devices specially adapted for wireless communication networks, e.g. terminals, base stations or access point devices
    • H04W88/08—Access point devices

Definitions

  • the present application relates to the field of antenna technology, and in particular to a base station antenna and a base station.
  • the radiating unit may be blocked by surrounding metal parts.
  • the electromagnetic wave When the electromagnetic wave propagates to these metal parts, it will scatter on the surface of the metal part and cannot completely propagate to the rear of the metal part, causing the generation of electromagnetic waves behind the metal part.
  • Electromagnetic shadow For the signal receiving process of the antenna, the electromagnetic shadow will cause the received signal quality of the radiation unit located behind the metal component to deteriorate; for the signal radiation process of the antenna, the electromagnetic shadow will affect the communication quality of the terminal located behind the metal component.
  • the present application provides a base station antenna and a base station, which can improve the electromagnetic shadow problem caused by metal parts.
  • the present application provides a base station antenna, including a first antenna array, a frequency selection surface, a second antenna array and an antenna conductive component; the frequency selection surface is located between the first radiator of the radiating unit of the first antenna array and the third antenna array.
  • the frequency selective surface is used to reflect the radiation signal of the first antenna array and transmit the radiation signal of the second antenna array;
  • the antenna conductive component and the first antenna array are located on the same side of the front surface of the second antenna array ;
  • the conductive component of the antenna includes a conductive base, a first structural unit and a second structural unit; the first structural unit and the second structural unit both surround the conductive base, the first structural unit and the second structural unit are spaced apart and arranged adjacently, and form a capacitor.
  • the frequency selection surface can be used as a reference plane to realize the first antenna array and the second antenna.
  • Stacked arrangement of arrays The stacked arrangement can deploy antenna arrays with more frequency bands and channels within a limited antenna aperture to meet communication requirements. Since the frequency selective surface can allow the electromagnetic waves of the second antenna array to pass through, the frequency selective surface will not block the signal of the second antenna array.
  • the conductive components of the antenna are positioned so as to physically block the second antenna array.
  • the gap and the structural units on both sides can form a capacitor, which constrains the electromagnetic wave to propagate in the gap, allowing the electromagnetic wave to propagate around the conductive component of the antenna to the conductive part of the antenna. behind the component, thereby reducing or eliminating electromagnetic shadows.
  • the antenna conductive component is located between the first antenna array and the second antenna array.
  • the conductive component of the antenna is arranged between the first antenna array and the second antenna array, which still satisfies the design that the conductive component of the antenna and the first antenna array are located on the same side of the front of the second antenna array.
  • the conductive substrate includes a feed network, and the feed network is connected to the radiating unit of the first antenna array.
  • the feed network can have electromagnetic stealth performance and improve the electromagnetic shadow problem caused by the physical shielding of the second antenna array by the feed network.
  • the frequency selective surface is not electrically connected to the first antenna array and the second antenna array, and/or the frequency selective surface is not electrically connected to the feed network.
  • the frequency selective surface electrically unconnected to the antenna array, the feed signal of the antenna array will not be transmitted through the frequency selective surface, thereby shortening the feed path, reducing losses, and making the structure of the frequency selective surface more compact. Simple, lower costs. Since the frequency selective surface has no electrical connection with the feed network as a conductive substrate, there is basically no coupling between the frequency selective surface and the feed network, which can ensure the electromagnetic stealth performance and the frequency selective performance of the frequency selective surface.
  • the first antenna array and the antenna conductive component are located on the same side of the frequency selective surface.
  • this solution can target a typical application scenario of stacked antennas and deploy more frequency bands and channels under a limited antenna aperture. Antenna array and improve electromagnetic shadowing.
  • the radiating unit of the first antenna array includes a feed structure, the feed structure connects the first radiator and the feed network, the feed structure passes through the frequency selection surface; the first radiator and The conductive components of the antenna are located on opposite sides of the frequency selective surface.
  • this solution can target a typical application scenario of stacked antennas and deploy more frequency bands and channels under a limited antenna aperture. Antenna array and improve electromagnetic shadowing.
  • the location of the frequency selection surface can be determined according to the antenna design requirements.
  • the conductive components of the antenna are arranged on the side of the frequency selection surface facing away from the first radiator, so that the distance between the conductive components of the antenna and the first radiator is larger, which can reduce the impact of the conductive components of the antenna (including the feed network) on the first antenna array.
  • the influence of near-field coupling ensures the performance of the first antenna array.
  • the frequency selection surface includes a first frequency selection surface and a second frequency selection surface that are stacked and spaced apart, and the first frequency selection surface is located between the first radiator and the second frequency selection surface.
  • the radiating unit of the first antenna array includes a feed structure, the feed structure connects the first radiator and the feed network, the feed structure passes through the first frequency selection surface, and the first radiator and the antenna conductive component are respectively located at the first frequency Select opposite sides of the surface.
  • this solution can target a typical application scenario of stacked antennas with limited antenna apertures. Deploy antenna arrays with more frequency bands and channels and improve electromagnetic shadows.
  • the positions of the first frequency selection surface and the second frequency selection surface can be determined according to the antenna design requirements.
  • the thickness of the antenna conductive component (the conductive base is the feed network) can be made smaller so that it can be located between the first frequency selection surface and the second frequency selection surface, which can make the total thickness of the first antenna smaller.
  • multi-layer frequency selection surfaces can enhance filtering selectivity and help expand the bandwidth of the antenna.
  • the frequency selection surface includes a first frequency selection surface and a second frequency selection surface that are stacked and spaced apart, and the first frequency selection surface is located between the first radiator and the second frequency selection surface. ;
  • the conductive component of the antenna passes through the first frequency selection surface, and the radiating unit of the first antenna array and the second antenna array are respectively located on opposite sides of the first frequency selection surface.
  • this solution can target a typical application scenario of stacked antennas with limited antenna apertures. Deploy antenna arrays with more frequency bands and channels and improve electromagnetic shadows.
  • the positions of the first frequency selection surface and the second frequency selection surface can be determined according to the antenna design requirements.
  • the antenna conductive component the conductive base is the feed network
  • the distance between the feed network and the first radiator can be prevented from being too large, thereby reducing the loss; and the feed network can be connected to the first frequency selection surface.
  • the distance between the first radiators is not too small to improve the influence of the feed network on the near-field coupling of the first antenna array.
  • the multi-layer frequency selection surface can enhance the filtering selectivity and help expand the bandwidth of the second antenna.
  • the first radiator includes a second radiator and a third radiator, and the second radiator and the third radiator have different frequency bands;
  • the feed network includes the first feed network and the third Two feed networks, the first feed network is electrically connected to the second radiator, and the second feed network is electrically connected to the third radiator.
  • the radiation unit of the second antenna array includes a fourth radiator and a fifth radiator, and the fourth radiator and the fifth radiator have different frequency bands.
  • the second antenna array by making the second antenna array have multiple frequency bands, the number of frequency bands and the number of channels can be expanded.
  • the minimum distance between the frequency selection surface and the conductive component of the antenna is greater than or equal to 0.1 times the wavelength corresponding to the highest operating frequency of the second antenna array.
  • the frequency selection surface includes a plurality of frequency selection units, the plurality of frequency selection units include a first frequency selection unit, the structure of the first frequency selection unit is different from the structures of other frequency selection units, and the A frequency selection element overlaps with the orthographic projection of the conductive component of the antenna on the frequency selection surface.
  • the structure of the first frequency selection unit in the frequency selection surface is relatively unique.
  • Such a frequency selection surface can be said to have a quasi-periodic array structure.
  • the coupling between the frequency selection surface and the antenna conductive component can be reduced, thereby Guaranteed electromagnetic stealth performance and frequency selective performance of frequency selective surfaces.
  • This solution can be applied to the following scenarios: If the distance between the frequency selection surface and the conductive parts of the antenna cannot meet the minimum spacing requirement due to product design limitations, this solution can be used to reduce the coupling between the frequency selection surface and the conductive parts of the antenna. .
  • the frequency selective surface includes a first part and a second part connected, the first part does not contain conductive material, the first part overlaps with the orthographic projection of the antenna conductive component on the frequency selective surface, and the second part Parts contain conductive materials.
  • this solution by removing the conductor layer in the first part of the frequency selective surface close to the conductive component of the antenna, the coupling between the frequency selective surface and the conductive component of the antenna can be greatly reduced, thus ensuring the electromagnetic stealth performance and frequency selection of the frequency selective surface. performance.
  • This solution can be applied to the following scenarios: If the distance between the frequency selection surface and the conductive parts of the antenna cannot meet the minimum spacing requirement due to product design limitations, this solution can be used to reduce the coupling between the frequency selection surface and the conductive parts of the antenna. .
  • the base station antenna includes a first radome and a second radome, a first antenna array, a frequency selection table
  • the surface and the conductive components of the antenna are located in the first radome, and the second antenna array is located in the second radome.
  • different parts of the capacitor have different capacitance values.
  • electromagnetic wave signals in different frequency bands can resonate in the gap with their respective electrical lengths, so that electromagnetic waves in different frequency bands can pass through the gap. Therefore, by making the capacitance values of different areas of the capacitor different, the gap can allow electromagnetic waves of multiple frequency bands to pass through, thereby expanding the stealth bandwidth.
  • the antenna conductive component includes at least two structural units, the first structural unit and the second structural unit are both structural units of at least two structural units; at least one structural unit is provided with a coupling gap , the parts of the structural unit located on both sides of the coupling gap are disconnected by the coupling gap and coupled through the coupling gap.
  • a coupling gap is formed in the structural unit to facilitate the assembly of different parts of the structural unit onto the conductive substrate in sequence, and finally to form a complete structural unit.
  • This can achieve reliable assembly of the structural unit in some scenarios.
  • the split assembly method can simplify the assembly process and improve the assembly yield.
  • the coupling gap can allow electromagnetic waves in certain frequency bands to pass through, so that the conductive components of the antenna can expand the stealth bandwidth to a certain extent.
  • the antenna conductive component includes at least two structural units, the first structural unit and the second structural unit are both structural units of at least two structural units; the structures of at least two structural units are the same , there is a gap between any two adjacent structural units and the shape of the gap is the same, and a capacitance is formed between any two adjacent structural units.
  • the conductive component of the antenna includes at least two structural units, and the first structural unit and the second structural unit are both structural units of the at least two structural units; the structures of the at least two structural units are incomplete. The same, and/or, there is a gap between at least two structural units and the shapes of the gaps are not all the same; capacitance is formed between any two adjacent structural units.
  • all structural units can form a quasi-periodic structural layer.
  • the quasi-periodic structural layer can be adapted to the shape and structure of the conductive substrate.
  • this application provides a base station, which includes a pole and any of the above base station antennas, and the base station antenna is fixed on the pole.
  • the base station antenna since the base station antenna includes a stacked antenna array, it can deploy antenna arrays with more frequency bands and channels under a limited antenna aperture, thereby meeting communication requirements. Due to the design of the conductive components of the antenna, the electromagnetic shadow conduction problem of the stacked antenna can be improved.
  • Figure 1 shows the application scenario of wireless communication between the base station and the terminal
  • Figure 2 shows the assembly structure of a base station according to an embodiment of the present application
  • Figure 3 shows a part of the internal frame structure of the base station in Figure 2;
  • Figure 4 shows the internal frame structure of a base station antenna according to the embodiment of the present application
  • Figure 5(a) shows a schematic structure of the frequency selection surface in the base station antenna in Figure 4;
  • Figure 5(b) shows another schematic structure of the frequency selection surface within the base station antenna in Figure 4;
  • Figure 6 is a schematic diagram of the internal frame structure of a base station antenna in an embodiment
  • Figure 7 is a schematic diagram of the internal frame structure of a base station antenna in an embodiment
  • Figure 8 is a schematic diagram of the internal frame structure of a base station antenna in an embodiment
  • Figure 9 is a schematic diagram of the internal frame structure of a base station antenna in an embodiment
  • Figure 10 is a schematic diagram of the internal structure of the first antenna of the base station antenna in an embodiment
  • Figure 11(a) shows the quasi-periodic array structure design of the frequency selective surface in one embodiment
  • Figure 11(b) shows the quasi-periodic array structure design of the frequency selective surface in another embodiment
  • Figure 12 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 13 is a schematic side cross-sectional structural view of the conductive component of the antenna shown in Figure 12;
  • Figure 14 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 15(a) is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 15(b) is a partial enlarged structural diagram of position A in Figure 15(a);
  • Figure 16 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 17 shows the application principle of the antenna conductive component shown in Figure 16 in a base station antenna
  • Figure 18 is a partial enlarged structural schematic diagram of the structure shown in Figure 17;
  • Figure 19 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 20 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 21 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 22 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 23 is a side structural schematic diagram of the conductive component of the antenna shown in Figure 22;
  • Figure 24 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 25 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 26(a) is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 26(b) is a schematic three-dimensional structural diagram of the conductive component of the antenna in an embodiment
  • Figure 27 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment
  • Figure 28 is a schematic three-dimensional structural diagram of an antenna conductive component in an embodiment.
  • first, second, third, “fourth”, “fifth”, etc. are only used to distinguish components and cannot be understood as indicating or implying the relative importance of the components. or an implicit indication of the quantity of the technical feature indicated. Thus, features defined by “first,” “second,” etc. may explicitly or implicitly include one or more of such features.
  • multiple (layers) means two (layers) or more than two (layers).
  • the embodiments of this application relate to base stations and base station antennas.
  • the base station will be introduced first, and then the base station antenna will be explained.
  • FIG. 1 illustrates the application scenario of wireless communication between a base station and a terminal.
  • the base station is used to provide cell coverage for wireless signals to achieve communication between terminal equipment and the wireless network.
  • the base station can be a base transceiver station (BTS) in the global system for mobile communication (GSM) or code division multiple access (code division multiple access, CDMA) system, or it can be A NodeB (NB) in a wideband code division multiple access (WCDMA) system, or an evolutionary NodeB (eNB) in a long term evolution (LTE) system , or it can be a wireless controller in a cloud radio access network (CRAN) scenario.
  • GSM global system for mobile communication
  • CDMA code division multiple access
  • NB wideband code division multiple access
  • eNB evolutionary NodeB
  • LTE long term evolution
  • CRAN cloud radio access network
  • the base station can also be a relay station, an access point, a vehicle-mounted device, a wearable device, a g node (gNodeB or gNB) in a new radio (NR) system or a base station in a future evolved network, etc., in the embodiments of this application Not limited.
  • gNodeB or gNB g node
  • NR new radio
  • FIG. 2 illustrates the structural composition of a base station antenna equipped with the base station in Figure 1.
  • the base station 1 may include a pole 11 , a pole bracket 12 , a radome 13 , an antenna array 14 , a radio frequency processing unit 15 , a cable 16 and a baseband processing unit 17 .
  • the pole support 12, the radome 13, and the antenna array 14 can be collectively referred to as a base station antenna.
  • the base station antenna can also include a feed network and a reflector, which will be described below.
  • the pole 11 can be fixed to the ground.
  • the pole bracket 12 connects the pole 11 and the radome 13 , and the radome 13 is fixed to the pole 11 through the pole bracket 12 .
  • Antenna array 14 may be mounted within radome 13 .
  • a feed network can also be installed inside the radome 13 .
  • the radome 13 has good electromagnetic wave penetration characteristics and environmental weather resistance, and can protect the components installed inside it.
  • Antenna array 14 is used to radiate and receive antenna signals.
  • the antenna array 14 may include several radiating units arranged in a certain regular array, and each radiating unit can radiate and receive electromagnetic waves.
  • the radiating element may include an antenna element.
  • the working frequency bands of different radiating units may be the same or different.
  • the radiating unit may include a connected radiator (which may be a radiating arm, for example) and a feed structure (which may include a balun, for example). Among them, the radiator is used to radiate and receive signals; the feed structure connects the radiator and the feed network to transmit the electrical signal transmitted by the feed network to the radiator, and transmits the signal received by the radiator to the feed network .
  • the base station antenna may also include a reflecting plate.
  • the reflecting plate may also be called a bottom plate, an antenna panel or a reflecting surface.
  • the reflecting plate may be made of metal material, for example.
  • the radiating unit can be mounted on the surface on one side of the reflector. When the radiating unit receives the antenna signal, the reflective plate can reflect the antenna signal and focus it on the receiving point to achieve directional reception; when the radiating unit transmits the antenna signal, the reflective plate can achieve directional transmission of the antenna signal.
  • the reflective plate can enhance the reception or emission capability of the antenna signal of the radiating unit, and can also block and shield the interference effect of other signals on the antenna signal from the back of the reflective plate (the back refers to the side of the reflective plate facing away from the radiating unit). , improve the gain of the antenna.
  • the radio frequency processing unit 15 (also called a radio frequency remote unit (RRU)) can be connected to the feed network through a jumper, and is electrically connected to the antenna array 14 through the feed network.
  • the feed network (will be described below) ) can be used as a signal transmission path between the radio frequency processing unit 15 and the antenna array 14 .
  • the radio frequency processing unit 15 may be electrically connected to the baseband processing unit 17 (which may also be called a baseband unit (BBU)) through a cable 16 (such as an optical cable).
  • BBU baseband unit
  • the radio frequency processing unit 15 and the baseband processing unit 17 may both be located outside the radome 13 , and the radio frequency processing unit 15 may be located at the proximal end of the base station antenna.
  • the radio frequency processing unit 15 can perform frequency selection, amplification and frequency down-conversion processing on the antenna signals received by the antenna array 14 , and convert them into intermediate frequency signals or baseband signals and send them to the baseband processing unit 17 .
  • the radio frequency processing unit 15 can also convert the baseband processing unit 17 or the intermediate frequency signal through up-conversion and amplification processing into electromagnetic waves through the antenna array 14 and send them out.
  • FIG. 3 may represent the internal frame structure of a part of the base station 1 in FIG. 2 .
  • the antenna array 14 of the base station 1 is connected to the feed network 18.
  • the feed network 18 can achieve different radiation beam directions through a transmission mechanism, or be connected to a calibration network to obtain the base station 1 required calibration signal.
  • the feeding network 18 can feed signals to the antenna array 14 according to a certain amplitude and phase, or send received signals to the baseband processing unit 17 according to a certain amplitude and phase.
  • the feed network 18 may include a phase shifter 181, which is used to change the maximum direction of antenna signal radiation.
  • the feed network 18 may also include modules for extending performance, such as a power splitter 182 .
  • the power divider 182 is used to combine multiple signals into one signal, which is transmitted through the antenna array 14; or, the power divider 182 divides one signal into multiple signals, for example, the signal received by the antenna array 14 is divided into different frequencies according to different frequencies. It is divided into multiplexes and transmitted to the baseband processing unit 17 for processing.
  • the feed network 18 may also include a filter 183 for filtering out interference signals.
  • the feed network 18 may also include a combiner.
  • the feed network 18 may also include any form of transmission line, such as coaxial lines, strip lines, microstrip lines, etc.
  • the structure of the base station 1 shown in Figures 2 and 3 is only an example. In fact, the structure of the base station in the embodiment of the present application can be flexibly designed according to product requirements and is not limited to the above.
  • the base station may not have a pole 11 , and the radome 13 may be fixed to the tower through a pole bracket 12 .
  • the antenna array may be surrounded by a conductor component (the conductor component at least includes a conductive part, for example, the entire area of the conductor component is a conductor, or the conductor component includes a conductor part and an insulating part.
  • the conductor component is called When electromagnetic waves propagate to these conductive components, they will be scattered on the surface of the conductive components and cannot completely propagate to the rear of the conductive components, causing electromagnetic shadows to be generated behind the conductive components. For the signal receiving process, the electromagnetic shadow will cause the received signal quality of the antenna array located behind the conductive component to deteriorate; for the signal radiation process, the electromagnetic shadow will affect the communication quality of the terminal located behind the conductive component.
  • base stations are required to have a larger number of communication frequency bands and channels to meet communication needs.
  • operator site antenna space resources are limited, and the antenna aperture is also strictly restricted, making it difficult to increase the number of frequency bands and channels.
  • the base station antenna in the embodiment of the present application has an "electromagnetic stealth" design for the conductor components around the antenna array, so that electromagnetic waves can continue to propagate around the conductor components, thereby improving the electromagnetic shadow problem.
  • the "layered design” of the antenna array antenna arrays with more frequency bands and channels can be set up under a limited antenna diameter. The following will first explain in detail the overall frame structure of the base station antenna, including the "layered design”; and then explain the "electromagnetic stealth" design.
  • Figure 4 illustrates the internal frame structure of the base station antenna 2 in an embodiment.
  • the base station antenna 2 has an electromagnetic stealth design and a stacked design.
  • the base station antenna 2 may include a first antenna and a second antenna.
  • the first antenna may include a first radome 21, a first antenna array 2A, an antenna conductive component 3 and a frequency selective surface (FSS) 24.
  • the first antenna array 2A, the antenna conductive component 3 and the frequency selective surface 24 may all be located within the first radome 21 .
  • the second antenna may include a second antenna cover 26 and a second antenna array 2B, and the second antenna array 2B is located in the second antenna cover 26.
  • the first radome 21 and the second radome 26 are two independent radomes, and they can be fixed on the same pole or tower.
  • the two antennas can be deployed separately, achieving decoupling design and flexible deployment of antennas in different frequency bands. It can be understood that the solution of this embodiment is only an example. In other embodiments, the first antenna array and the second antenna array may also be in the same radome.
  • the first antenna array 2A may include a plurality of first radiating units 22 .
  • the frequency bands of each first radiating unit 22 may be consistent, or the frequency band of at least one first radiating unit 22 may be different from the frequency bands of the remaining first radiating units 22 .
  • the first radiating unit 22 may include a radiator 221 (which may be called a first radiator) and a feed structure 222, both of which are connected. It can be understood that in FIG. 4 , the horizontal lines represent the radiator 221 and the vertical lines represent the feed structure 222 . This is only an illustration and does not limit the specific structures and details of the radiator 221 and the feed structure 222 . Location.
  • the antenna conductive component 3 and the first antenna array 2A may be located on the same side of the array surface of the second antenna array 2B.
  • the antenna conductive component 3 may be located between the first antenna array 2A and the second antenna array 2B, and the three may be considered to be stacked.
  • the antenna conductive component 3 may be longer, for example, it may substantially block the second antenna array 2B.
  • the antenna conductive component 3 and the first antenna array 2A are located on the same side of the second antenna array 2B, and may also include the following design: the antenna conductive component 3, the first antenna array 2A, the second antenna array 2B are stacked in sequence, and the first antenna array 2A is located between the antenna conductive component 3 and the second antenna array 2B.
  • the antenna conductive component 3 and the first antenna array 2A may be approximately side by side (not in an obvious stacked relationship), and they may be located on the same side of the second antenna array 2B.
  • the antenna conductive component 3 may be a feed network with an electromagnetic stealth design. This will be explained below.
  • the antenna conductive component 3 may include a conductive base 31 and a structural layer 33 .
  • the conductive base 31 may be a feed network, and the feed network may include at least one of a phase shifter, a power splitter, a filter, and the like.
  • the feed network may be connected to the feed structure 222 of the first radiating unit 22 of the first antenna array 2A to realize feeding the first antenna array 2A.
  • the structural layer 33 covers at least a part of the outer surface of the conductive base 31.
  • the structural layer 33 can only cover the main functional parts of the conductive base 31 (such as including phase shifters, power splitters, and filters). etc.), or the structural layer 33 can also cover all the outer surfaces of the conductive base 31 .
  • the structural layer 33 can allow electromagnetic waves to continue propagating around the conductive base 31 and reduce or eliminate electromagnetic shadows. The specific structure and working principle of the structural layer 33 will be described in detail below.
  • the structural layer 33 can be relatively lightweight and suitable for local locations in the antenna.
  • the conductive component of the antenna may also be other components with an electromagnetic stealth design, that is, the conductive base in the conductive component of the antenna may be other conductive components other than the feed network.
  • the conductive base in the conductive component of the antenna may be other conductive components other than the feed network.
  • the pole 11 may block the signal of the antenna array 14 in the radome 13.
  • the outer surface of the pole 11 can be covered with a structural layer, and the specific distribution of the structural layer can be determined as needed.
  • the structural layer can be covered in a corresponding local area of the outer surface of the pole 11 according to the scanning range of the antenna array 14; or, the structural layer can cover the entire outer surface of the pole 11.
  • the pole 11 serves as a conductive base, and the pole 11 and the structural layer can form a conductive component of the antenna.
  • the pole support 12 can be used as a conductive base, and the pole support 12 and the structural layer thereon can constitute another conductive component of the antenna.
  • metal parts in the base station 1 can also be used as conductive bases, and these metal parts and the structural layers on them can constitute another conductive component of the antenna.
  • the antenna conductive component is located between the first antenna array and the second antenna array. same side of the face.
  • the second antenna array 2B may include a plurality of second radiating units 25 .
  • the frequency bands of each second radiating unit 25 may be consistent, or there may be at least one second radiating unit 25 whose frequency band is different from the frequency bands of the remaining second radiating units 25 .
  • the second radiation unit 25 may include a radiator 251 and a feed structure 252, both of which are connected. It can be understood that in FIG. 4 , the horizontal lines represent the radiator 251 and the vertical lines represent the feed structure 252 . This is only an illustration and does not limit the specific structures and details of the radiator 251 and the feed structure 252 . Location. It can be understood that the second antenna cover 26 may also have a reflection plate and a feed network, each second radiating unit 25 may be installed on the reflection plate, and the feed structure 252 is connected to the feed network.
  • the first antenna array 2A and the antenna conductive component 3 may be located on one side of the frequency selection surface 24
  • the second radiation unit 25 may be located on the other side of the frequency selection surface 24
  • “one side” and “the other side” of the frequency selection surface 24 may respectively be opposite two sides along the thickness direction of the frequency selection surface 24
  • the frequency selective surface 24 can also be considered to be located between the radiator 221 and the second antenna array 2B.
  • the frequency selection surface 24 as the stacking reference plane, it can be said that the first antenna array and the second antenna array are stacked, or the first antenna and the second antenna are stacked.
  • the stacked arrangement can deploy antenna arrays with more frequency bands and channels under limited antenna aperture to meet communication requirements.
  • the frequency band of the first antenna array 2A may be lower than the frequency band of the second antenna array 2B, thus ensuring the transceiver performance of the first antenna and the second antenna.
  • the frequency band of the first antenna array 2A and the frequency band of the second antenna array 2B may not be limited as above.
  • the frequency selection surface 24 may be substantially a two-dimensional planar structure as a whole.
  • the frequency selective surface 24 may include an insulating base material layer and a conductor layer, with the conductor layer attached to the insulating base material layer; or, the frequency selective surface 24 may include a conductor layer but no insulating base material layer.
  • the insulating base material layer is made of insulating material, and the conductor layer is made of conductive material.
  • the frequency selection surface 24 has good designability and can be relatively lightweight.
  • the frequency selection surface 24 can be divided into multiple frequency selection units, and all frequency selection units can be arranged in a certain manner.
  • FIG. 5(a) shows a schematic structure of a possible frequency selection surface.
  • a plurality of frequency selection units 24a can be divided into the frequency selection surface 24 (shown by criss-crossing dotted lines in Figure 5(a) Indicates the boundary between the frequency selection units 24a (the dotted line is not shown in the actual product), and the frequency selection units 24a are closely connected without gaps.
  • the frequency selection unit 24a may include two inner and outer metal parts (indicated by different hatching lines), with a gap (a blank area between the inner and outer hatched areas) between the inner and outer metal parts.
  • a plurality of slits 24h may be formed on the frequency selection surface 24, and these slits 24h may be distributed in a criss-cross pattern, for example.
  • the gap 24h may or may not penetrate the frequency selection surface 24 .
  • the frequency selection surface 24 may be divided into a plurality of frequency selection units 24a based on the gaps 24h.
  • the solid portion 24e on one side of the slot 24h and a part 24f of the slot 24h can form a frequency selection unit 24a
  • the solid portion on the other side of the slot 24h 24e and another part 24g of the gap 24h may form another frequency selection unit 24a.
  • the dotted line in Figure 5(b) can represent the dividing line between a part 24f of the gap 24h and another part 24g (the dotted line is not shown in the actual product).
  • the dotted line can, for example, be located at half the width of the gap 24h. at.
  • the frequency selection unit may be roughly a two-dimensional planar structure or a three-dimensional three-dimensional structure.
  • the structure of all frequency selection units may be the same, and such frequency selection surface 24 may be said to have a periodic array structure.
  • the structures of all frequency selection units are not exactly the same, for example, the structures of any two frequency selection units are different (each frequency selection unit can be called a first frequency selection unit); or there are at least two frequency selection units with the same structure. unit (each such frequency selection unit may be called a first frequency selection unit), but the structure of the first frequency selection unit is different from the structures of other frequency selection units.
  • Such frequency selective surface 24 may be said to have a quasi-periodic array structure.
  • the frequency selection surface 24 may have only one layer. In other embodiments, there may be multiple layers of frequency selective surfaces 24 , and each layer of frequency selective surfaces 24 may be separated by an insulating material or air.
  • the frequency selective surface 24 has a specific frequency selective function, which can be transmissive to incident waves in one frequency band and reflective to incident waves in another frequency band, thereby effectively controlling the transmission and reflection of incident electromagnetic waves.
  • the frequency selection surface 24 may be, for example, a spatial filter, which interacts with electromagnetic waves to exhibit obvious band-pass or band-rejection filtering characteristics.
  • the multi-layer frequency selective surface 24 can be used as a multi-order spatial filter, which can expand the bandwidth and increase the frequency selectivity.
  • the frequency selective surface 24 can reflect most of the electromagnetic waves radiated by the first antenna array 2A, so the frequency selective surface 24 can serve as a reflection plate of the first antenna array 2A.
  • the frequency selective surface 24 can also transmit the electromagnetic waves radiated by the second antenna array 2B. Therefore, the frequency selective surface 24 does not block the electromagnetic waves radiated by the second antenna array 2B.
  • the frequency selective surface 24 does not block the electromagnetic waves radiated by the second antenna array 2B. It is equivalent to being electromagnetically transparent.
  • the minimum distance between the frequency selection surface 24 and the antenna conductive component 3 may be no less than 0.1 times the wavelength corresponding to the highest operating frequency of the second antenna array 2B.
  • the distance between the frequency selection surface 24 and the antenna conductive component 3 is the distance between the frequency selection surface 24 and the structural layer 33 .
  • the significance of this design is that by keeping the distance between the frequency selection surface 24 and the structural layer 33 within a reasonable range (rather than being too small), strong coupling between the frequency selection surface 24 and the structural layer 33 can be avoided, thus ensuring electromagnetic stealth. Performance and frequency selective performance of the frequency selective surface 24 . In other embodiments, the above-mentioned limitation on the distance between the frequency selection surface 24 and the antenna conductive component 3 may not be imposed.
  • the frequency selection surface 24 and the first antenna array 2A may be electrically connected.
  • the frequency selective surface 24 can also be electrically connected to the feed network as conductive base body 31 . Since the frequency selection surface 24 and the second antenna array 2B are respectively in different radomes, the frequency selection surface 24 and the second antenna array 2B may also be electrically connected. In other embodiments, if the second antenna array and the first antenna array are disposed in the same radome, the frequency selection surface 24 may not be electrically connected to the second antenna array and the first antenna array.
  • no electrical connection can mean that the two are not directly connected through a conductor in structure (for example, the two are not connected at all in structure, there is a gap between them; or the two are connected through an insulator), and there is no signal coupling.
  • no electrical connection design is that since the frequency selection surface 24 has no electrical connection with the first antenna array 2A and the second antenna array 2B, the feed signal of the antenna array will not be transmitted through the frequency selection surface 24. This can shorten the feed path and reduce losses, and can also make the structure of the frequency selection surface 24 simpler and reduce costs. Since the frequency selective surface 24 is not electrically connected to the feed network as the conductive base 31, there is basically no coupling between the frequency selective surface 24 and the feed network, which can ensure the electromagnetic stealth performance and the frequency selective performance of the frequency selective surface 24.
  • the frequency selection surface 24 can also be electrically connected to the feed network as the conductive base 31, which can reduce the impact of the induced current generated by the feed network on the first antenna array 2A and the second antenna array 2B. influence and improve the performance of multi-band base station antennas.
  • FIG 6 shows the internal frame structure of the base station antenna 70 in an embodiment.
  • the second antenna of the base station antenna 70 can include two second antenna arrays 2B.
  • the two antennas Arrays 2B may be located within two second antenna covers 76 respectively.
  • the length of the first antenna array 2A may be greater than the length of either antenna array 2B, and the first antenna array 2A physically blocks the two antenna arrays 2B.
  • the radiating unit in one of the second antenna arrays 2B may include a radiator 751 (which may be called a fourth radiator), and the radiating unit in the other second antenna array 2B may include a radiator 771 (which may be called a fifth radiator). ), the frequency band of the radiator 751 and the frequency band of the radiator 771 may be different.
  • the frequency bands of the radiator 751 and the radiator 771 may be higher than the frequency band of the radiator 221 .
  • Figure 6 shows two second antenna arrays 2B in the second antenna.
  • the two second antenna arrays 2B have different frequency bands. This is just an example.
  • the second antenna may also include more than two second antenna arrays 2B. Among them, the frequency bands of all second antenna arrays 2B may be the same or different.
  • the frequency selection surface 24 can transmit electromagnetic waves from the two second antenna arrays 2B; the stealth design of the antenna conductive component 3 can improve the electromagnetic shadow problem; and the stacked design of the antenna array can operate under limited sky conditions.
  • Antenna arrays with more frequency bands and channels are set up under the surface aperture; the two antennas can be deployed separately, achieving decoupling design and flexible deployment of antennas in different frequency bands.
  • the second antenna can have multiple frequency bands, the number of frequency bands and the number of channels are further expanded.
  • FIG 7 shows the internal frame structure of the base station antenna 80 in one embodiment. Different from the base station antenna 2 shown in Figure 4, in the base station In the antenna 80 , the feed structure 222 of the first radiating unit 22 can pass through the through hole on the frequency selection surface 84 to extend to the other side of the frequency selection surface 84 , so that the first radiator 221 and the antenna conductive component 3 are located respectively. Opposite sides of the frequency selection surface 84 . It can be understood that the frequency selective surface 84 is also located between the first radiator 221 and the second antenna array 2B.
  • the position of the frequency selection surface 84 can be determined according to the antenna design requirements. And arranging the antenna conductive component 3 on the side of the frequency selection surface 84 facing away from the first radiator 221 makes the distance between the antenna conductive component 3 and the first radiator 221 larger, which can reduce the number of antenna conductive components 3 (including the feed network). ) affects the near-field coupling of the first antenna array 2A to ensure the performance of the first antenna array 2A.
  • Figure 8 shows the internal frame structure of the base station antenna 90 in one embodiment.
  • the embodiment shown in FIG. 8 can be regarded as a combination of the embodiments shown in FIG. 4 and FIG. 7 .
  • the first frequency selection surface 941 and the second frequency selection surface 942 there may be two frequency selection surfaces in the first antenna, which are respectively called the first frequency selection surface 941 and the second frequency selection surface 942 .
  • the first frequency selection surface 941 and the second frequency selection surface 942 are stacked and arranged at intervals.
  • the feed structure 222 of the first radiating unit 22 can pass through the through hole on the first frequency selection surface 941 to extend to the first frequency selection surface 941 on the other side, so that the first radiator 221 and the antenna conductive component 3 are respectively located on opposite sides of the first frequency selection surface 941.
  • the second frequency selection surface 942 may be located between the antenna conductive component 3 and the second antenna array 2B. It can be understood that the first frequency selection surface 941 is also located between the first radiator 221 and the second frequency selection surface 942 , and the antenna conductive component 3 is located between the first frequency selection surface 941 and the second frequency selection surface 942 .
  • the positions of the first frequency selection surface 941 and the second frequency selection surface 942 can be determined according to antenna design requirements.
  • the thickness (for example, the vertical dimension in FIG. 8 ) of the antenna conductive component 3 (the conductive base 31 is the feed network) can be made smaller so that it can be located on the first frequency selection surface 941 and the second frequency selection surface. 942, which can make the total thickness of the first antenna smaller.
  • the multi-layer frequency selection surface can enhance the filtering selectivity and help expand the bandwidth of the second antenna.
  • the position of the second frequency selection surface 942 may also be: the second frequency selection surface 942 is passed through the feed structure 222 , and the second frequency selection surface 942 is located on the first Between the radiator 221 and the antenna conductive component 3 , the second frequency selection surface 942 is farther from the first radiator 221 , and the first frequency selection surface 941 is closer to the first radiator 221 .
  • the second frequency selection surface 942 may be penetrated by the antenna conductive component 3 , the first radiating unit 22 and a part of the antenna conductive component 3 are located on one side of the second frequency selection surface 942 , and the other part of the antenna conductive component 3 and the second frequency selection surface 942 may be penetrated by the antenna conductive component 3 .
  • Antenna array 2B is located on the other side of second frequency selection surface 942 .
  • FIG. 9 shows the internal frame structure of the base station antenna 100 in another embodiment.
  • the embodiment shown in FIG. 9 can be considered as a modification based on the embodiment shown in FIG. 8 , wherein the view direction of FIG. 9 can be as shown in FIG. Side view direction in 8.
  • Figure 9 illustrates a plurality of antenna conductive components 3 (feed networks covered with structural layers 33).
  • the feed network in each antenna conductive component 3 can be connected to a plurality of first conductive components distributed in a direction perpendicular to the screen.
  • the feed structures 222 of the radiating unit 22 are connected (due to the viewing angle, only each feed network is shown to be connected to one feed structure 222).
  • the antenna conductive component 3 can pass through the through hole on the first frequency selection surface 141 to extend to the other side of the first frequency selection surface 141,
  • the first radiating unit 22 and a part of the antenna conductive component 3 are located on one side of the first frequency selection surface 141
  • the other part of the antenna conductive component 3 is located on the other side of the first frequency selection surface 141 .
  • the second frequency selection surface 142 may be located between the first frequency selection surface 141 and the second antenna array 2B. It can be understood that the first frequency selection surface 141 is also located between the first radiator 221 and the second frequency selection surface 142 .
  • the positions of the first frequency selection surface 141 and the second frequency selection surface 142 can be determined according to antenna design requirements.
  • the antenna conductive component 3 the conductive base 31 is the feed network
  • the distance between the feed network and the first radiator 221 is not too large (compared to the implementation shown in FIG. 8 For example), thereby reducing the loss; and making the distance between the feed network and the first radiator 221 not too small (compared to the fact that the antenna conductive component 3 and the first radiating unit 22 are completely located on the first frequency selection surface 141 scheme on the same side) to improve the influence of the feed network on the near-field coupling of the first antenna array 2A.
  • the multi-layer frequency selection surface can enhance the filtering selectivity and help expand the bandwidth of the second antenna.
  • the position of the second frequency selection surface 142 can also be: like the first frequency selection surface 141 , the second frequency selection surface 142 is also penetrated by the antenna conductive component 3 , the first radiating unit 22 and a part of the antenna conductive component 3 are located on one side of the second frequency selection surface 142, and the other part of the antenna conductive component 3 is located on the other side of the second frequency selection surface 142.
  • the first frequency selection surface 141 may Closer to the first radiating unit 22
  • the second frequency selective surface 142 may be further away from the first radiating unit 22 .
  • the radiating unit of the first antenna array of the base station antenna may include a plurality of different frequency bands Radiators, such as radiators 211 (which can be called second radiators) and radiators 213 (which can be called third radiators) in different frequency bands.
  • the arrangement of radiators in different frequency bands can be designed as needed.
  • a row of radiators 211 and a row of radiators 213 can be arranged alternately, that is, according to one row of radiators 211 - one row of radiators 213 - one row of radiators.
  • radiators in different frequency bands can all be electrically connected to the frequency selective surface, and the frequency selective surface can reflect the radiation signals of the radiators in all frequency bands.
  • the feed network in the conductive component of the antenna may include a first feed network 212 and a second feed network 214.
  • the first feed network 212 is electrically connected to the radiator 211 to provide power to the radiator. 211 feeds power
  • the second feeding network 214 is electrically connected to the radiator 213 to feed power to the radiator 213 .
  • Both the first feed network 212 and the second feed network 214 have electromagnetic stealth performance.
  • the first feed network 212 and the second feed network 214 may both be electrically connected to the frequency selective surface.
  • the first antenna array include multiple frequency bands
  • the number of frequency bands and channels of the base station antenna can be increased, thereby increasing the antenna aperture utilization.
  • the mutual coupling between the radiators of different frequency bands in the first radome 21 can be weakened, ensuring the electromagnetic stealth performance and frequency. Select surfaces for frequency selective performance, ultimately improving antenna performance.
  • the minimum distance between the frequency selection surface and the antenna conductive component can be limited (the minimum distance may not be less than 0.1 times the wavelength corresponding to the highest operating frequency of the second antenna array) to avoid frequency A strong coupling is generated between the selective surface and the structural layer, thereby ensuring the electromagnetic stealth performance and the frequency selective performance of the frequency selective surface 24 .
  • the frequency selective surface can be manufactured to have a quasi-periodic array structure to achieve the purpose of reducing the coupling between the frequency selective surface and the structural layer. This is explained below.
  • 11(a) and 11(b) take the antenna conductive component 3 and a layer of frequency selective surface 24 located below the antenna conductive component 3 as examples to illustrate the quasi-periodic array structure of the frequency selective surface. It can be understood that this does not limit the number of frequency selective surfaces and their relative positions to the conductive components of the antenna, nor does it limit the structure and type of the conductive components of the antenna. In fact, the design of the quasi-periodic array structure of the frequency selective surface It can be applied to any of the above embodiments.
  • the frequency selection surface 24 includes a plurality of frequency selection units 24b and a plurality of frequency selection units 24c.
  • the frequency selection unit 24c (which can be called the first frequency selection unit) has a different structure from the frequency selection unit 24b, or in other words, the frequency selection unit 24c has a different structure from other frequency selection units in the frequency selection surface 24.
  • the frequency selection unit 24c may be a frequency selection unit close to the antenna conductive component 3.
  • the frequency selection unit 24c may overlap with the orthographic projection of the antenna conductive component 3 on the frequency selection surface 24.
  • “There is overlap” may include that the frequency selection unit 24c completely overlaps with the front projection, or a part of the frequency selection unit 24c overlaps with a part of the front projection (the frequency selection unit 24c is misaligned with the front projection), or a part of the frequency selection unit 24c overlaps with all of the orthographic projection (the frequency selection unit 24c is larger, the orthographic projection is smaller, and the orthographic projection is all located within the boundary of the frequency selection unit 24c), or the entire area of the frequency selection unit 24c overlaps with the orthoprojection Partial overlap (the frequency selection unit 24c is smaller, the orthographic projection is larger, and the frequency selection unit 24c is all located within the boundary of the orthographic projection), etc.
  • the above-mentioned quasi-periodic array structure design can be performed on all the frequency selection surfaces 24 , or only the frequency selection surface 24 that is closer to the antenna conductive component 3 can be subjected to the above-mentioned quasi-periodic array structure design.
  • Array structure design if the frequency selection surface 24 has more than two layers, the above-mentioned quasi-periodic array structure design can be performed on all the frequency selection surfaces 24 , or only the frequency selection surface 24 that is closer to the antenna conductive component 3 can be subjected to the above-mentioned quasi-periodic array structure design.
  • the frequency selection surface 24 by manufacturing the frequency selection surface 24 into a quasi-periodic array structure, the structure of the frequency selection unit close to the antenna conductive component 3 is different from the structure of other frequency selection units, and the distance between the frequency selection surface 24 and the structural layer 3 can be reduced. The coupling between them ensures the electromagnetic stealth performance and the frequency selective performance of the frequency selective surface 24 .
  • the solution of this embodiment can be applied to the following scenarios: If the distance between the frequency selection surface and the conductive component of the antenna cannot meet the minimum spacing requirement due to product design limitations, the solution of this embodiment can be used to reduce the frequency selection surface and structure. Coupling between layers. It can be understood that in a scenario where the distance between the frequency selection surface and the conductive component of the antenna already meets the minimum distance requirement, the solution of this embodiment can still be adopted to further reduce the coupling between the frequency selection surface and the structural layer.
  • the area 24d of the frequency selection surface that is originally a periodic array structure and close to the antenna conductive component 3 can be The conductor layer is removed to create a frequency selective surface 24 having a quasi-periodic array structure.
  • the region 24d can only have insulating material but no conductor material, and frequency selection units 24b can be distributed on both sides of the region 24d.
  • the frequency selection unit 24b can include Insulating material and conductive material; for the frequency selective surface 24 without an insulating base material layer, the region 24d can be hollowed out, and the frequency selective unit 24b can only contain conductive material.
  • the area 24d may overlap with the orthographic projection of the antenna conductive component 3 on the frequency selection surface 24, and the meaning of "overlapping" here may be consistent with that described above.
  • the frequency selective surface 24 can be considered to include a first part and a second part, the first part is connected to the second part, the first part is the part where the region 24d is located, the first part does not contain conductive material, and the second part is The second part, in which the frequency selection unit 24b is located, contains conductive material.
  • the solution of this embodiment can greatly reduce the coupling between the frequency selection surface and the structural layer by removing the conductor layer in the area of the frequency selection surface close to the antenna conductive component 3 .
  • each antenna conductive component described below can be applied to the base station antenna in any embodiment of the present application.
  • each antenna conductive component described below can be applied to the base station antenna in any embodiment of the present application.
  • FIG. 12 illustrates a schematic three-dimensional structure of the antenna conductive component 3 in FIG. 4
  • FIG. 13 illustrates a schematic side view structure of the antenna conductive component 3 in FIG. 12
  • the antenna conductive component 3 may include a conductive base 31 and a structural layer 33
  • the structural layer 33 includes at least two structural units 32 .
  • the conductive base 31 may be substantially cylindrical, and its axial length is, for example, at least 1* ⁇ ( ⁇ is the wavelength corresponding to the lowest frequency band of the second antenna array 2B blocked by the conductive base 31). It can be understood that the substantially cylindrical conductive base 31 is only an example, and the embodiments of the present application do not limit the actual shape and structure of the conductive base.
  • the cross-sectional shape of the conductive substrate includes, but is not limited to, quadrangular, circular, elliptical, hexagonal, etc.
  • Figure 12 schematically depicts five structural units 32.
  • the structure of the structural unit 32 can be designed as needed, for example, it can be sheet-shaped, ring-shaped, etc.
  • all structural units 32 are located outside the conductive base 31 .
  • these structural units 32 may only surround the outer peripheral surface of the conductive base 31 (the outer peripheral surface is the surface surrounding the axis of the conductive base 31 ) and circle the outer periphery, and are not provided on the conductive base 31 .
  • the structural units 32 can be distributed on the outer peripheral surface and the end surface at the same time. The following description will continue with the implementation shown in FIG. 12 as an example.
  • the structural unit 32 may be made of a conductor material. Such structural unit 32 may be, for example, a sheet metal-formed metal piece, which has greater weight and structural strength.
  • the structural unit 32 may include a conductor layer and an insulating layer, which are stacked, with the insulating layer close to the conductive base 31 and the conductor layer facing away from the conductive base 31 .
  • the conductor layer is made of conductive material, and the insulating layer is made of insulating material.
  • the conductor layer can be thin and the structural strength is weak.
  • the conductor layer is attached to the insulating layer, and the insulating layer can support and strengthen the conductor layer.
  • each structural unit 32 and the conductive base 31 there may be a gap 3 a between each structural unit 32 and the conductive base 31 , that is, each structural unit 32 and the conductive base 31 may be separated, and they are not directly connected.
  • the radial size of the gap 3a (that is, the radial size of the gap 3a along the conductive base 31, which may also be called the electrical thickness) may be, for example, 0.5* ⁇ ( ⁇ is the thickness of the second antenna array 2B blocked by the conductive base 31 The wavelength corresponding to the lowest frequency band).
  • the gap 3a between the structural unit 32 and the conductive base 31 can be filled with an insulating medium (the insulation is represented by diagonal hatching in Figure 13 medium).
  • the insulating medium can be continuously distributed and cover the entire outer circumferential surface of the conductive base 31 , that is, the insulating medium is distributed both in the intervals 3 a and in the gaps between adjacent structural units 32 (the gaps will be in (Explanation continues below).
  • the insulating medium is distributed discretely on the entire outer circumferential surface of the conductive base 31 .
  • the insulating medium is only distributed in the intervals 3 a but not in the gaps between adjacent structural units 32 .
  • the insulating medium in each interval 3a can be distributed discretely, the insulating medium everywhere forms a structure similar to several connecting pillars, gaps are formed between the insulating medium everywhere, and air exists in the gap; or, each The insulating medium within interval 3a is continuously distributed.
  • the insulating medium can not only connect the structural unit 32 and the conductive base 31 , but also electrically isolate the structural unit 32 and the conductive base 31 .
  • the insulating medium everywhere on the outer peripheral surface of the conductive base 31 may be of the same material, that is, the insulating medium everywhere on the outer peripheral surface of the conductive base 31 has the same dielectric constant.
  • the insulating medium at various places on the outer circumferential surface of the conductive base may be different materials with different dielectric constants, which will be further described below.
  • the insulating layer in the structural unit 32 can replace the insulating medium in the interval 3a, that is, this structural unit 32 includes a conductor layer and an insulating layer. It can be connected to the conductive base 31, and there may be no gap between the structural unit 32 and the conductive base 31. It can be understood that, according to product requirements, there may also be a gap between the structural unit 32 including a conductor layer and an insulating layer and the conductive base 31, and the gap may be additionally filled with an insulating medium.
  • the above-mentioned insulating medium may also be called an insulating bracket.
  • the insulating bracket serves to connect and isolate the structural unit 32 and the conductive base 31 .
  • the structural unit 32 includes an insulating layer and a conductive layer, the junction
  • the insulating layer in the structural unit 32 may also be called an insulating bracket.
  • the structural unit 32 is connected to the conductive base 31 through the insulating bracket and is isolated from the conductive base 31 .
  • all structural units 32 can be distributed sequentially along the axial direction of the conductive base 31 , and every two adjacent structural units 32 (one structural unit 32 can be called the first structural unit, and the other structural unit 32 can be called the first structural unit).
  • a gap may be formed between the units 32 (called second structural units), and the gap surrounds the conductive base 31 .
  • the above-mentioned insulating medium may be distributed in the gap, or may not be distributed in the gap.
  • Each structural unit 32 has conductive properties, so that the gap can actually form a capacitor, which can be called the first capacitor 32a.
  • the structural units 32 on both sides of the first capacitor 32a can serve as the plates of the first capacitor 32a.
  • the insulating medium in the gap can also be a component of the first capacitor 32a.
  • the first capacitor 32a may include a first part 32b, a second part 32c, a third part 32d and a fourth part 32e, and these four areas are connected end to end in sequence.
  • the first part 32b and the third part 32d may be centrally symmetrical, and the center of symmetry of the two parts may be the axis of the conductive base 31 .
  • the first part 32b and the third part 32d are centrally symmetrically distributed, which means that the structures of the two are consistent (the consistent structure includes the distribution of the insulating medium in the two areas). One of them coincides with the other after rotating 180 degrees around the center of symmetry. .
  • the second part 32c and the fourth part 32e may be centrally symmetrical, and the center of symmetry of the two parts may be the axis of the conductive base 31 .
  • the second part 32c and the fourth part 32e are centrally symmetrically distributed, which means that the structures of the two are consistent (the consistent structure includes the distribution of the insulating medium in the two areas). One of them is rotated 180 degrees around the center of symmetry and is connected to the other. coincide.
  • the electrode plates are the structural units 32 on both sides of the first capacitor 32a, and the medium between the electrode plates is the insulating medium (for the case where the insulating medium is distributed in the gap between the structural units 32) or air (for the situation between the structural units 32). There is no insulating medium in the gap between them), S is the facing area of the adjacent structural unit 32, and d is the width of the gap.
  • the capacitance values of the first part 32b and the third part 32d are equal.
  • the second part 32c and the fourth part 32e are centrally symmetrically distributed, the capacitance values of the second part 32c and the fourth part 32e are equal. The following will take the first part 32b and the second part 32c as the description object, and continue to explain the characteristics of the first capacitor 32a.
  • the corresponding gap in the first part 32b can have a uniform width, that is, the two sides of the gap in the first part 32b are basically parallel, and the width of the gap everywhere in the first part 32b can be the same, or it can be said that the gap in the first part 32b has the same width.
  • the gap corresponding to the second part 32c may have a non-uniform width, that is, the two sides of the gap in the second part 32c are not parallel, and the width of the gap everywhere in the second part 32c is inconsistent, or it is said that the gap in the second part 32c has a variable width.
  • the two sides of the gap in the second part 32c can be curves (for example, arcs), the width of the gap at both ends of the second part 32c can be smaller, and the width of the gap in the middle between the two ends can be larger. , the gap width from both ends to the middle may be gradual, thereby making the gap widths everywhere in the second part 32c inconsistent.
  • the maximum width of the gap in the first part 32b may be less than or equal to the minimum width of the gap in the second part 32c (for example, the second part 32c is adjacent to the first part 32b (the gap width at ), that is, overall, the gap width of the first part 32b is smaller than the gap width of the second part 32c. Therefore, according to the above capacitance formula, it can be known that the capacitance value of the first part 32b is greater than the capacitance value of the second part 32c.
  • the shapes of all structural units 32 can be consistent and evenly spaced, so that the shapes of all slits are also consistent and evenly spaced.
  • the structural layer 33 thus formed can be said to have a periodic structure.
  • the shapes of all structural units 32 may not be exactly the same (meaning that any two structural units 32 have different shapes).
  • at least two structural units 32 may have the same shape, but not all structural units 32 may have the same shape. same), and/or, all structural units 32 may not be evenly spaced (meaning that for all gaps between structural units 32, the shapes of any two gaps are different; or at least two gaps have the same shape, but not All gaps have the same shape).
  • a quasi-periodic structure may be a structure obtained by deleting several structural units from a periodic structure.
  • the structural layer with a quasi-periodic structure can be adapted to the shape and structure of the conductive base 31 . For example, if there is a protrusion somewhere on the outer surface of the conductive base 31, the structural layer can avoid the protrusion there to form a quasi-periodic structure.
  • the electromagnetic stealth principle of the antenna conductive component 3 will be explained below.
  • Figures 12 and 13 also show the relationship between the wave source and the antenna conductive component 3, where the wave source refers to the source of the electromagnetic wave.
  • the wave source is the second antenna array 2B; for the second antenna array In the receiving process of 2B, the wave source can be understood as the air ring territory.
  • K represents the propagation direction of electromagnetic waves
  • E represents the direction of the electric field
  • H represents the direction of the magnetic field.
  • the origin of the coordinate system can refer to the position of the wave source.
  • the narrower first part 32b can be closest to the wave source, and the narrower third part 32d can be farthest from the wave source.
  • the electromagnetic wave K will change the propagation direction and be constrained to propagate in the gap along the extension direction of the gap.
  • the electromagnetic wave can propagate in two ways. One electromagnetic wave propagates along the paths of the first part 32b, the second part 32c and the third part 32d, and the other electromagnetic wave propagates along the paths of the first part 32b, the fourth part 32e and the third part 32d. Three parts of 32d path propagation. When the two electromagnetic waves propagate to the third part 32d, they will be emitted from the third part 32d in the propagation direction K.
  • the first part 32b can receive electromagnetic waves from the wave source, and the third part 32d can emit electromagnetic waves.
  • the first part 32b and the third part 32d are equivalent to patch antennas.
  • the second part 32c and the fourth part 32e can confine electromagnetic waves therein for transmission, and they can be equivalent to slot lines.
  • the function of the first capacitor 32a is to change the propagation direction of the electromagnetic wave emitted by the wave source and constrain the electromagnetic wave to propagate within it, so that the electromagnetic wave can propagate around the antenna conductive component 3 and can keep the electromagnetic wave from the first capacitor.
  • the propagation direction remains unchanged when 32a is ejected. Therefore, even if the antenna conductive component 3 blocks the wave source, the electromagnetic wave can bypass the antenna conductive component 3 and propagate to the rear of the antenna conductive component 3 due to the presence of the first capacitor 32a, thereby reducing or eliminating electromagnetic shadows.
  • the propagation direction of the electromagnetic wave does not need to be changed, the propagation characteristics of the electromagnetic wave can be ensured to remain unchanged.
  • the antenna conductive component 3 of this embodiment disposes at least two structural units 32 on the outer periphery of the conductive base 31 and forms the first capacitor 32a, so that the conductive base 31 has electromagnetic stealth performance relative to electromagnetic waves, thereby avoiding or reducing the need for 31 Blocking of electromagnetic waves.
  • the electromagnetic wave signals of different frequency bands can resonate in the gap with their respective electrical lengths, so that the electromagnetic waves of different frequency bands can pass through the gap. That is, by making the capacitance values of different areas of the first capacitor 32a different, the gap can allow electromagnetic waves of multiple frequency bands to pass through, thereby expanding the stealth bandwidth.
  • first capacitor 32a in the antenna conductive component 3
  • the shielding of electromagnetic waves by the conductive base 31 can be improved and the stealth bandwidth can be expanded.
  • the number of first capacitors 32a may be multiple according to actual needs.
  • the design with a larger capacitance value in the first part 32b close to the wave source can meet the propagation needs of electromagnetic waves in some frequency bands, but this is not a limitation on the embodiment of the present application.
  • the corresponding relationship between the capacitance value of each area of the first capacitor 32a and the distance from the wave source can be designed as needed, and is not limited to the above. For example, for electromagnetic waves in some frequency bands, a region in the first capacitor 32a that is closer to the wave source can be made to have a smaller capacitance value.
  • the gap in the first part 32b close to the wave source has a uniform width
  • the gap in the second part 32c slightly farther away from the wave source has a non-uniform width.
  • the gap of the first part 32b close to the wave source have a non-uniform width
  • the minimum gap width that is, the gap width anywhere in the second part 32c
  • the first capacitor 32a is divided into four parts by changing the width of the gap.
  • the width of the gap can also be designed to change from the first capacitor to the first capacitor.
  • Other quantities are divided into 32a.
  • the gap in the embodiment of the present application only needs to be a non-constant width gap, so that the purpose of expanding the stealth bandwidth can be achieved.
  • the first part 32b is centrally symmetrical to the third part 32d
  • the second part 32c is centrally symmetrical to the fourth part 32e.
  • This design can ensure that the electromagnetic wave maintains its previous propagation direction and propagation characteristics after being emitted through the first capacitor 32a. (such as polarization characteristics, frequency band, etc.).
  • this design is only an example and does not limit the embodiments of the present application.
  • the shapes of the first part 32b and the third part 32d can only be consistent, but the positions are not required to be centrally symmetrical.
  • the electromagnetic waves emitted from the first capacitor 32a are refracted to other directions to expand the signal scanning range of the second antenna array 2B (for example, a multiple-input multiple-output MIMO antenna can apply this solution).
  • the shapes of the first portion 32b and the third portion 32d can be different, and the positions do not require central symmetry.
  • the antenna conductive component 3 in the base station antenna 2 may be a feed network covered with a structural layer 33.
  • the antenna conductive component 3 has a certain shielding effect on the second antenna array 2B.
  • the electromagnetic waves radiated by the second antenna array 2B will continue to propagate around the antenna conductive component 3, or the electromagnetic waves will bypass the antenna conductive component. 3 is received by the second antenna array 2B, thereby reducing or eliminating electromagnetic shadows.
  • the second antenna array 2B can have a large-angle scanning capability, and its aperture (such as the horizontal aperture in Figure 4) can be expanded without being blocked or restricted by the feed network of the first antenna in front. .
  • the conductive base 41 of the antenna conductive component 4 may have a substantially rectangular columnar structure.
  • the structural unit 42 may be roughly a square cylindrical structure surrounded by four flat plates.
  • a capacitor may include a first portion 42b and a second portion 42c.
  • the first part 42b may be located on the periphery of one side of the conductive base 41, and the second part 42c may be located on the outer periphery of the other side of the conductive base 41.
  • the adjacent position of the first part 42b and the second part 42c may correspond to the edge of the conductive base 41.
  • both the first part 42b and the second part 42c may be rectangular areas, and the gaps between the first part 42b and the second part 42c have uniform widths.
  • the gap width of the first portion 42b may be smaller than the gap width of the second portion 42c.
  • the first capacitor of the structural unit 42 may also include a third part and a fourth part (not shown due to the perspective of FIG. 14).
  • the third part and the first part 42b may be centrally symmetrical, and the fourth part and the fourth part may be centrally symmetrical.
  • the two portions 42c may be centrally symmetrical.
  • the capacitance value of the first part 42b is greater than the capacitance value of the second part 42c. That is, the gap widths in different areas of the first capacitor are different, resulting in different capacitance values in different areas of the first capacitor.
  • the propagation direction K of the electromagnetic wave can be perpendicular to the side surface where the first part 42b of the antenna conductive component 4 is located.
  • the solution of this embodiment is not limited to this.
  • the side surface where the first part 42b is located can also be Not perpendicular to the propagation direction K.
  • the solution of this embodiment enables the conductive substrate 41 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 41, and can also expand the stealth bandwidth.
  • the structure of the gap on the antenna conductive component 4 is simple, has good mass production, and can meet specific product requirements.
  • a capacitor may include a first part 52b and a second part 52c, wherein the gap in the first part 52b may be formed by bending and connecting at least two sub-slits 52d in sequence, that is, several sub-slits 52d are connected in sequence, and each two adjacent terminal slots 52d Form a bent corner.
  • the bending angle between the sub-slits 52d can be designed as needed, for example, it can be 90°.
  • gaps in the first portion 52b may form a square wave-like shape.
  • the bending angle of adjacent sub-slots 52d may not be limited to 90°, so that the slots of the first part 52b form other shapes, such as curved shapes (such as sinusoids, parabolas, etc.).
  • each sub-slot 52d may have a uniform width, and all sub-slits 52d have the same width, so the width of the sub-slit 52d is also the slot width d1 of the first part 52b.
  • the slit of the second part 52c has a uniform width, and the slit width d2 of the second part 52c may be greater than the slit width of the first part 52b.
  • the total gap length formed by connecting all the sub-slits 52d in the first part 52b may be greater than the gap length of the second part 52c.
  • ⁇ the dielectric constant of the medium between the plates
  • S the area of the plates
  • d the distance between the plates
  • the gap length and gap width of different regions of the first capacitor can be configured so that the capacitance values of different regions of the first capacitor are different.
  • the solution of this embodiment enables the conductive substrate 51 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 41, and can also expand the stealth bandwidth.
  • the solution of this embodiment can be applied in the following scenarios: when due to limitations of the manufacturing process, it is impossible to manufacture the first part of a regular shape (such as a rectangular shape) with a gap width smaller than a threshold, you can consider designing the first part as shown in Figure 15
  • the first part 52b shown in (a) (the first part 52b can be considered as an irregular shape) increases the gap length to compensate for the process limitation that the gap width cannot be made small, ultimately making the first part have a larger capacitance value. Therefore, the design of this embodiment can match the existing manufacturing process and has good mass production.
  • the first part can be formed by bending and connecting at least two sub-slits in sequence, the slit length of the first part is greater than the slit length of the second part, each sub-slit has a uniform width, and the width of all sub-slits Consistent, the slit in the second part has a uniform width, and the slit width in the second part is equal to the slit width in the first part.
  • the first part can be formed by bending and connecting at least two sub-slits in sequence, and the slit length of the first part is greater than the slit length of the second part, but the width of the sub-slits is not limited (for example The sub-slits may have non-uniform slits, the widths of all sub-slits are not all the same, etc.), and the gap width of the second part is not limited (for example, the second slit may have non-uniform widths, and the gap width of the second slit is not limited to the width of the sub-slits). the width of the gap).
  • the first part can be formed by at least two sections of sub-slits being bent and connected in sequence
  • the second part can also be formed by at least two sections of sub-slits being bent and connected in sequence. There is no limit to this. .
  • the first capacitance between 62 may include a first portion 62b and a second portion 62c.
  • the second part 62c can span one edge of the conductive base 61 and can be distributed on the periphery of two adjacent sides of the conductive base 61, that is, a part of the second part 62c is located on one side, and the other part of the second part 62c is located on one side. One part is located on the other side, and the two parts of the second part 62c are bent and connected.
  • the first part 62b may span another edge of the conductive base 61 and may be distributed on the periphery of the other two adjacent sides of the conductive base 61 (due to the perspective of FIG. 16, the complete first part 62b is not shown).
  • the propagation direction K of the electromagnetic wave is not perpendicular to any side surface of the antenna conductive component 6 .
  • the solution of this embodiment enables the conductive substrate 61 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 61, and can also expand the stealth bandwidth.
  • the structure of the gap on the antenna conductive component 6 is simple, has good mass production, and can meet specific product requirements. A specific application of the solution shown in Figure 16 will be described below.
  • Figures 17 and 18 show the specific application of the electromagnetic stealth design shown in Figure 16 in a base station antenna 2'. In order to highlight the key points, Figure 18 only enlarges the right side of the base station antenna 2' in Figure 17. Side part.
  • the base station antenna 2' may include a first antenna and a second antenna arranged in a stack.
  • the first antenna may include a first radome 21 , a first antenna array 2A, a frequency selection surface 24 and an antenna conductive component 6 .
  • the first radiating unit 22 of the first antenna array 2A may include a radiating unit 223 and a radiating unit 224, and each of the radiating unit 223 and the radiating unit 224 may be multiple.
  • the working frequency bands of the radiating unit 223 and the radiating unit 224 may be different.
  • the working frequency band of the radiating unit 223 may be 690MHz-960MHz
  • the working frequency band of the radiating unit 224 may be 1427MHz-2690MHz. Both the radiating unit 223 and the radiating unit 224 may be connected to respective feed networks.
  • the frequency selection surface 24 may, for example, have two layers.
  • the antenna conductive component 6 and the first antenna array 2A may be located on the same side of the front of the second antenna array 2B (to be described below).
  • the conductive base 61 in the antenna conductive component 6 may be a phase shifter in the feed network
  • the structural layer 63 in the antenna conductive component 6 is provided on the outer periphery of the phase shifter.
  • the first capacitor in the structural layer 63 includes a first part 62b, a second part 62c, a third part 62d and a fourth part 62e.
  • the first part 62b is centrally symmetrical to the third part 62d
  • the second part 62c is centrally symmetrical to the fourth part 62e.
  • the second antenna may include a second antenna cover 26 and a second antenna array 2B.
  • the working frequency band of the second radiating unit 25 of the second antenna array 2B may be 3.3GHz-3.8GHz. It can be understood that other components may also be disposed in the second antenna cover 26 , such as a feed network connected to the second radiating unit 25 .
  • the second radiating unit 25 is closest to the first part 62b.
  • the electromagnetic waves radiated by the second radiating unit 25 will generally propagate in the "oblique direction" to two adjacent sides of the antenna conductive component 6, so that the first part 62b is distributed on these two sides, so that the first part 62b can receive the electromagnetic waves and transmit the electromagnetic waves to the two adjacent sides.
  • the confinement propagates within the first capacitor, eventually causing the electromagnetic wave to emit from the third portion 62d.
  • the first portion 62b is distributed "across the edge of the phase shifter"
  • the second portion 62c, the third portion 62d and the fourth portion 62e are also distributed "across the edge of the phase shifter”. It can be seen from this that the different capacitance value areas of the first capacitor are distributed on two adjacent sides of the phase shifter, which can match the position of the wave source, thereby achieving a better electromagnetic stealth effect.
  • the antenna conductive component 7 includes a conductive base 71 and at least two structural units 72 , and a conductive component 72 is formed between adjacent structural units 72 .
  • the first capacitor may include a first part 72b and a second part 72c.
  • the structural unit 72 of this embodiment is not an integrated structure, but has a coupling gap inside, and the parts of the structural unit 72 located on both sides of the coupling gap are completely disconnected. Without connection, the parts on both sides of the coupling gap can be coupled through the coupling gap.
  • the structural unit 72 may include a first part 721, a second part 722, a third part 723 and a fourth part 724, and these four parts may be located on different sides of the conductive base 71 respectively.
  • coupling gap 72f between the first part 721 and the second part 722
  • a coupling gap 72g between the second part 722 and the third part 723
  • a coupling gap 72h between the third part 723 and the fourth part 724
  • the fourth part There is a coupling gap 72i between 724 and the first part 721.
  • the above-mentioned four coupling gaps can separate the structural unit 72 into four independent parts. When the electromagnetic wave propagates to the structural unit 72, the electromagnetic wave can "cross" these coupling gaps, so the parts of the structural unit 72 located on both sides of the coupling gap are coupled through the coupling gaps.
  • each coupling gap extends along the edge of the conductive base 71 .
  • the structural unit 72 has four coupling slits, which separate the structural unit 72 into four independent parts.
  • the above are only examples and are not limitations of this embodiment. According to product needs, the position and extension direction of the coupling gap can be flexibly designed, and the number of coupling gaps can be at least one. In addition, all structural units 72 may have coupling gaps, or only some structural units 72 may have coupling gaps.
  • a coupling gap is formed in the structural unit 72 to facilitate the assembly of different parts of the structural unit 72 onto the conductive base 71 in sequence, and finally to form a complete structural unit 72.
  • This can realize the coupling of the structural unit 72 in some scenarios. Reliable assembly.
  • the separate assembly method can simplify the assembly process and improve the assembly yield.
  • the coupling gap can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna conductive component 7 has a certain role in expanding the stealth bandwidth.
  • the antenna conductive component 8 includes a conductive base 81 and at least two structural units 82 , and a structure formed between adjacent structural units 82
  • the first capacitor may include a first part 82b and a second part 82c.
  • the structural unit 82 is not an integral structure, but has a coupling gap inside. The parts of the structural unit 82 on both sides of the coupling gap are completely disconnected and the parts on both sides of the coupling gap can be coupled through the coupling gap.
  • the structural unit 82 of this embodiment may have a coupling gap 82f and a coupling gap 82g.
  • the coupling gap 82f and the coupling gap 82g may be located at opposite sides of the structural unit 82 respectively. side.
  • both the coupling gap 82f and the coupling gap 82g can be approximately in the middle of the side of the structural unit 82, rather than at the edge of the structural unit 82.
  • the coupling gap 82f and the coupling gap 82g can separate the structural unit 82 into a first part 821 and a second part 822, and both the first part 821 and the second part 822 can have an approximately C-shaped structure.
  • the structural layer of this embodiment may have a periodic structure, so the coupling gaps on the same side of all structural units 82 may be collinear.
  • a coupling gap is formed in the structural unit 82 to facilitate the assembly of different parts of the structural unit 82 onto the conductive base 81 in sequence, and finally to form a complete structural unit 82.
  • This can realize the coupling of the structural unit 82 in some scenarios. Reliable assembly.
  • the separate assembly method can simplify the assembly process and improve the assembly yield. Since the number of components of the structural unit 82 is small, the assembly process can be simplified to a certain extent.
  • the coupling gap can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna conductive component 8 has a certain role in expanding the stealth bandwidth.
  • the antenna conductive component 9 includes a conductive base 91 and at least two structural units 92 , and a structure formed between adjacent structural units 92
  • the first capacitor may include a first part 92b and a second part 92c.
  • each structural unit 92 can be hollowed out to form a hollow area.
  • hollows can be formed on two opposite sides of each structural unit 92 to form hollow regions 92f and 92g respectively.
  • the position and number of the hollow areas can be designed according to product requirements, and are not limited to those shown in Figure 15 . For example, as long as at least one structural unit 92 forms a hollow area.
  • forming a hollow area on the structural unit 92 can reduce the weight, which is beneficial to reducing the weight of the antenna conductive component 9 .
  • the structural unit 92 is a heavier metal piece, providing a hollow area can greatly reduce the weight.
  • the electromagnetic field is mainly distributed at the first capacitor, and the electromagnetic field in the remaining areas is very weak, so the hollow area does not affect the propagation characteristics of the electromagnetic wave.
  • the antenna conductive component 10 may include a conductive base 101 and at least two structural units 102 , and a first capacitor 102 a is formed between adjacent structural units 102 .
  • the first capacitor 102a in FIG. 22 may have a uniform gap width, that is, the width of each position of the gap of the first capacitor 102a may be consistent.
  • an insulating medium may be filled between the structural unit 102 and the conductive base 101, and the insulating medium may, for example, cover the entire outer peripheral surface of the conductive base 101.
  • the insulating medium may include a first insulating medium 103a and a second insulating medium 103b, and the dielectric constant of the first insulating medium 103a may be greater than the dielectric constant of the second insulating medium 103b.
  • first insulating medium 103a and the second insulating medium 103b may extend from one end to the other end of the conductive base 101 along the length direction of the conductive base 101, and they may be alternately arranged in the circumferential direction of the conductive base 101, so as to The arrangement shown in Figure 23 is formed: first insulating medium 103a - second insulating medium 103b - first insulating medium 103a - second insulating medium 103b.
  • the first insulating medium 103a can be distributed on two adjacent sides of the conductive base 101, and the second insulating medium 103b can also be distributed on two adjacent sides of the conductive base 101. Both the first insulating medium 103a and the second insulating medium 103b can be across the edges of the conductive substrate 101 .
  • a first part, a second part, a third part and a fourth part can be defined in the first capacitor 102a.
  • the first part is closest to the wave source and is filled with the third part.
  • An insulating medium 103a, the second part is adjacent to the first part, the second part is filled with the second insulating medium 103b, the third part is opposite to the first part (for example, it can be centrally symmetrical), the third part is filled with the first insulating medium 103a, the fourth part is opposite to the second part (for example, it can be centrally symmetrical), and the fourth part is filled with the second insulating medium 103b.
  • the solution of this embodiment enables the conductive substrate 101 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 101, and can also expand the stealth bandwidth.
  • the propagation direction K of the electromagnetic wave may not be perpendicular to any side of the antenna conductive component 10.
  • This design enables the antenna conductive component 10 to be applied to the base station antenna 2' shown in Figure 12, by This allows the different capacitance value areas of the first capacitor 102a to be distributed on two adjacent sides of the phase shifter, which can match the position of the wave source, thereby achieving a better electromagnetic stealth effect.
  • the detailed principles have been described above and will not be repeated here.
  • this embodiment realizes the design of different capacitance values in different areas by filling insulating media with different dielectric constants, and can be applied to any other embodiment of the present application as needed.
  • the gap size of the first capacitor including the width dimension and length dimension, etc.
  • the gap pattern referring to whether the gap is a whole gap, or whether it is composed of several segments of gaps that are connected by bending in sequence as shown in Figure 15(a) (formed)
  • gap distribution referring to whether the gap is only distributed on one side of the conductive substrate or on two adjacent sides
  • insulating media with different dielectric constants are filled in different areas of the first capacitor.
  • the antenna conductive component 20 may include a conductive base 201 and at least two structural units 202, and a first capacitance is formed between adjacent structural units 202. 202a.
  • the first capacitor 202a does not need to be filled with an insulating medium, or can be filled with an insulating medium of the same dielectric constant.
  • capacitor devices with different capacitance values can be installed in different areas of the first capacitor 202a.
  • the first capacitor device 204 can be installed in the areas closest and farthest from the wave source (due to the limitation of the viewing angle in Figure 24, the area farthest from the wave source is not shown.
  • the second capacitive device 203 can be installed in the area adjacent to the first capacitive device 204.
  • the area where the first capacitor device 204 is installed can be called a first part and a third part, and the area where the second capacitor device 203 is installed can be called a second part and a fourth part.
  • the capacitance value of the first capacitive device 204 is greater than the capacitance value of the second capacitive device 203 .
  • the first capacitive device 204 may be a capacitive device with a fixed capacitance value, or may be a capacitive device (such as a varactor) that can change the capacitance value under signal control.
  • the second capacitive device 203 may be a capacitive device with a fixed capacitance value, or may be a capacitive device (such as a varactor) that can change the capacitance value under signal control.
  • the first capacitive device 204 may also be called a second capacitor, and the second capacitive device 203 may also be called a third capacitor.
  • the first capacitor device 204 and the second capacitor device 203 may be fixed in the gap by welding or other methods.
  • the number of the first capacitor device 204 and the second capacitor device 203 can be determined as needed, and is not limited in this embodiment.
  • the capacitance value is added to the capacitance value of the capacitive device in the area.
  • the capacitance value of the first part is larger; since the second capacitor device 203 with a smaller capacitance value is disposed in the second part, the capacitance value of the second part is The value is smaller.
  • the capacitance value of the third part may be equal to the capacitance value of the first part, and the capacitance value of the fourth part may be equal to the capacitance value of the second part.
  • this embodiment can make the capacitance values of different areas of the first capacitor 202a different by making the first capacitor 202a have a uniform gap width and installing capacitor devices with different capacitance values in different areas of the first capacitor 202a.
  • the solution of this embodiment enables the conductive substrate 201 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 201, and can also expand the stealth bandwidth.
  • the capacitive device is a capacitive device with variable capacitance
  • the capacitance of the capacitive device in the corresponding area can be adaptively adjusted according to the change of the scanning angle of the wave source, and then the capacitance value of the area can be adjusted to ensure that the conductive component of the antenna 20 Electromagnetic cloaking effect on wave sources.
  • the capacitive device (eg, the first part) may be provided only in a part of the first capacitor 202a, and no capacitive device may be provided in other regions.
  • the capacitance values of different regions of the first capacitor 202a may be different.
  • the design of influencing the capacitance value of the area by arranging the capacitive device in the area can be applied to any embodiment of the present application as needed.
  • the gap size, gap pattern, gap distribution, filling condition of the insulating medium, etc. of the first capacitor may not be limited, and the capacitor device may be installed in the first capacitor. The electrical constant and the capacitance value of the capacitive device ultimately make the capacitance value of the first part greater than the capacitance value of the second part.
  • a capacitance (for example, called a plate capacitor) may be formed between the structural unit and the conductive base, and the plate capacitance may affect the frequency band of electromagnetic waves that bypass the conductive component of the antenna.
  • the plate capacitance may affect the frequency band of electromagnetic waves that bypass the conductive component of the antenna.
  • it may be desirable to reduce the spacing between the structural units and the conductive substrate. However, reducing the spacing may lead to an increase in the frequency band of electromagnetic waves that bypass the conductive parts of the antenna, changing the propagation of electromagnetic waves. characteristic.
  • the conductive component of the antenna may also include an inductor element.
  • the inductor element may be disposed in the interval between the structural unit and the conductive base, and connect the structural unit and the conductive base, so that the structural unit and the conductive base are connected.
  • the conductive base is electrically connected.
  • the inductance element can form a parallel resonance circuit with the above-mentioned plate capacitor, and the parallel resonance circuit can reduce the frequency band of the electromagnetic wave that bypasses the conductive component of the antenna.
  • the effects on the frequency band of arranging the inductive element and reducing the distance between the structural unit and the conductive substrate can cancel each other out, so that the frequency band of the electromagnetic wave that bypasses the conductive component of the antenna remains unchanged, thereby maintaining the propagation characteristics of the electromagnetic wave.
  • the inductance element may be a conductive structural member, such as a metal pillar. Such an inductance element may be equivalent to an inductor. Such an inductance element facilitates the mechanical processing of the conductive components of the antenna. Alternatively, the inductive component can be directly an inductor.
  • the position of the inductor element can be designed as needed, for example, it is at a certain distance from the first capacitor to avoid being too close.
  • the number of inductance elements can be designed as needed.
  • each structural unit can be connected to the conductive base through at least one inductance element, or only some of the structural units can be connected to the conductive base through inductance elements.
  • FIG. 25 illustrates an antenna conductive component 30 designed using the inductive element of this embodiment.
  • the antenna conductive component 30 may include a conductive base 301 and at least two structural units 302.
  • a first capacitor 302a is formed between adjacent structural units 302. Different regions of the first capacitor 302a have different capacitance values.
  • Each side of the structural unit 302 is connected to the conductive base 301 through an inductor element 303, and several inductor elements 303 are provided between each structural unit 302 and the conductive base 301.
  • the antenna conductive component 30 shown in FIG. 25 is only an example and does not limit the application environment of the inductive element 303.
  • the capacitance values of different regions of the first capacitor in the conductive component of the antenna are different.
  • the capacitance values of different regions of the first capacitor may be the same. It can be understood that electromagnetic stealth design can also be achieved by making the capacitance values of different areas of the first capacitor the same. Several solutions in which the capacitance values of different areas of the first capacitor are the same are listed below.
  • the antenna conductive component 40 may include a conductive base 401 and at least two structural units 402 surrounding the conductive base 401.
  • the adjacent structural units 402 The first capacitor 402a is formed between them.
  • the conductive base 401 in FIG. 26(a) may be, for example, substantially cylindrical, and the conductive base 401 in FIG. 26(b) may be, for example, substantially square columnar.
  • the gaps between any adjacent structural units 402 can have the same width, that is, the gap widths everywhere in the gap can be consistent.
  • the capacitance values of different areas of the first capacitor 402a may be the same.
  • the first capacitor 402a in this embodiment can also change the propagation direction of the electromagnetic wave emitted by the wave source, and confine the electromagnetic wave to propagate within it, so that the electromagnetic wave can propagate around the antenna conductive component 40. Therefore, even if the antenna conductive component 40 blocks the wave source, the presence of the first capacitor 402 a allows the electromagnetic wave to bypass the antenna conductive component 40 and propagate to the rear of the antenna conductive component 40 , thereby reducing or eliminating electromagnetic shadows.
  • the antenna conductive component 50 includes a conductive base 501 and at least two structural units 502, and a first structural unit 502 is formed between adjacent structural units 502. capacitance.
  • the structural unit 502 is not an integrated structure, but has a coupling gap inside. The parts of the structural unit 502 on both sides of the coupling gap are completely disconnected and unconnected, and the parts on both sides of the coupling gap can be coupled through the coupling gap.
  • the structural unit 502 may include a first part 503, a second part 504, a third part 505 and a fourth part 506, and these four parts may be located on different sides of the conductive base 501 respectively.
  • each coupling gap extends along the edge of the conductive base 501 .
  • the above four coupling gaps can separate the structural unit 502 into four independent parts. When the electromagnetic wave propagates to the structural unit 502, the electromagnetic wave can "cross" these coupling gaps, so the parts of the structural unit 502 located on both sides of the coupling gap are coupled through the coupling gap.
  • the position and extension direction of the coupling gap can be flexibly designed, and the number of coupling gaps can be at least one.
  • all structural units 502 may have coupling gaps, or only some structural units 502 may have coupling gaps.
  • the gaps between any adjacent structural units 502 can have the same width, that is, the gap widths can be consistent everywhere.
  • the capacitance values of different regions of the constructed first capacitor may be the same.
  • the embodiment shown in FIG. 27 can also improve the electromagnetic shadow problem, and can realize the separate assembly of the structural unit 502, thereby simplifying the assembly process and improving the assembly yield.
  • the coupling gap in the antenna conductive component 50 can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna conductive component 50 has a certain effect in expanding the stealth bandwidth.
  • the antenna conductive component 60 includes a conductive base 601 and at least two structural units 602, and a first structural unit 602 is formed between adjacent structural units 602. capacitance.
  • the structural unit 602 is not an integrated structure, but has a coupling gap 602f and a coupling gap 602g inside.
  • the coupling gap 602f and the coupling gap 602g may be located on opposite sides of the structural unit 602 respectively.
  • both the coupling gap 602f and the coupling gap 602g can be approximately in the middle of the side of the structural unit 602, not is at the edge of the structural unit 602.
  • the coupling gap 602f and the coupling gap 602g can separate the structural unit 602 into a first part 603 and a second part 604. Both the first part 603 and the second part 604 can have an approximately C-shaped structure, and the first part 603 and the second part 604 are completely disconnected. If not connected, the first part 603 and the second part 604 may be coupled through the coupling gap 602f and the coupling gap 602g. Illustratively, the coupling gaps on the same side of all structural units 602 may be collinear.
  • the gaps between any adjacent structural units 602 can have the same width, that is, the gap widths can be consistent everywhere.
  • the capacitance values of different regions of the constructed first capacitor may be the same.
  • the embodiment shown in FIG. 28 can also improve the electromagnetic shadow problem, and can realize the separate assembly of the structural unit 602, thereby simplifying the assembly process and improving the assembly yield.
  • the coupling gap in the antenna conductive component 60 can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna conductive component 60 has a certain effect in expanding the stealth bandwidth.
  • the first capacitor may include a first part 52b (which is formed by at least two sections of sub-slits 52d sequentially bent and connected) and a second part 52c.
  • first part 52b and the second part 52c (S1/d1)>(S2/d2).
  • the capacitance formula C ⁇ S/d ( ⁇ is the dielectric constant of the medium between the plates, S is the area of the plates, and d is the distance between the plates), which can make the capacitance value of the first part 52b equal to the capacitance value of the second part 52c.
  • the capacitance value of the third part may be equal to the capacitance value of the first part; the fourth part and the second part 52c may be centrally symmetrical, and the fourth part may be centrally symmetrical with the second part 52c.
  • the capacitance value of can be equal to the capacitance value of the second part. Therefore, the capacitance values of different areas of the first capacitor may be the same.
  • the first part 62b shown in FIG. 16 may be filled with an insulating medium with a smaller dielectric constant
  • the second part 62c shown in FIG. 16 may be filled with an insulating medium with a larger dielectric constant.
  • the capacitance value of the first part 62b is equal to the capacitance value of the first part 62b.
  • the third part and the first part 62b of the first capacitor may be centrally symmetrical
  • the capacitance value of the third part may be equal to the capacitance value of the first part
  • the fourth part and the second part 62c may be centrally symmetrical
  • the fourth part may be centrally symmetrical with the second part 62c.
  • the capacitance value of can be equal to the capacitance value of the second part. Therefore, the capacitance values of different areas of the first capacitor may be the same.
  • the gaps between the structural units 92 can be set to have the same width, that is, the gap widths everywhere in the gaps can be consistent, so that the first capacitor has the same width. Capacitance values in different areas can be the same.
  • the same insulating medium can be filled between the structural unit 102 and the conductive base 101, so that the capacitance values of different areas of the first capacitor can be the same.
  • the capacitance values of different areas of the first capacitor can be set to be consistent through any of the above methods.

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Abstract

本申请提供了一种基站天线和基站。基站天线包括第一天线阵列、频率选择表面、第二天线阵列和天线导电部件；频率选择表面位于第一天线阵列的辐射单元的第一辐射体与第二天线阵列之间，频率选择表面用于反射第一天线阵列的辐射信号，并透过第二天线阵列的辐射信号；天线导电部件与第一天线阵列位于第二天线阵列的阵面的同侧；天线导电部件包括导电基体、第一结构单元和第二结构单元；第一结构单元与第二结构单元均环绕导电基体一周，第一结构单元与第二结构单元间隔且相邻排布，并形成电容。基站包括抱杆和该基站天线，基站天线固定于抱杆。本申请的能够改善由于金属部件遮挡导致的电磁阴影问题。

Description

基站天线和基站
本申请要求于2022年09月08日提交中国专利局、申请号为202211097482.8、申请名称为“基站天线和基站”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及天线技术领域，特别涉及一种基站天线和基站。
背景技术
在天线系统中，辐射单元可能会被周围的金属部件遮挡，电磁波传播至这些金属部件时会在该金属部件的表面产生散射，无法完全传播至该金属部件的后方，使得该金属部件的后方产生电磁阴影。对于天线的信号接收过程，电磁阴影会导致位于该金属部件后方的辐射单元的接收信号质量劣化；对于天线的信号辐射过程，电磁阴影会影响位于金属部件后方的终端的通信质量。
发明内容
本申请提供一种基站天线和基站，能够改善由于金属部件遮挡导致的电磁阴影问题。
第一方面，本申请提供了一种基站天线，包括第一天线阵列、频率选择表面、第二天线阵列和天线导电部件；频率选择表面位于第一天线阵列的辐射单元的第一辐射体与第二天线阵列之间，频率选择表面用于反射第一天线阵列的辐射信号，并透过第二天线阵列的辐射信号；天线导电部件与第一天线阵列位于第二天线阵列的阵面的同侧；天线导电部件包括导电基体、第一结构单元和第二结构单元；第一结构单元与第二结构单元均环绕导电基体一周，第一结构单元与第二结构单元间隔且相邻排布，并形成电容。
本申请的方案中，通过使得频率选择表面位于第一天线阵列的辐射单元的第一辐射体与第二天线阵列之间，能够以频率选择表面作为基准面，实现第一天线阵列与第二天线阵列的层叠布置。层叠布置能够在有限的天线口面口径下部署更多频段和通道的天线阵列，从而满足通信要求。由于频率选择表面能够允许第二天线阵列的电磁波透过，因此频率选择表面对于第二天线阵列的信号并不会造成遮挡。天线导电部件的位置，使其对第二天线阵列在物理上造成遮挡。但是，由于天线导电部件中的结构单元之间形成缝隙，该缝隙以及两侧结构单元可以形成电容，该电容将电磁波约束在该缝隙内进行传播，使得电磁波能够绕着天线导电部件传播至天线导电部件的后方，从而减少或者消除了电磁阴影。
在第一方面的一种实现方式中，天线导电部件位于第一天线阵列与第二天线阵列之间。本方案中，将天线导电部件设置在第一天线阵列与第二天线阵列之间，依然满足天线导电部件与第一天线阵列位于第二天线阵列的阵面的同侧的设计。本方案通过限定天线导电部件的位置，能够针对一种典型的层叠布置天线的应用场景，在有限的天线口面口径下部署更多频段和通道的天线阵列，且改善电磁阴影。
在第一方面的一种实现方式中，导电基体包括馈电网络，馈电网络与第一天线阵列的辐射单元连接。本方案中，通过在馈电网络的外侧形成结构单元及电容，能够使得馈电网络具备电磁隐身性能，改善由于馈电网络对第二天线阵列的物理遮挡导致的电磁阴影问题。
在第一方面的一种实现方式中，频率选择表面与第一天线阵列及第二天线阵列均无电连接，和/或，频率选择表面与馈电网络无电连接。本方案中，通过使得频率选择表面与天线阵列无电连接，使得天线阵列的馈电信号不会通过频率选择表面传输，从而能够缩短馈电路径，降低损耗，还能使得频率选择表面的结构较为简单，降低成本。由于频率选择表面与作为导电基体的馈电网络无电连接，因此频率选择表面与该馈电网络之间基本不存在耦合，能够保证电磁隐身性能以及频率选择表面的频率选择性能。
在第一方面的一种实现方式中，第一天线阵列与天线导电部件位于频率选择表面的同侧。本方案通过限定第一天线阵列、天线导电部件以及频率选择表面之间的位置关系，能够针对一种典型的层叠布置天线的应用场景，在有限的天线口面口径下部署更多频段和通道的天线阵列，且改善电磁阴影。
在第一方面的一种实现方式中，第一天线阵列的辐射单元包括馈电结构，馈电结构连接第一辐射体与馈电网络，馈电结构穿过频率选择表面；第一辐射体与天线导电部件分别位于频率选择表面的相对两侧。
本方案通过限定第一天线阵列、天线导电部件以及频率选择表面之间的位置关系，能够针对一种典型的层叠布置天线的应用场景，在有限的天线口面口径下部署更多频段和通道的天线阵列，且改善电磁阴影。 本方案中，频率选择表面的位置可以根据天线设计要求确定。而将天线导电部件设在频率选择表面背向第一辐射体的一侧，使得天线导电部件与第一辐射体的距离较大，能减少天线导电部件(包括馈电网络)对第一天线阵列的近场耦合的影响，保证第一天线阵列的性能。
在第一方面的一种实现方式中，频率选择表面包括层叠且间隔布置的第一频率选择表面与第二频率选择表面，第一频率选择表面位于第一辐射体与第二频率选择表面之间；第一天线阵列的辐射单元包括馈电结构，馈电结构连接第一辐射体与馈电网络，馈电结构穿过第一频率选择表面，第一辐射体与天线导电部件分别位于第一频率选择表面的相对两侧。
本方案通过限定频率选择表面的数量，以及限定第一天线阵列、天线导电部件以及频率选择表面之间的位置关系，能够针对一种典型的层叠布置天线的应用场景，在有限的天线口面口径下部署更多频段和通道的天线阵列，且改善电磁阴影。本方案中，第一频率选择表面与第二频率选择表面的位置可以根据天线设计要求确定。可以将天线导电部件(导电基体为馈电网络)的厚度做的较小，使其能够位于第一频率选择表面与第二频率选择表面之间，这样能够使得第一天线的总厚度较小。另外，多层频率选择表面可以增强滤波选择性，有利于拓展天线的带宽。
在第一方面的一种实现方式中，频率选择表面包括层叠且间隔布置的第一频率选择表面与第二频率选择表面，第一频率选择表面位于第一辐射体与第二频率选择表面之间；天线导电部件穿过第一频率选择表面，第一天线阵列的辐射单元与第二天线阵列分别位于第一频率选择表面的相对两侧。
本方案通过限定频率选择表面的数量，以及限定第一天线阵列、天线导电部件以及频率选择表面之间的位置关系，能够针对一种典型的层叠布置天线的应用场景，在有限的天线口面口径下部署更多频段和通道的天线阵列，且改善电磁阴影。本方案中，第一频率选择表面与第二频率选择表面的位置可以根据天线设计要求确定。通过使天线导电部件(导电基体为馈电网络)穿过第一频率选择表面，能够使得馈电网络与第一辐射体的距离不至于过大，进而减小损耗；又能够使馈电网络与第一辐射体的距离不至于过小，以改善馈电网络对第一天线阵列的近场耦合的影响。另外，多层频率选择表面可以增强滤波选择性，有利于拓展第二天线的带宽。
在第一方面的一种实现方式中，第一辐射体包括第二辐射体与第三辐射体，第二辐射体与第三辐射体的频段不同；馈电网络包括第一馈电网络与第二馈电网络，第一馈电网络与第二辐射体电连接，第二馈电网络与第三辐射体电连接。本方案中，通过使第一天线阵列包括多个频段，能够增加基站天线的频段和通道数，增加了天面口径利用率。
在第一方面的一种实现方式中，第二天线阵列的辐射单元包括第四辐射体与第五辐射体，第四辐射体与第五辐射体的频段不同。本方案中，通过使第二天线阵列具有多种频段，能够扩展频段数和通道数。
在第一方面的一种实现方式中，频率选择表面与天线导电部件的最小间距大于或等于第二天线阵列的最高工作频率对应的波长的0.1倍。本方案中，通过对频率选择表面与天线导电部件的最小间距进行限定，能够避免频率选择表面与线导电部件之间产生较强耦合，从而保证电磁隐身性能以及频率选择表面的频率选择性能。
在第一方面的一种实现方式中，频率选择表面包括多个频率选择单元，多个频率选择单元包括第一频率选择单元，第一频率选择单元的结构与其他频率选择单元的结构不同，第一频率选择单元与天线导电部件在频率选择表面上的正投影存在重叠。
本方案中，频率选择表面中的第一频率选择单元的结构相较独特，这样的频率选择表面可以称为具有准周期阵列结构。通过将频率选择表面制造成准周期阵列结构，使靠近天线导电部件的第一频率选择单元的结构与其他频率选择单元的结构不同，能够减小频率选择表面与天线导电部件之间的耦合，从而保证电磁隐身性能以及频率选择表面的频率选择性能。本方案能够适用于如下场景：若由于产品设计限制，导致频率选择表面与天线导电部件的间距无法满足该最小间距的要求，则可以通过本方案减小频率选择表面与天线导电部件之间的耦合。
在第一方面的一种实现方式中，频率选择表面包括相连的第一部分与第二部分，第一部分不含导体材料，第一部分与天线导电部件在频率选择表面上的正投影存在重叠，第二部分包含导体材料。
本方案中，通过将频率选择表面靠近天线导电部件的第一部分中的导体层去除，能够极大减少频率选择表面与天线导电部件之间的耦合，从而保证电磁隐身性能以及频率选择表面的频率选择性能。本方案能够适用于如下场景：若由于产品设计限制，导致频率选择表面与天线导电部件的间距无法满足该最小间距的要求，则可以通过本方案减小频率选择表面与天线导电部件之间的耦合。
在第一方面的一种实现方式中，基站天线包括第一天线罩与第二天线罩，第一天线阵列、频率选择表 面及天线导电部件均位于第一天线罩内，第二天线阵列位于第二天线罩内。本方案中，通过将第一天线阵列与第二天线阵列分别设在不同的天线罩内，使得两个天线可以分别单独部署，实现了不同频段天线的解耦设计与灵活部署。
在第一方面的一种实现方式中，电容的不同部分的电容值不同。本方案中，由于电容的不同区域的电容值不同，使得不同频段的电磁波信号均能够以各自的电长度在缝隙内发生谐振，从而使得不同频段的电磁波均能通过缝隙。因此，通过使电容的不同区域的电容值不同，使缝隙能够允许多种频段的电磁波通过，从而拓展了隐身带宽。
在第一方面的一种实现方式中，天线导电部件包括至少两个结构单元，第一结构单元与第二结构单元均为至少两个结构单元中的结构单元；至少一个结构单元设有耦合缝隙，结构单元分别位于耦合缝隙两侧的部分被耦合缝隙断开，并通过耦合缝隙耦合。
本方案中，在结构单元中形成耦合缝隙，便于将结构单元的不同部分依次装配到导电基体上，最后拼成完整的结构单元，这样能够在一些场景下实现结构单元的可靠组装。尤其是在导电基体的尺寸较大、结构单元的数量较多时，分体组装的方式能够简化组装工艺，提高组装良率。另外，耦合缝隙能够允许某些频段的电磁波通过，使得天线导电部件具有一定的拓展隐身带宽作用。
在第一方面的一种实现方式中，天线导电部件包括至少两个结构单元，第一结构单元与第二结构单元均为至少两个结构单元中的结构单元；至少两个结构单元的结构相同，任意相邻的两个结构单元之间存在缝隙且缝隙的形状相同，任意两个相邻的结构单元之间均形成电容。
本方案中，所有结构单元的结构均一致。任意两个结构单元之间存在缝隙，且各个缝隙的形状相同。由此，任意两个相邻的结构单元之间均形成电容。本方案使得天线导电部件上形成多个电容，使得电磁波能在天线导电部件的各个区域进行绕射，使得整个天线导电部件能相对电磁波隐身，避免了电磁阴影。本方案中，所有结构单元可以构成周期性结构层，该周期性结构层容易制造，量产性好。
在第一方面的一种实现方式中，天线导电部件包括至少两个结构单元，第一结构单元与第二结构单元均为至少两个结构单元中的结构单元；至少两个结构单元的结构不全相同，和/或，至少两个结构单元之间存在缝隙且缝隙的形状不全相同；任意两个相邻的结构单元之间均形成电容。
本方案中，不全相同指任意两个都不同；或者，至少有两个相同，但不是所有都相同。本方案中，相较上述的周期性结构层，所有结构单元可以构成准周期性结构层。准周期性结构层能够与导电基体的外形结构适配。
第二方面，本申请提供了一种基站，包括抱杆和上述任一项的基站天线，基站天线固定于抱杆。本方案，由于基站天线包括层叠布置的天线阵列，能够在有限的天线口面口径下部署更多频段和通道的天线阵列，从而满足通信要求。由于天线导电部件的设计，能够改善层叠天线的电磁阴影导电问题。
附图说明
图1表示基站与终端进行无线通信的应用场景；
图2表示本申请实施例的一种基站的组装结构；
图3表示图2中的基站的一部分内部框架结构；
图4表示本申请实施例的一种基站天线的内部框架结构；
图5(a)表示图4中的基站天线内的频率选择表面的一种示意性结构；
图5(b)表示图4中的基站天线内的频率选择表面的另一种示意性结构；
图6是一种实施例中的基站天线的内部框架结构示意图；
图7是一种实施例中的基站天线的内部框架结构示意图；
图8是一种实施例中的基站天线的内部框架结构示意图；
图9是一种实施例中的基站天线的内部框架结构示意图；
图10是一种实施例中的基站天线的第一天线的内部结构示意图；
图11(a)表示一种实施例中的频率选择表面的准周期阵列结构设计；
图11(b)表示另一种实施例中的频率选择表面的准周期阵列结构设计；
图12是一种实施例中的天线导电部件的立体结构示意图；
图13是图12所示的天线导电部件的侧剖结构示意图；
图14是一种实施例中的天线导电部件的立体结构示意图；
图15(a)是一种实施例中的天线导电部件的立体结构示意图；
图15(b)是图15(a)中A处的局部放大结构示意图；
图16是一种实施例中的天线导电部件的立体结构示意图；
图17表示图16所示的天线导电部件在一种基站天线中的应用原理；
图18是图17所示的局部放大结构示意图；
图19是一种实施例中的天线导电部件的立体结构示意图；
图20是一种实施例中的天线导电部件的立体结构示意图；
图21是一种实施例中的天线导电部件的立体结构示意图；
图22是一种实施例中的天线导电部件的立体结构示意图；
图23是图22所示的天线导电部件的侧视结构示意图；
图24是一种实施例中的天线导电部件的立体结构示意图；
图25是一种实施例中的天线导电部件的立体结构示意图；
图26(a)是一种实施例中的天线导电部件的立体结构示意图；
图26(b)是一种实施例中的天线导电部件的立体结构示意图；
图27是一种实施例中的天线导电部件的立体结构示意图；
图28是一种实施例中的天线导电部件的立体结构示意图。
附图标记：
1-基站；11-抱杆；12-抱杆支架；13-天线罩；14-天线阵列；15-射频处理单元；16-线缆；17-基带处理
单元；18-馈电网络；181-移相器；182-功分器；183-滤波器；
2-基站天线；21-第一天线罩；2A-第一天线阵列；22-第一辐射单元；221-第一辐射体；222-馈电结构；
24-频率选择表面；24a-频率选择单元；24b-频率选择单元；24c-频率选择单元；2B-第二天线阵列；25-第二辐射单元；251-辐射体；252-馈电结构；26-第二天线罩；211-辐射体；212-第一馈电网络；213-辐射体；214-第二馈电网络；
2’-基站天线；223-辐射单元；224-辐射单元；
3-天线导电部件；3a-间隔；31-导电基体；32-结构单元；32a-第一电容；32b-第一部分；32c-第二部分；
32d-第三部分；32e-第四部分；33-结构层；E-电场方向；H-磁场方向；K-电磁波的传播方向；
4-天线导电部件；41-导电基体；42-结构单元；42b-第一部分；42c-第二部分；
5-天线导电部件；51-导电基体；52-结构单元；52b-第一部分；52d-子缝隙；52c-第二部分；
6-天线导电部件；61-导电基体；63-结构层；62-结构单元；62b-第一部分；62c-第二部分；62d-第三部
分；62e-第四部分；
7-天线导电部件；71-导电基体；72-结构单元；721-第一部分；722-第二部分；723-第三部分；724-第四
部分；72b-第一部分；72c-第二部分；72f-耦合缝隙；72g-耦合缝隙；72h-耦合缝隙；72i-耦合缝隙；
8-天线导电部件；81-导电基体；82-结构单元；821-第一部分；822-第二部分；82b-第一部分；82c-第二
部分；82f-耦合缝隙；82g-耦合缝隙；
9-天线导电部件；91-导电基体；92-结构单元；92b-第一部分；92c-第二部分；92f-镂空区；92g-镂空区；
10-天线导电部件；101-导电基体；102-结构单元；102a-第一电容；103a-第一绝缘介质；103b-第二绝缘介质；
20-天线导电部件；201-导电基体；202-结构单元；202a-第一电容；203-第二电容器件；204-第一电容器
件；
30-天线导电部件；301-导电基体；302-结构单元；302a-第一电容；303-电感元件；
40-天线导电部件；401-导电基体；402-结构单元；402a-第一电容；
50-天线导电部件；501-导电基体；502-结构单元；502f-耦合缝隙；502g-耦合缝隙；502h-耦合缝隙；502i-
耦合缝隙；503-第一部分；504-第二部分；505-第三部分；506-第四部分；
60-天线导电部件；601-导电基体；602-结构单元；602f-耦合缝隙；602g-耦合缝隙；603-第一部分；604-
第二部分；
70-基站天线；76-第一天线罩；751-辐射体；771-辐射体；
80-基站天线；84-频率选择表面；
90-基站天线；941-第一频率选择表面；942-第二频率选择表面；
100-基站天线；141-第一频率选择表面；142-第二频率选择表面。
具体实施方式
下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行描述，显然，所描述的实施例仅仅是本申请一部分实施例，而不是全部的实施例。
本申请实施例中，术语“第一”、“第二”、“第三”、“第四”、“第五”等仅用于区分部件，而不能理解为指示或暗示部件的相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”等的特征可以明示或者隐含地包括一个或者更多个该特征。在本申请实施例的描述中，除非另有说明，“多个(层)”的含义是两个(层)或两个(层)以上。
本申请实施例中，“上”、“下”、“前”、“前方”、“后”、“后方”等术语是相对于附图中的结构示意置放的方位来定义的，应当理解，这些方向性术语是相对的概念，它们是一种相对的描述和澄清，其可以根据结构所放置的方位的变化而相应地发生变化。
本申请实施例中，除非另有说明，“和/或”仅仅是一种描述关联对象的关联关系，表示可以存在三种关系。例如A和/或B可以表示：单独存在A，同时存在A和B，单独存在B这三种情况。
本申请实施例涉及基站和基站天线。下面先介绍基站，再说明基站天线。
图1示意出了基站与终端进行无线通信的应用场景。如图1所示，基站用于进行无线信号的小区覆盖以实现终端设备与无线网络之间的通信。具体来说，基站可以是全球移动通信系统(global system for mobile comunication，GSM)或码分多址(code division multiple access,CDMA)系统中的基站收发台(base transceiver station，BTS)，也可以是宽带码分多址(wideband code division multiple access，WCDMA)系统中的节点B(NodeB，NB)，还可以是长期演进(long term evolution,LTE)系统中的演进型节点B(evolutional NodeB，eNB)，还可以是云无线接入网络(cloud radio access network，CRAN)场景下的无线控制器。或者基站也可以为中继站、接入点、车载设备、可穿戴设备以及新无线(new radio,NR)系统中的g节点(gNodeB或者gNB)或者未来演进的网络中的基站等，本申请实施例并不限定。
基站配备有基站天线来实现信号在空间中的传输。图2示意了图1中的基站所配备的一种基站天线的结构组成。如图2所示，基站1可以包括抱杆11、抱杆支架12、天线罩13、天线阵列14、射频处理单元15、线缆16和基带处理单元17。其中，抱杆支架12、天线罩13、天线阵列14可以合称基站天线，该基站天线还可以包括下文将要描述的馈电网络与反射板等。
其中，抱杆11可以固定至地面。抱杆支架12连接抱杆11与天线罩13，天线罩13通过抱杆支架12固定至抱杆11。天线阵列14可以安装在天线罩13内。天线罩13内还可以安装馈电网络。天线罩13具有良好的电磁波穿透特性和环境耐候性，能够对安装于其内的部件进行防护。
天线阵列14用于辐射和接收天线信号。天线阵列14可以包括若干个按照一定规律阵列排布的辐射单元，每个辐射单元均能辐射与接收电磁波。该辐射单元可以包括天线振子。在天线阵列14中，不同辐射单元的工作频段可以相同或者不同。该辐射单元可以包括相连接的辐射体(例如可以是辐射臂)与馈电结构(例如可以包括巴伦)。其中，辐射体用于进行信号的辐射与接收；馈电结构连接辐射体与馈电网络，以将馈电网络传输的电信号传送至辐射体，并将辐射体接收的信号传送至馈电网络。
基站天线还可以包括反射板，反射板也可以称为底板、天线面板或者反射面等，反射板例如可以采用金属材料制造。辐射单元可以安装在反射板一侧的表面上。辐射单元接收天线信号时，反射板可以把天线信号反射聚集在接收点上，从而实现定向接收；辐射单元发射天线信号时，反射板可以实现天线信号的定向发射。反射板可以增强辐射单元的天线信号的接收或发射能力，还能够阻挡、屏蔽来自反射板背面(该背面是指反射板上的背向辐射单元的一侧)的其它信号对天线信号的干扰作用，提升天线的增益。
射频处理单元15(又可称为射频拉远单元(remote radio unit，RRU))可通过跳线连接馈电网络，并通过馈电网络与天线阵列14电连接，馈电网络(下文将继续说明)可以作为射频处理单元15与天线阵列14之间的信号传输通路。射频处理单元15可以通过线缆16(例如光缆)与基带处理单元17(也可以称为基带单元(baseband unit，BBU))电连接。如图2所示，射频处理单元15和基带处理单元17可以均位于天线罩13外，射频处理单元15可以位于基站天线的近端。
射频处理单元15可对天线阵列14接收到的天线信号进行选频、放大以及下变频处理，并将其转换成中频信号或基带信号发送给基带处理单元17。射频处理单元15还可以将基带处理单元17或中频信号经过上变频以及放大处理通过天线阵列14转换成电磁波发送出去。
图3可以表示图2中的基站1的一部分的内部框架结构。如图3所示，基站1的天线阵列14与馈电网络18相连。馈电网络18可以通过传动机构实现不同辐射波束指向，或者与校准网络连接以获取基站1 所需的校准信号。馈电网络18可将信号按照一定的幅度、相位馈送到天线阵列14，或者将接收到的信号按照一定的幅度、相位发送到基带处理单元17。
示意性的，馈电网络18可以包括移相器181，移相器181用于改变天线信号辐射的最大方向。馈电网络18还可以包括用于扩展性能的模块，例如功分器182。功分器182用于将多路信号合路为一路信号，通过天线阵列14发射；或者，功分器182将一路信号分为多路信号，例如将天线阵列14接收到的信号根据不同的频率分成多路传输到基带处理单元17进行处理。馈电网络18还可以包括滤波器183，用于滤除干扰信号。馈电网络18还可包括合路器。馈电网络18还可以包含任何形式的传输线，如同轴线、带状线、微带线等。
图2-图3所示的基站1的结构仅仅是一种举例，实际上本申请实施例中的基站的结构可以根据产品需求灵活地设计，并不限于上文所述。例如，基站也可以没有抱杆11，天线罩13可以通过抱杆支架12固定至铁塔。
在基站中，天线阵列可能会被周围的导体部件(该导体部件至少包含导电部分，例如该导体部件的全部区域均是导体，或者该导体部件包括导体部分与绝缘部分。下文将该导体部件称之为导电基体)遮挡，电磁波传播至这些导体部件时会在该导体部件的表面产生散射，无法完全传播至该导体部件的后方，使得该导体部件的后方产生电磁阴影。对于信号接收过程，电磁阴影会导致位于该导体部件后方的天线阵列的接收信号质量劣化；对于信号辐射过程，电磁阴影会影响位于导体部件后方的终端的通信质量。另外，随着无线通信行业的发展，要求基站具有更多数量的通信频段和通道以满足通信需求。但是运营商站点天面空间资源有限，天面口径也受到严格限制，导致频段和通道的数量难以提升。
为了解决上述问题，本申请实施例的基站天线对天线阵列周围的导体部件做了“电磁隐身”设计，使得电磁波能够绕过该导体部件继续传播，改善了电磁阴影问题。通过天线阵列的“层叠设计”，能够在有限的天面口径下设置更多频段和通道的天线阵列。下面将先详细说明基站天线的整体框架结构，其中包括“层叠设计”；再说明“电磁隐身”设计。
图4示意出了一种实施例中的基站天线2的内部框架结构，基站天线2具有电磁隐身设计与层叠设计。
如图4所示，基站天线2可以包括第一天线与第二天线。
其中，第一天线可以包括第一天线罩21、第一天线阵列2A、天线导电部件3和频率选择表面(frequency selective surface，FSS)24。第一天线阵列2A、天线导电部件3和频率选择表面24均可以位于第一天线罩21内。
其中，第二天线可以包括第二天线罩26和第二天线阵列2B，第二天线阵列2B位于第二天线罩26内。
本实施例中，第一天线罩21与第二天线罩26分别是两个独立的天线罩，二者可以固定于同一个抱杆或者铁塔。通过将第一天线阵列2A与第二天线阵列2B分别设在不同的天线罩内，使得两个天线可以分别单独部署，实现了不同频段天线的解耦设计与灵活部署。可以理解的是，本实施例的方案仅仅是一种示例。在其他实施例中，第一天线阵列与第二天线阵列也可以在同一个天线罩内。
如图4所示，第一天线阵列2A可以包括多个第一辐射单元22。各个第一辐射单元22的频段可以一致，或者存在至少一个第一辐射单元22的频段与其余第一辐射单元22的频段不同。第一辐射单元22可以包括辐射体221(可以称为第一辐射体)与馈电结构222，二者相连。可以理解的是，图4中以水平线条代表辐射体221，以竖直线条代表馈电结构222，这仅仅是一种示意，并非是在限定辐射体221与馈电结构222的具体结构与具体位置。
本申请实施例中，天线导电部件3与第一天线阵列2A，可以位于第二天线阵列2B的阵面的同一侧。例如图4所示，天线导电部件3可以位于第一天线阵列2A与第二天线阵列2B之间，可以认为三者层叠布置。天线导电部件3可以较长，例如基本将第二天线阵列2B遮挡。
在其他实施例中，天线导电部件3与第一天线阵列2A位于第二天线阵列2B的阵面的同一侧，还可以包括如下设计：天线导电部件3、第一天线阵列2A、第二天线阵列2B三者依次层叠，第一天线阵列2A位于天线导电部件3与第二天线阵列2B之间。或者，天线导电部件3与第一天线阵列2A可以大致并排(并非呈明显的层叠关系)，二者位于第二天线阵列2B的同侧。
本实施例中，天线导电部件3可以是具有电磁隐身设计的馈电网络。下面将进行说明。
如图4所示，天线导电部件3可以包括导电基体31与结构层33。其中，导电基体31可以是馈电网络，该馈电网络可以包括移相器、功分器、滤波器等中的至少一个。该馈电网络可与第一天线阵列2A的第一辐射单元22的馈电结构222连接，以实现对第一天线阵列2A的馈电。结构层33覆盖导电基体31的至少一部分外表面，例如结构层33可以仅覆盖导电基体31的主要功能部分(如包含移相器、功分器、滤波器 等的部分)的外表面，或者结构层33也可以覆盖导电基体31的所有外表面。结构层33能够使得电磁波绕过导电基体31继续传播，减少或者消除电磁阴影。结构层33的具体结构及工作原理将在下文详细说明。结构层33可以较为轻便，可以适用于天线中的局部位置。
在其他实施例中，天线导电部件也可以是具有电磁隐身设计的其他部件，也即天线导电部件中的导电基体可以是除馈电网络以外的其他可导电部件。下面将借助图2，列举其他几种天线导电部件。
参考图2所示，抱杆11可能会对天线罩13内的天线阵列14的信号产生遮挡，可以在抱杆11的外表面覆盖结构层，该结构层的具体分布可以根据需要确定。例如，可以根据天线阵列14的扫描范围，将该结构层覆盖在抱杆11的外表面的相应局部区域；或者，该结构层可以覆盖抱杆11的全部外表面。本方案中，抱杆11作为导电基体，抱杆11与该结构层可以构成一种天线导电部件。
同理，可以将抱杆支架12作为导电基体，抱杆支架12与其上的结构层可以构成另一种天线导电部件。
或者，基站1中的其他金属件(如传动机构、支撑结构等)也可以作为导电基体，这些金属件与其上的结构层可以构成另一种天线导电部件。
在其他实施例中，根据天线导电部件的具体产品类型不同，其具体位置可以不同，但是天线导电部件的位置总是满足如下设计要求：天线导电部件与第一天线阵列位于第二天线阵列的阵面的同一侧。
如图4所示，第二天线阵列2B可以包括多个第二辐射单元25。各个第二辐射单元25的频段可以一致，或者存在至少一个第二辐射单元25的频段与其余第二辐射单元25的频段不同。第二辐射单元25可以包括辐射体251与馈电结构252，二者相连。可以理解的是，图4中以水平线条代表辐射体251，以竖直线条代表馈电结构252，这仅仅是一种示意，并非是在限定辐射体251与馈电结构252的具体结构与具体位置。可以理解的是，第二天线罩26内也可以有反射板与馈电网络，各个第二辐射单元25可以安装在该反射板上，馈电结构252与该馈电网络连接。
如图4所示，本实施例中，第一天线阵列2A与天线导电部件3可以位于频率选择表面24的一侧，第二辐射单元25可以位于频率选择表面24的另一侧。其中，频率选择表面24的“一侧”与“另一侧”可以分别是沿频率选择表面24的厚度方向的相对两侧。也可以认为频率选择表面24位于辐射体221与第二天线阵列2B之间。
由此，以频率选择表面24作为层叠基准面，可以称第一天线阵列与第二天线阵列是层叠布置的，或者说第一天线与第二天线是层叠布置的。层叠布置能够在有限的天线口面口径下部署更多频段和通道的天线阵列，满足通信要求。
本实施例中，第一天线阵列2A的频段可以低于第二天线阵列2B的频段，这样能保证第一天线与第二天线的收发性能。在其他实施例中，第一天线阵列2A的频段与第二天线阵列2B的频段可以不做上述限定。
本申请实施例中，频率选择表面24整体上可以大致为二维平面结构。从横截面结构来说，频率选择表面24可以包括绝缘基材层和导体层，导体层依附于绝缘基材层；或者，频率选择表面24可以含有导体层，但没有绝缘基材层。绝缘基材层由绝缘材料制成，导体层由导体材料制成。频率选择表面24的可设计性好，可以较为轻便。
本申请实施例中，频率选择表面24可以划分为多个频率选择单元，所有频率选择单元可以按照一定方式排列而成。
例如在一种实施方式中，所有频率选择单元可以紧密连接无间隙。例如图5(a)所示为一种可能的频率选择表面的一种示意性结构，可以在频率选择表面24中划分出多个频率选择单元24a(图5(a)中以纵横交错的虚线表示频率选择单元24a之间的边界，该虚线在实际产品中并不显示)，频率选择单元24a之间紧密连接无间隙。示意性的，频率选择单元24a可以包括内外两个金属部分(用不同阴影线表示)，内外金属部分之间具有缝隙(内外阴影区域之间的空白区域)。
或者在另一种实施方式中，如图5(b)所示，频率选择表面24上可以形成多个缝隙24h，这些缝隙24h例如可以纵横交错分布。缝隙24h可以贯通或者不贯通频率选择表面24。可以基于缝隙24h将频率选择表面24划分为多个频率选择单元24a。对于单个缝隙24h及该缝隙24h两侧的实体部分24e而言，该缝隙24h一侧的实体部分24e以及该缝隙24h的一部分24f可以构成一个频率选择单元24a，该缝隙24h另一侧的实体部分24e以及该缝隙24h的另一部分24g可以构成另一个频率选择单元24a。其中，图5(b)中的虚线可以表示缝隙24h的一部分24f与另一部分24g的分界线(该虚线在实际产品中并不显示)，该虚线例如可以位于缝隙24h的二分之一缝宽处。
本申请实施例中，频率选择单元可以大致为二维平面结构，或者为三维立体结构。一种实施方式中，所有频率选择单元的结构可以相同，此种频率选择表面24可以称为具有周期阵列结构。另一种实施方式 中，所有频率选择单元的结构不全相同，例如任意两个频率选择单元的结构均不同(可以将每个频率选择单元均称为第一频率选择单元)；或者存在至少两个结构相同的频率选择单元(可以将每个这样的频率选择单元称为第一频率选择单元)，但该第一频率选择单元的结构与其他频率选择单元的结构不同。此种频率选择表面24可以称为具有准周期阵列结构。
如图4所示，示意性的，频率选择表面24可以只有一层。在其他实施例中，可以有多层频率选择表面24，各层频率选择表面24之间可通过绝缘材料或者空气隔开。
频率选择表面24具有特定的频率选择作用，其可以对一种频段的入射波呈现出透射性，对另一种频段的入射波呈现出反射性，从而可以有效控制入射电磁波的透射和反射。频率选择表面24例如可以是空间滤波器，与电磁波相互作用表现出明显的带通或带阻的滤波特性。多层的频率选择表面24可以用做多阶空间滤波器，能够拓展带宽，并增加频率选择性。
本实施例中，频率选择表面24能够反射第一天线阵列2A辐射的大部分电磁波，因而频率选择表面24可以作为第一天线阵列2A的反射板。频率选择表面24还能够使第二天线阵列2B辐射的电磁波透过，因此频率选择表面24对于第二天线阵列2B而言并不会造成遮挡，频率选择表面24对第二天线阵列2B辐射的电磁波而言相当于是电磁透明的。
本实施例中，参考图4所示，频率选择表面24与天线导电部件3的最小间距，可以不小于第二天线阵列2B的最高工作频率对应的波长的0.1倍。其中，频率选择表面24与天线导电部件3的间距，也即频率选择表面24与结构层33的间距。该设计的意义在于：通过使得频率选择表面24与结构层33的间距保持在合理范围(而不是过小)，能够避免频率选择表面24与结构层33之间产生较强耦合，从而保证电磁隐身性能以及频率选择表面24的频率选择性能。在其他实施例中，可以不对频率选择表面24与天线导电部件3的间距做上述限定。
本实施例中，参考图4所示，频率选择表面24与第一天线阵列2A可以无电连接。频率选择表面24与作为导电基体31的馈电网络也可以无电连接。由于频率选择表面24与第二天线阵列2B分别在不同的天线罩内，频率选择表面24与第二天线阵列2B也可以无电连接。在其他实施例中，若第二天线阵列与第一天线阵列设于同一个天线罩内，频率选择表面24与第二天线阵列及第一天线阵列可以均无电连接。其中，上述的“无电连接”可以指二者在结构上没有通过导体直接连接(例如二者在结构上完全不连接，二者之间具有间距；或者二者通过绝缘体连接)，且不存在信号耦合。
上述的“无电连接”设计的目的在于：由于频率选择表面24与第一天线阵列2A及第二天线阵列2B均无电连接，因此天线阵列的馈电信号不会通过频率选择表面24传输，这能够缩短馈电路径，降低损耗，还能使得频率选择表面24的结构较为简单，降低成本。由于频率选择表面24与作为导电基体31的馈电网络无电连接，因此频率选择表面24与该馈电网络之间基本不存在耦合，能够保证电磁隐身性能以及频率选择表面24的频率选择性能。
在其他实施例中，根据产品需要，频率选择表面24也可以与作为导电基体31的馈电网络电连接，这能够减少馈电网络产生的感应电流对第一天线阵列2A与第二天线阵列2B的影响，提升多频段基站天线的性能。
图6表示一种实施例中的基站天线70的内部框架结构，与图4所示的基站天线2不同的是，基站天线70的第二天线可以包括两个第二天线阵列2B，两个天线阵列2B可以分别位于两个第二天线罩76内。示意性的，第一天线阵列2A的长度可以大于任一个天线阵列2B的长度，第一天线阵列2A对两个天线阵列2B造成物理上的遮挡。其中一个第二天线阵列2B中的辐射单元可以包括辐射体751(可以称为第四辐射体)，另一个第二天线阵列2B中的辐射单元可以包括辐射体771(可以称为第五辐射体)，辐射体751的频段与辐射体771的频段可以不同。示意性的，辐射体751与辐射体771的频段，均可以高于辐射体221的频段。
图6画出了第二天线中的两个第二天线阵列2B，两个第二天线阵列2B的频段不同，这仅仅是一种举例。在其他实施例中，根据产品需要，第二天线也可以包括两个以上的第二天线阵列2B。其中，所有第二天线阵列2B的频段可以相同或者不全相同。
图6所示的实施例，频率选择表面24能够透过两个第二天线阵列2B的电磁波；天线导电部件3的隐身设计，能够改善电磁阴影问题；天线阵列的层叠设计，能够在有限的天面口径下设置更多频段和通道的天线阵列；两个天线可以分别单独部署，实现了不同频段天线的解耦设计与灵活部署。并且，由于第二天线可以具有多种频段，因此进一步扩展了频段数和通道数。
图7表示一种实施例中的基站天线80的内部框架结构。与图4所示的基站天线2不同的是，在基站 天线80中，第一辐射单元22的馈电结构222可以穿过频率选择表面84上的通孔以伸到频率选择表面84的另一侧，使得第一辐射体221与天线导电部件3分别位于频率选择表面84的相对两侧。可以理解的是，频率选择表面84也位于第一辐射体221与第二天线阵列2B之间。
在图7所示实施例中，频率选择表面84的位置可以根据天线设计要求确定。而将天线导电部件3设在频率选择表面84背向第一辐射体221的一侧，使得天线导电部件3与第一辐射体221的距离较大，能减少天线导电部件3(包括馈电网络)对第一天线阵列2A的近场耦合的影响，保证第一天线阵列2A的性能。
图8表示一种实施例中的基站天线90的内部框架结构。图8所示实施例可以视为是图4与图7所示实施例的结合。
如图8所示，第一天线中的频率选择表面可以有两个，分别称为第一频率选择表面941与第二频率选择表面942。第一频率选择表面941与第二频率选择表面942层叠且间隔布置，第一辐射单元22的馈电结构222可以穿过第一频率选择表面941上的通孔以伸到第一频率选择表面941的另一侧，使得第一辐射体221与天线导电部件3分别位于第一频率选择表面941的相对两侧。示意性的，第二频率选择表面942可以位于天线导电部件3与第二天线阵列2B之间。可以理解的是，第一频率选择表面941也位于第一辐射体221与第二频率选择表面942之间，天线导电部件3位于第一频率选择表面941与第二频率选择表面942之间。
在图8所示实施例中，第一频率选择表面941与第二频率选择表面942的位置可以根据天线设计要求确定。可以将天线导电部件3(导电基体31为馈电网络)的厚度(例如图8中沿竖直方向的尺寸)做的较小，使其能够位于第一频率选择表面941与第二频率选择表面942之间，这样能够使得第一天线的总厚度较小。另外，多层频率选择表面可以增强滤波选择性，有利于拓展第二天线的带宽。
在其他实施例中，与图8所示不同的是，第二频率选择表面942的位置还可以是：第二频率选择表面942被馈电结构222穿过，第二频率选择表面942位于第一辐射体221与天线导电部件3之间，其中第二频率选择表面942距离第一辐射体221较远，第一频率选择表面941距离第一辐射体221较近。或者，第二频率选择表面942可以被天线导电部件3穿过，第一辐射单元22与天线导电部件3的一部分位于第二频率选择表面942的一侧，天线导电部件3的另一部分以及第二天线阵列2B位于第二频率选择表面942的另一侧。
图9表示另一种实施例中的基站天线100的内部框架结构，图9所示实施例可以认为是基于图8所示实施例的一种变形方案，其中，图9的视图方向可以是图8中的侧视方向。
图9中示意出了多个天线导电部件3(覆盖有结构层33的馈电网络)，每个天线导电部件3中的馈电网络均可以与沿垂直于画面的方向分布的多个第一辐射单元22的馈电结构222连接(由于视角关系，仅示意出了每个馈电网络与一个馈电结构222连接)。与图8所示的基站天线90不同的是：在基站天线100中，天线导电部件3可穿过第一频率选择表面141上的通孔以伸到第一频率选择表面141的另一侧，使得第一辐射单元22以及天线导电部件3的一部分位于第一频率选择表面141的一侧、天线导电部件3的另一部分位于第一频率选择表面141的另一侧。示意性的，第二频率选择表面142可位于第一频率选择表面141与第二天线阵列2B之间。可以理解的是，第一频率选择表面141也位于第一辐射体221与第二频率选择表面142之间。
在图9所示实施例中，第一频率选择表面141与第二频率选择表面142的位置可以根据天线设计要求确定。通过使天线导电部件3(导电基体31为馈电网络)穿过第一频率选择表面141，能够使得馈电网络与第一辐射体221的距离不至于过大(相较于图8所示实施例而言)，进而减小损耗；又能够使馈电网络与第一辐射体221的距离不至于过小(相较于天线导电部件3与第一辐射单元22完全位于第一频率选择表面141的同一侧的方案)，以改善馈电网络对第一天线阵列2A的近场耦合的影响。另外，多层频率选择表面可以增强滤波选择性，有利于拓展第二天线的带宽。
在其他实施例中，与图9所示不同的是，第二频率选择表面142的位置还可以是：与第一频率选择表面141一样，第二频率选择表面142也被天线导电部件3穿过，第一辐射单元22以及天线导电部件3的一部分位于第二频率选择表面142的一侧、天线导电部件3的另一部分位于第二频率选择表面142的另一侧，第一频率选择表面141可以距离第一辐射单元22较近，第二频率选择表面142可以距离第一辐射单元22较远。
基于以上任意实施例中的层叠布置设计与电磁隐身设计，在图10所示(图10的视图方向可以是图9中的俯视方向)的实施例中，基站天线的第一天线阵列的辐射单元的第一辐射体可以包括多个不同频段的 辐射体，例如不同频段的辐射体211(可称为第二辐射体)与辐射体213(可称为第三辐射体)。不同频段的辐射体的排布方式可以根据需要设计，例如图10所示，一行辐射体211与一行辐射体213可以交替往复排布，即按照一行辐射体211-一行辐射体213-一行辐射体211-一行辐射体213-一行辐射体211的次序排布。不同频段的辐射体可以均与频率选择表面无电连接，频率选择表面可对所有频段的辐射体的辐射信号进行反射。
示意性的，如图10所示，天线导电部件中的馈电网络可以包括第一馈电网络212与第二馈电网络214，第一馈电网络212与辐射体211电连接以向辐射体211馈电，第二馈电网络214与辐射体213电连接以向辐射体213馈电。第一馈电网络212与第二馈电网络214均具备电磁隐身性能。第一馈电网络212与第二馈电网络214可以均与频率选择表面无电连接。
图10所示的实施例中，通过使第一天线阵列包括多个频段，能够增加基站天线的频段和通道数，增加了天面口径利用率。通过使第一馈电网络212与第二馈电网络214都不与频率选择表面电连接，可以减弱第一天线罩21内的不同频段的辐射体之间的互耦，保证电磁隐身性能与频率选择表面的频率选择性能，最终提升天线性能。
以上各个实施例中，示意性的，可以对频率选择表面与天线导电部件的最小间距进行限定(该最小间距可以不小于第二天线阵列的最高工作频率对应的波长的0.1倍)，以避免频率选择表面与结构层之间产生较强耦合，从而保证电磁隐身性能以及频率选择表面24的频率选择性能。在一些场景下，可以无需对该最小间距进行限定，而是将频率选择表面制造成具有准周期阵列结构，以实现减小频率选择表面与结构层之间的耦合的目的。下文将进行说明。
图11(a)和图11(b)以天线导电部件3及位于天线导电部件3以及下方的一层频率选择表面24为例，说明了频率选择表面的准周期阵列结构。可以理解的是，这并非是在限定频率选择表面的数量及其与天线导电部件的相对位置，也并非是在限定天线导电部件的结构与类型，实际上频率选择表面的准周期阵列结构设计方案可以适用于以上任一实施例。
如图11(a)所示，一种实施例中，频率选择表面24包括多个频率选择单元24b与多个频率选择单元24c。其中，频率选择单元24c(可以称其为第一频率选择单元)与频率选择单元24b的结构不同，或者说频率选择单元24c与频率选择表面24中的其他频率选择单元的结构不同。并且，频率选择单元24c可以是靠近天线导电部件3的频率选择单元，例如频率选择单元24c可以与天线导电部件3在频率选择表面24上的正投影存在重叠。“存在重叠”可以包括频率选择单元24c与该正投影完全重叠，或者频率选择单元24c的一部分与该正投影的一部分重叠(频率选择单元24c与该正投影错位)，或者频率选择单元24c的一部分与该正投影的全部重叠(频率选择单元24c较大，该正投影较小，且该正投影全部位于频率选择单元24c的边界内)，或者，频率选择单元24c的全部区域与该正投影的一部分重叠(频率选择单元24c较小，该正投影较大，频率选择单元24c全部位于该正投影的边界内)等。
本实施例中，若频率选择表面24为两层以上，可以对所有频率选择表面24均做上述准周期阵列结构设计，或者仅对距离天线导电部件3较近的频率选择表面24做上述准周期阵列结构设计。
本实施例中，通过将频率选择表面24制造成准周期阵列结构，使靠近天线导电部件3的频率选择单元的结构与其他频率选择单元的结构不同，能够减小频率选择表面24与结构层3之间的耦合，从而保证电磁隐身性能以及频率选择表面24的频率选择性能。
本实施例的方案能够适用于如下场景：若由于产品设计限制，导致频率选择表面与天线导电部件的间距无法满足该最小间距的要求，则可以通过本实施例的方案减小频率选择表面与结构层之间的耦合。可以理解的是，在频率选择表面与天线导电部件的间距已经满足该最小间距的要求的场景中，仍然可以采用本实施例的方案，以进一步减小频率选择表面与结构层之间的耦合。
与图11(a)所示不同的是，如图11(b)所示，在另一种实施例中，可以将原本为周期阵列结构的频率选择表面中靠近天线导电部件3的区域24d的导体层去除，以制造出具有准周期阵列结构的频率选择表面24。其中，对于包括绝缘基材层与导体层的频率选择表面24而言，区域24d仅可以有绝缘材料而无导体材料，区域24d的两侧可以分布有频率选择单元24b，频率选择单元24b可以包括绝缘材料与导体材料；对于不含绝缘基材层的频率选择表面24而言，区域24d可以镂空，频率选择单元24b可以仅含有导体材料。
如图11(b)所示，区域24d可以与天线导电部件3在频率选择表面24上的正投影存在重叠，此处的“存在重叠”的含义可与上文所述可以一致。可以理解的是，可以认为频率选择表面24包括第一部分与第二部分，第一部分与第二部分相连，第一部分即区域24d所在的部分，第一部分不含导体材料，第二部分即 频率选择单元24b所在的部分，第二部分含有导体材料。
本实施例的方案通过将频率选择表面靠近天线导电部件3的区域的导体层去除，能够极大减少频率选择表面与结构层之间的耦合。
上文对本申请实施例的基站天线的整体框架结构做了说明。下文将详细说明本申请实施例的天线导电部件的电磁隐身设计。可以理解的是，下文所述的各天线导电部件均可以应用在本申请任一实施例的基站天线中。
上文对本申请实施例的基站天线的整体框架结构做了说明。下文将详细说明本申请实施例的天线导电部件的电磁隐身设计。可以理解的是，下文所述的各天线导电部件均可以应用在本申请任一实施例的基站天线中。
图12示意出了图4中的天线导电部件3的一种原理性立体结构，图13示意出了图12中的天线导电部件3的原理性侧视结构。如图12与图13所示，天线导电部件3可以包括导电基体31与结构层33，结构层33包括至少两个结构单元32。
示意性的，导电基体31可以大致呈圆柱状，其轴向长度例如至少为1*λ(λ为导电基体31所遮挡的第二天线阵列2B的最低频段对应的波长)。可以理解的是，大致呈圆柱状的导电基体31仅仅是一种举例，本申请实施例并不限定导电基体的实际形状与构造。例如，导电基体的横截面外形包括不限于四边形、圆形、椭圆、六边形等。
图12示意性地画出了五个结构单元32。结构单元32的结构可以根据需要设计，例如可以为片状、环状等。
如图12所示，所有结构单元32均位于导电基体31的外侧。图12所示的实施方式中，这些结构单元32可以仅环绕导电基体31的外周面(该外周面是环绕导电基体31的轴线的表面)并环绕该外周一周，并未设在导电基体31的端面(该端面是垂直于导电基体31的轴线的表面)上。在另一种实施方式中，结构单元32可以同时分布在该外周面以及该端面上。下文将以图12所示的实施方式为例继续说明。
在一种实施方式中，结构单元32可以由导体材料制造，此种结构单元32例如可以是钣金成型的金属件，其重量与结构强度较大。在另一种实施方式中，结构单元32可以包括导体层与绝缘层，二者层叠设置，且绝缘层靠近导电基体31，导体层背离导电基体31。导体层由导体材料制造，绝缘层由绝缘材料制造。导体层可以较薄，结构强度较弱，导体层依附在绝缘层上，绝缘层能对导体层进行支撑和加强。
如图12与图13所示，每个结构单元32与导电基体31之间均可以具有间隔3a，也即每个结构单元32与导电基体31可以是隔开的，二者并未直接相连。间隔3a的径向尺寸(即间隔3a沿导电基体31的径向的尺寸，该尺寸也可以称为电厚度)例如可以为0.5*λ(λ为导电基体31所遮挡的第二天线阵列2B的最低频段对应的波长)。
如图12与图13所示，对于仅由导体材料制造的结构单元32而言，该结构单元32与导电基体31之间的间隔3a内可以填充绝缘介质(图13中用斜线阴影表示绝缘介质)。
一种实施方式中，绝缘介质可以连续分布并覆盖导电基体31的整个外周面，也即绝缘介质既分布在间隔3a内，也分布在相邻结构单元32之间的缝隙内(该缝隙将在下文继续说明)。
另一种实施方式中，绝缘介质在导电基体31的整个外周面上呈离散分布，例如绝缘介质仅分布在间隔3a内，但并未分布在相邻结构单元32之间的缝隙内。其中，每个间隔3a内的绝缘介质可以是离散分布的，各处的绝缘介质形成类似若干个连接柱的结构，各处的绝缘介质之间形成间隙，该间隙内存在空气；或者，每个间隔3a内的绝缘介质是连续分布的。
本实施例中，该绝缘介质既可以起到连接结构单元32与导电基体31的作用，又能将结构单元32与导电基体31电隔绝。
本实施例中，导电基体31的外周面上各处的绝缘介质可以是同一种材料，也即导电基体31的外周面上各处的绝缘介质具有相同的介电常数。在其他实施例中，导电基体的外周面上各处的绝缘介质可以是具有不同介电常数的不同材料，该方案将在下文继续说明。
本实施例中，对于包括导体层与绝缘层的结构单元32而言，该结构单元32中的绝缘层可以替代间隔3a内的绝缘介质，也即此种包括导体层与绝缘层的结构单元32可以与导电基体31连接，结构单元32与导电基体31之间可以无间隔。可以理解的是，根据产品需要，此种包括导体层与绝缘层的结构单元32与导电基体31之间也可以有间隔，该间隔内可以额外填充绝缘介质。
本实施例中，上述的绝缘介质(例如离散分布的绝缘介质)也可以称为绝缘支架，该绝缘支架起到连接并隔绝结构单元32与导电基体31的作用。当没有绝缘介质且结构单元32包括绝缘层与导电层时，结 构单元32中的该绝缘层也可以称为绝缘支架，结构单元32通过该绝缘支架与导电基体31连接，并与导电基体31隔绝。
如图12所示，所有结构单元32可以沿导电基体31的轴向依次间隔分布，每相邻的两个结构单元32(可以将其中一个结构单元32称为第一结构单元，将另一个结构单元32称为第二结构单元)之间均可以形成缝隙，该缝隙环绕导电基体31一周。上述的绝缘介质可以分布在该缝隙内，也可以不在该缝隙内。每个结构单元32均具有导电性能，使得该缝隙实质上可形成电容，可以称其为第一电容32a，其中，第一电容32a两侧的结构单元32可作为第一电容32a的极板。当绝缘介质分布在该缝隙内时，该缝隙内的绝缘介质也可以作为第一电容32a的组成部分。
如图12和图13所示，第一电容32a可以包括第一部分32b、第二部分32c、第三部分32d和第四部分32e，这四个区域依次首尾相连。第一部分32b与第三部分32d可以是中心对称的，二者的对称中心可以是导电基体31的轴心。第一部分32b与第三部分32d呈中心对称分布，意味着二者的结构一致(结构一致包括两个区域内绝缘介质的分布情况也一致)，其中一个绕对称中心旋转180度后与另一个重合。第二部分32c与第四部分32e可以是中心对称的，二者的对称中心可以是导电基体31的轴心。第二部分32c与第四部分32e呈中心对称分布，意味着二者的结构一致(结构一致包括两个区域内绝缘介质的分布情况也一致)，其中一个绕对称中心旋转180度后与另一个重合。
本实施例中，第一电容32a的电容值C满足电容公式：C＝εS/d，ε为极板间介质的介电常数，S为极板面积，d为极板间的距离。其中，极板即第一电容32a两侧的结构单元32，极板间介质即该绝缘介质(对于该绝缘介质分布在结构单元32之间的缝隙内的情况)或者空气(对于结构单元32之间的缝隙内没有该绝缘介质的情况)，S为相邻的结构单元32的正对面积，d为缝隙宽度。
本实施例中，由于第一部分32b与第三部分32d呈中心对称分布，根据上述电容公式可知：第一部分32b与第三部分32d的电容值相等。同理，由于第二部分32c与第四部分32e呈中心对称分布，因此第二部分32c与第四部分32e的电容值相等。下面将以第一部分32b和第二部分32c为描述对象，继续说明第一电容32a的特征。
如图12所示，第一部分32b对应的缝隙可以具有均匀宽度，即第一部分32b的缝隙的两边基本平行，第一部分32b的各处的缝隙宽度可以一致，或称第一部分32b的缝隙具有同一宽度。第二部分32c对应的缝隙可以具有非均匀宽度，即第二部分32c的缝隙的两边不平行，第二部分32c的各处的缝隙宽度不一致，或称第二部分32c的缝隙具有可变宽度。示意性的，第二部分32c的缝隙的两条边可以是曲线(例如为弧线)，第二部分32c的两端的缝隙宽度可以较小，位于两端之间的中部的缝隙宽度可以较大，从两端到中部的缝隙宽度可以是渐变的，由此使得第二部分32c的各处的缝隙宽度不一致。
如图12所示，第一部分32b的缝隙的最大宽度(也第一部分32b的任意处的缝隙宽度)可以小于或等于第二部分32c的缝隙的最小宽度(例如第二部分32c与第一部分32b邻接处的缝隙宽度)，也即从整体来上看，第一部分32b的缝隙宽度是小于第二部分32c的缝隙宽度的。因此根据上述电容公式可知：第一部分32b的电容值大于第二部分32c的电容值。
综上所述，在第一电容32a中，第一部分32b的缝隙宽度＝第三部分32d的缝隙宽度＜第二部分32c的缝隙宽度＝第四部分32e的缝隙宽度，第一部分32b的电容值＝第三部分32d的电容值＞第二部分32c的电容值＝第四部分32e的电容值。也即，第一电容32a的不同区域的缝隙宽度不同，导致第一电容32a的不同区域的电容值不同。
如图12所示的实施方式中，所有结构单元32的形状可以一致且均匀间隔分布，使得所有缝隙的形状也一致并均匀间隔分布，这样形成的结构层33可以称为具有周期性结构。
在其他实施方式中，所有结构单元32的形状可以不全相同(指任意两个结构单元32的形状都不同。或者，至少有两个结构单元32的形状相同，但不是所有结构单元32的形状都相同)，和/或，所有结构单元32可以不是均匀间隔分布(指对于结构单元32之间的所有缝隙而言，任意两个缝隙的形状不同；或者至少有两个缝隙的形状相同，但不是所有缝隙的形状都相同)。这样使得所有缝隙的形状不全一致和/或非均匀间隔分布，由此形成的结构层可以称为准周期性结构。例如，准周期性结构可以是在周期性结构中删除若干个结构单元得到的结构。具有准周期性结构的结构层，能够与导电基体31的外形结构适配。例如，若导电基体31的外表面某处具有凸起，则结构层在该处可以避让该凸起，以形成准周期性结构。
下面将说明天线导电部件3的电磁隐身原理。
图12与图13中还示出了波源与天线导电部件3的关系，其中波源指电磁波的源头，对于第二天线阵列2B的辐射过程，波源即为第二天线阵列2B；对于第二天线阵列2B的接收过程，波源可以理解为空中环 境。如图12与图13所示，在KEH三坐标系中，K表示电磁波的传播方向，E表示电场方向，H表示磁场方向，坐标系的原点可以指代波源位置。
结合图12与图13所示，示意性的，较窄的第一部分32b可以距离波源最近，较窄的第三部分32d可以距离波源最远。当电磁波沿K向传播至第一部分32b内时，电磁波K将改变传播方向，并被约束在缝隙内沿缝隙的延伸方向传播。从第一部分32b起，电磁波可以分为两路传播，一路电磁波沿着第一部分32b、第二部分32c与第三部分32d的路径传播，另一路电磁波沿着第一部分32b、第四部分32e与第三部分32d的路径传播。两路电磁波传播至第三部分32d时，将会以传播方向K从第三部分32d射出。
本实施例中，如图13所示，第一部分32b可以接收波源的电磁波，第三部分32d可出射电磁波，第一部分32b与第三部分32d相当于贴片天线。第二部分32c与第四部分32e可将电磁波束缚在其内传输，二者可相当于缝隙传输线(slotline)。
由此可见，第一电容32a的作用是改变波源发出的电磁波的传播方向，并将电磁波约束在其内进行传播，使得电磁波能够绕着天线导电部件3进行传播，并可以保持电磁波从第一电容32a内射出时的传播方向不变。因此，即使天线导电部件3对波源存在遮挡，但是由于存在第一电容32a，使得电磁波能够绕过天线导电部件3传播至天线导电部件3的后方，从而减少或者消除了电磁阴影。并且，由于可以不改变电磁波的传播方向，因而可以保证电磁波的传播特性不变。
所以，本实施例的天线导电部件3，通过在导电基体31的外周设置至少两个结构单元32，并形成第一电容32a，使得导电基体31相对电磁波具有电磁隐身性能，避免或减少了导电基体31对电磁波的遮挡。
本实施例中，由于第一电容32a的不同区域的电容值不同，使得不同频段的电磁波信号均能够以各自的电长度在缝隙内发生谐振，从而使得不同频段的电磁波均能通过缝隙。也即，通过使第一电容32a的不同区域的电容值不同，使缝隙能够允许多种频段的电磁波通过，从而拓展了隐身带宽。
根据上述的原理说明容易理解，天线导电部件3中只要存在一个第一电容32a，即能改善导电基体31对电磁波的遮挡，拓展隐身带宽。当然根据实际需要，第一电容32a的数量可以是多个。
本实施例中，靠近波源的第一部分32b的电容值较大的设计，能够满足一些频段的电磁波的传播需要，但这并非是对本申请实施例的限定。在其他实施例中，第一电容32a的各个区域的电容值大小，与距离波源的远近的对应关系可以根据需要设计，不限于上文所述。例如，针对一些频段的电磁波，可以使得第一电容32a中的距离波源较近的区域具有较小的电容值。
本实施例中，使得靠近波源的第一部分32b的缝隙具有均匀宽度，距离波源稍远的第二部分32c的缝隙具有非均匀宽度，这仅仅是一种举例，并非是对本申请实施例的限定。例如，也可以使得靠近波源的第一部分32b的缝隙具有非均匀宽度，使得距离波源稍远的第二部分32c的缝隙具有均匀宽度，且使得第一部分32b的最大缝隙宽度小于或等于第二部分32c的最小缝隙宽度(也即第二部分32c的任意处的缝隙宽度)，进而使得第一部分32b电容值大于所述第二部分32c的电容值。
本实施例中，以缝隙的宽度变化将第一电容32a分为四个部分，这仅仅是一种举例，并非是对本申请实施例的限定，还可以设计缝隙的宽度变化，以从第一电容32a中划分出其他数量的部分。实际上根据产品需要，本申请实施例中的缝隙只要不是恒定宽度缝隙即可，这样就能够实现拓展隐身带宽的目的。
本实施例中，第一部分32b与第三部分32d中心对称，第二部分32c与第四部分32e中心对称，该设计能够能保证电磁波经第一电容32a射出后，保持之前的传播方向与传播特性(例如极化特性、频段等)。但是该设计仅仅是一种举例，并非是对本申请实施例的限定。例如，可以仅使第一部分32b与第三部分32d的形状一致，但位置上并不要求中心对称，这样虽然改变了电磁波的传播方向与传播特性，但是可以满足天线信号的互易性，还可以使得从第一电容32a射出的电磁波折射到其他方向进而扩大第二天线阵列2B的信号扫描范围(例如一种多输入多输出MIMO天线可应用该方案)。或者，可以使得第一部分32b与第三部分32d的形状不同，且位置上不要求中心对称。
上文详细说明了电磁隐身设计的原理，下面将结合图4说明电磁隐身设计在基站天线2中的具体应用。
如图4所示以及上文所述，基站天线2中的天线导电部件3可以是具有覆盖有结构层33的馈电网络。天线导电部件3对第二天线阵列2B具有一定遮挡，但是由于设置了结构层33，第二天线阵列2B辐射的电磁波将会绕过天线导电部件3继续传播，或者电磁波将会绕过天线导电部件3而被第二天线阵列2B接收到，从而能减少或者消除电磁阴影。由此，第二天线阵列2B可以具备大角度扫描能力，其口径(例如图4中的水平方向的口径)可以得到扩展，而不会受到前置的第一天线的馈电网络的遮挡与限制。
与上述实施例不同的是，如图14所示，在另一种实施例中，天线导电部件4的导电基体41可以大致为矩形柱状结构。结构单元42可以大致是由四个平板围成的方形筒状结构。相邻的结构单元42之间的第 一电容可以包括第一部分42b与第二部分42c。第一部分42b可以位于导电基体41的一个侧面的外周，第二部分42c可以位于导电基体41的另一个侧面的外周，第一部分42b与第二部分42c的邻接位置可以对应导电基体41的棱边。
如图14所示，示意性的，第一部分42b与第二部分42c均可以为矩形区域，第一部分42b与第二部分42c的缝隙均具有均匀宽度。第一部分42b的缝隙宽度可以小于第二部分42c的缝隙宽度。可以理解的是，结构单元42的第一电容还可以包括第三部分与第四部分(由于图14视角原因未显示)，第三部分与第一部分42b可以是中心对称的，第四部分与第二部分42c可以是中心对称的。
本实施例中，由于第一部分42b的缝隙宽度小于第二部分42c的缝隙宽度，因此根据上述电容公式，第一部分42b的电容值大于第二部分42c的电容值。也即，第一电容的不同区域的缝隙宽度不同，导致第一电容的不同区域的电容值不同。
如图14所示，示意性的，电磁波的传播方向K可以垂直于天线导电部件4中第一部分42b所在的侧面，但是本实施例的方案并不限于此，例如第一部分42b所在的侧面也可与传播方向K不垂直。
本实施例的方案使得导电基体41相对电磁波具有电磁隐身性能，避免或减少了导电基体41对电磁波的遮挡，还能拓展隐身带宽。另外，天线导电部件4上的缝隙的结构简单，量产性好，并且能满足特定的产品需求。
与图14所示的实施例不同的是，如图15(a)和图15(b)所示，在另一种实施例中，天线导电部件5的相邻的结构单元52之间的第一电容可以包括第一部分52b与第二部分52c，其中，第一部分52b的缝隙可由至少两段子缝隙52d依次弯折连接而成，即若干段子缝隙52d依次连接，且每相邻的两端子缝隙52d形成弯折角。子缝隙52d之间的弯折角度可以根据需要设计，例如可以为90°。第一部分52b的此种缝隙可以形成类似方波的形状。在其他实施方式中，相邻子缝隙52d的弯折角可以不限于90°，以使第一部分52b的缝隙形成其他形状，例如曲线形状(如正弦曲线、抛物线等)。
如图15(b)所示，每段子缝隙52d均可以具有均匀宽度，且所有子缝隙52d的宽度相同，因此子缝隙52d的宽度也即第一部分52b的缝隙宽度d1。第二部分52c的缝隙具有均匀宽度，且第二部分52c的缝隙宽度d2可以大于第一部分52b的缝隙宽度。
本实施例中，第一部分52b中的所有子缝隙52d连接而成的总缝隙长度，可以大于第二部分52c的缝隙长度。对于上述电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)，由于第一部分52b的缝隙长度较大，因此第一部分52b的极板面积S1较大(第一部分52b与第二部分52c的缝隙深度一致)；第二部分52c的缝隙长度较小，因此第一部分52b的极板面积S2较小。
本实施例中，对于第一部分52b与第二部分52c而言，可以使(S1/d1)＞(S2/d2)，从而使第一部分52b的电容值C1＞第二部分52c的电容值C2。也即，本实施例可通过配置第一电容的不同区域的缝隙长度与缝隙宽度，使得第一电容的不同区域的电容值不同。
本实施例的方案使得导电基体51相对电磁波具有电磁隐身性能，避免或减少了导电基体41对电磁波的遮挡，还能拓展隐身带宽。
本实施例的方案可以应用在如下的场景中：当出于制造工艺的限制，无法制造出缝隙宽度小于阈值的规则形状(例如矩形形状)的第一部分时，可以考虑将第一部分设计成图15(a)所示的第一部分52b(第一部分52b可认为是一种不规则形状)，通过增加缝隙长度来弥补缝隙宽度无法做小的工艺限制，最终使得第一部分具有较大的电容值。所以，本实施例的设计能够与已有制造工艺匹配，量产性较好。
在其他实施例中，可以采用与图15(a)所示实施例不同的方案，只要保证(S1/d1)＞(S2/d2)从而使第一部分的电容值大于第二部分的电容值即可。
例如，在一种实施方式中，可以使得第一部分由至少两段子缝隙依次弯折连接而成，第一部分的缝隙长度大于第二部分的缝隙长度，每段子缝隙具有均匀宽度，所有子缝隙的宽度一致，第二部分的缝隙具有均匀宽度，且第二部分的缝隙宽度等于第一部分的缝隙宽度。
或者，在另一种实施方式中，可以使得第一部分由至少两段子缝隙依次弯折连接而成，第一部分的缝隙长度大于第二部分的缝隙长度，但是对子缝隙的宽度不做限定(例如子缝隙可以具有非均匀缝隙，所有子缝隙的宽度不全相同等)，对第二部分的缝隙宽度也不做限定(例如第二缝隙可以具有非均匀宽度，不限定第二缝隙的缝隙宽度与子缝隙的宽度的大小关系)。
或者，在另一种实施方式中，可以使得第一部分由至少两段子缝隙依次弯折连接而成，第二部分也由至少两段子缝隙依次弯折连接而成，除此之外均不做限定。
与图14所示实施例不同的是，如图16所示，在另一种实施例中，天线导电部件6的相邻的结构单元 62之间的第一电容可以包括第一部分62b与第二部分62c。其中，第二部分62c可以跨越导电基体61的一条棱边，并可以分布于导电基体61的两个相邻侧面的外周，也即第二部分62c的一部分位于一个侧面，第二部分62c的另一部分位于另一个侧面，第二部分62c的这两部分弯折连接。第一部分62b可以跨越导电基体61的另一条棱边，并可以分布于导电基体61的另外两个相邻侧面的外周(由于图16视角原因，并未显示出完整的第一部分62b)。另外，电磁波的传播方向K并不垂直于天线导电部件6的任一个侧面。
本实施例的方案使得导电基体61相对电磁波具有电磁隐身性能，避免或减少了导电基体61对电磁波的遮挡，还能拓展隐身带宽。另外，天线导电部件6上的缝隙的结构简单，量产性好，并且能满足特定的产品需求。下面将说明图16所示方案的一种具体应用。
图17和图18示出了图16所示的电磁隐身设计在一种基站天线2’中的具体应用，其中为了突出说明重点，图18仅放大显示了图17中的基站天线2’的右侧部分。
如图17和图18所示，基站天线2’可以包括层叠布置的第一天线与第二天线。
如图17所示，第一天线可以包括第一天线罩21、第一天线阵列2A、频率选择表面24和天线导电部件6。其中，第一天线阵列2A的第一辐射单元22可以包括辐射单元223与辐射单元224，辐射单元223与辐射单元224均可以为多个。辐射单元223与辐射单元224的工作频段可以不同，例如辐射单元223的工作频段可以为690MHz-960MHz，辐射单元224的工作频段可以为1427MHz-2690MHz。辐射单元223与辐射单元224均可以与各自的馈电网络连接。频率选择表面24例如可以有两层。天线导电部件6与第一天线阵列2A可以位于第二天线阵列2B(下文将会描述)的阵面的同侧。示意性的，天线导电部件6中的导电基体61可以是馈电网络中的移相器，天线导电部件6中的结构层63设在移相器的外周。如图18所述，结构层63中的第一电容包括第一部分62b、第二部分62c、第三部分62d和第四部分62e。示意性的，第一部分62b与第三部分62d中心对称，第二部分62c与第四部分62e中心对称。
如图17所示，第二天线可以包括第二天线罩26与第二天线阵列2B。第二天线阵列2B的第二辐射单元25的工作频段可以为3.3GHz-3.8GHz。可以理解的是，第二天线罩26内还可以设置其他部件，例如与第二辐射单元25连接的馈电网络等。
如图18所示，以第二天线阵列2B中的第二辐射单元25作为波源为例，第二辐射单元25距离第一部分62b最近。第二辐射单元25辐射的电磁波大致会沿“斜向”传播至天线导电部件6的两个相邻侧面，因此使得第一部分62b分布在这两个侧面，便于第一部分62b接收电磁波，并将电磁波约束在第一电容内进行传播，最终使电磁波从第三部分62d射出。由于第一部分62b采用“跨越移相器的棱边”式分布，因此第二部分62c、第三部分62d和第四部分62e也是“跨越移相器的棱边”式分布。由此可见，使得第一电容的不同电容值区域均分布在移相器的两个相邻侧面，能够与波源的位置匹配，从而实现较好的电磁隐身效果。
与图14所示实施例相同的是，如图19所示，在另一种实施例中，天线导电部件7包括导电基体71以及至少两个结构单元72，相邻的结构单元72之间形成第一电容，第一电容可以包括第一部分72b与第二部分72c。
与图14所示实施例不同的是，如图19所示，本实施例的结构单元72并非是一体式结构，而是内部具有耦合缝隙，结构单元72位于耦合缝隙两侧的部分完全断开不连接，耦合缝隙两侧的部分可通过该耦合缝隙耦合。示意性的，结构单元72可以包括第一部分721、第二部分722、第三部分723和第四部分724，这四个部分可以分别位于导电基体71的不同侧面。第一部分721与第二部分722之间具有耦合缝隙72f，第二部分722与第三部分723之间具有耦合缝隙72g，第三部分723与第四部分724之间具有耦合缝隙72h，第四部分724与第一部分721之间具有耦合缝隙72i。上述四个耦合缝隙可以将结构单元72分隔成四个独立的部分。当电磁波传播至结构单元72时，电磁波可以“跨过”这些耦合缝隙，因此结构单元72位于耦合缝隙两侧的部分通过耦合缝隙耦合。
如图19所示，示意性的，每个耦合缝隙均沿着导电基体71的棱边延伸。结构单元72具有四个耦合缝隙，四个耦合缝隙将结构单元72分隔成四个独立的部分。以上均仅仅是一种举例，并非是对本实施例的限定。根据产品需要，耦合缝隙的位置与延伸方向可以灵活设计，耦合缝隙的数量可以是至少一个。另外，可以是所有结构单元72均具有耦合缝隙，也可以仅有部分结构单元72具有耦合缝隙。
本实施例中，在结构单元72中形成耦合缝隙，便于将结构单元72的不同部分依次装配到导电基体71上，最后拼成完整的结构单元72，这样能够在一些场景下实现结构单元72的可靠组装。尤其是在导电基体71的尺寸较大、结构单元72的数量较多时，分体组装的方式能够简化组装工艺，提高组装良率。另外，耦合缝隙能够允许某些频段的电磁波通过，使得天线导电部件7具有一定的拓展隐身带宽作用。
可以理解的是，本实施例的耦合缝隙设计可以根据需要应用在本申请的其他任一实施例中。
与图19所示实施例相同的是，如图20所示，在另一种实施例中，天线导电部件8包括导电基体81以及至少两个结构单元82，相邻的结构单元82之间形成第一电容，第一电容可以包括第一部分82b与第二部分82c。结构单元82并非是一体式结构，而是内部具有耦合缝隙，结构单元82位于耦合缝隙两侧的部分完全断开不连接，耦合缝隙两侧的部分可通过该耦合缝隙耦合。
与图19所示实施例不同的是，如图20所示，本实施例的结构单元82可以具有耦合缝隙82f与耦合缝隙82g，耦合缝隙82f与耦合缝隙82g可以分别位于结构单元82的相对两侧。示意性的，耦合缝隙82f与耦合缝隙82g均可以大致在结构单元82的侧面的中部，并非是在结构单元82的棱边处。耦合缝隙82f与耦合缝隙82g可以将结构单元82分隔成第一部分821与第二部分822，第一部分821与第二部分822均可以近似呈C形结构。示意性的，本实施例的结构层可以具有周期性结构，因此所有结构单元82的同侧的耦合缝隙可以共线。
本实施例中，在结构单元82中形成耦合缝隙，便于将结构单元82的不同部分依次装配到导电基体81上，最后拼成完整的结构单元82，这样能够在一些场景下实现结构单元82的可靠组装。尤其是在导电基体81的尺寸较大、结构单元82的数量较多时，分体组装的方式能够简化组装工艺，提高组装良率。由于结构单元82的部件数量较少，可以一定程度上简化组装工艺。另外，耦合缝隙能够允许某些频段的电磁波通过，使得天线导电部件8具有一定的拓展隐身带宽作用。
可以理解的是，本实施例的耦合缝隙设计可以根据需要应用在本申请的其他任一实施例中，包括下文将要描述的实施例。
与图14所示实施例相同的是，如图21所示，在另一种实施例中，天线导电部件9包括导电基体91以及至少两个结构单元92，相邻的结构单元92之间形成第一电容，第一电容可以包括第一部分92b与第二部分92c。
与图14所示实施例不同的是，如图21所示，每个结构单元92的局部区域可以镂空形成镂空区。示意性的，每个结构单元92的两个相对侧面均可以形成镂空，分别形成镂空区92f与镂空区92g。在其他实施方式中，可以根据产品需要设计镂空区的位置及数量，不限于图15所示。例如，只要至少一个结构单元92形成镂空区即可。
本实施例中，在结构单元92上形成镂空区，能够减轻重量，有利于减小天线导电部件9的重量。特别是当结构单元92为较重的金属件时，开设镂空区能极大减重。另外，当电磁波传播至天线导电部件9附近时，电磁场主要分布在第一电容处，其余区域的电磁场很弱，因此开设镂空区也基本不影响电磁波的传播特性。
可以理解的是，本实施例的镂空设计可以应用在本申请的其他任一实施例中，包括下文将要描述的实施例。
与上述各个实施例相同的是，如图22所示的实施例中，天线导电部件10可以包括导电基体101以及至少两个结构单元102，相邻的结构单元102之间形成第一电容102a。
与上述各个实施例均不同的是，图22中的第一电容102a可以具有均匀的缝隙宽度，也即第一电容102a的缝隙的各个位置的宽度可以一致。并且，结构单元102与导电基体101之间可以填充绝缘介质，绝缘介质例如可以覆盖导电基体101的整个外周面。绝缘介质可以包括第一绝缘介质103a与第二绝缘介质103b，第一绝缘介质103a的介电常数可以大于第二绝缘介质103b的介电常数。第一绝缘介质103a与第二绝缘介质103b例如可以沿着导电基体101的长度方向从导电基体101的一端延伸到另一端，并且二者可以在导电基体101的周向方向上交替排布，以形成图23所示的排布方式：第一绝缘介质103a-第二绝缘介质103b-第一绝缘介质103a-第二绝缘介质103b。第一绝缘介质103a可以分布于导电基体101的两个相邻侧面，第二绝缘介质103b也可以分布于导电基体101的两个相邻侧面，第一绝缘介质103a与第二绝缘介质103b均可以跨越导电基体101的棱边。
如图22与图23所示，本实施例中，可以在第一电容102a中定义出第一部分、第二部分、第三部分与第四部分，第一部分距离波源最近，第一部分内填充有第一绝缘介质103a，第二部分与第一部分相邻，第二部分内填充有第二绝缘介质103b，第三部分与第一部分相对(例如可以中心对称)，第三部分内填充有第一绝缘介质103a，第四部分与第二部分相对(例如可以中心对称)，第四部分内填充有第二绝缘介质103b。
根据上述的电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)，对于第一电容102a的各个区域而言，在S与d均一致的情况下，由于第一部分内的第一绝缘介质103a的介电 常数较大，因此第一部分的电容值较大；由于第二部分内的第二绝缘介质103b的介电常数较小，因此第一部分的电容值较小。第三部分的电容值可以等于第一部分的电容值，第四部分的电容值可以等于第二部分的电容值。因此，本实施例可通过使第一电容102a具有均匀缝隙宽度，且使得第一电容102a的不同区域填充不同介电常数的绝缘介质，使得第一电容102a的不同区域的电容值不同。
本实施例的方案使得导电基体101相对电磁波具有电磁隐身性能，避免或减少了导电基体101对电磁波的遮挡，还能拓展隐身带宽。另外如图22和图23所示，电磁波的传播方向K可以不垂直于天线导电部件10的任一个侧面，该设计使得天线导电部件10能够应用于图12所示的基站天线2’中，通过使得第一电容102a的不同电容值区域均分布在移相器的两个相邻侧面，能够与波源的位置匹配，从而实现较好的电磁隐身效果。详细原理上文已有描述，此处不再重复。
可以理解的是，本实施例通过填充不同介电常数的绝缘介质实现不同区域的电容值差异的设计，可以根据需要应用在本申请的其他任一实施例中。例如，可以不限定第一电容的缝隙尺寸(包括宽度尺寸与长度尺寸等)、缝隙样式(指缝隙为一整条缝隙，还是如图15(a)所示的由若干段子缝隙依次弯折连接而成)、缝隙分布(指缝隙仅分布在导电基体的一个侧面还是分布在两个相邻侧面)等，并在第一电容的不同区域填充不同介电常数的绝缘介质，通过综合配置缝隙的形状尺寸、位置尺寸和绝缘介质的介电常数，最终使第一部分的电容值大于第二部分的电容值。
与图22所示实施例相同的是，如图24所示的实施例中，天线导电部件20可以包括导电基体201以及至少两个结构单元202，相邻的结构单元202之间形成第一电容202a。
与图22所示实施例不同的是，如图24所示，第一电容202a可以无需填充绝缘介质，或者可以填充同种介电常数的绝缘介质。并且，第一电容202a的不同区域可以分别安装电容值不同的电容器件，例如距离波源最近与最远的区域可以安装第一电容器件204(由于图24视角所限，未显示距离波源最远的、位于下方的第一电容器件204)，与第一电容器件204相邻的区域可以安装第二电容器件203。可以将安装第一电容器件204的区域称为第一部分与第三部分，将安装第二电容器件203的区域称为第二部分与第四部分。第一电容器件204的电容值大于第二电容器件203的电容值。第一电容器件204可以是固定电容值的电容器件，或者可以是能在信号控制下改变电容值的电容器件(例如变容管)。第二电容器件203可以是固定电容值的电容器件，或者可以是能在信号控制下改变电容值的电容器件(例如变容管)。第一电容器件204也可以称为第二电容，第二电容器件203也可以称为第三电容。
第一电容器件204与第二电容器件203例如可以通过焊接等方式固定在缝隙内。第一电容器件204与第二电容器件203的数量可以根据需要确定，本实施例不做限定。
第一电容202a的各个区域的电容值可以等于根据上述的电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)计算得到的电容值加上该区域的电容器件的电容值。对于第一电容202a的各个区域而言，在ε、S、d均一致的情况下，根据电容公式C＝εS/d计算得到的电容值相等。由于第一部分内设有电容值较大的第一电容器件204，因此第一部分的电容值较大；由于第二部分内设有电容值较小的第二电容器件203，因此第二部分的电容值较小。第三部分的电容值可以等于第一部分的电容值，第四部分的电容值可以等于第二部分的电容值。
因此，本实施例可通过使第一电容202a具有均匀缝隙宽度，且使得第一电容202a的不同区域安装不同电容值的电容器件，使得第一电容202a的不同区域的电容值不同。
本实施例的方案使得导电基体201相对电磁波具有电磁隐身性能，避免或减少了导电基体201对电磁波的遮挡，还能拓展隐身带宽。示意性的，当电容器件为可变电容的电容器件时，可以根据波源的扫描角度变化，适应性地调整相应区域的电容器件的电容，进而调整该区域的电容值大小，确保天线导电部件20对波源的电磁隐身效果。
基于本实施例的原理容易得出其他变形方案。例如，可以仅在第一电容202a的部分区域设电容器件(例如第一部分)，不在其他区域设电容器件，同样可以使得第一电容202a的不同区域的电容值不同。另外，通过在区域内设置电容器件影响区域的电容值的设计，可以根据需要应用在本申请的任一实施例中。例如，可以不限定第一电容的缝隙尺寸、缝隙样式、缝隙分布、绝缘介质的填充情况等，并在第一电容内安装电容器件，通过综合配置缝隙的形状尺寸、位置尺寸、绝缘介质的介电常数及电容器件的电容值，最终使第一部分的电容值大于第二部分的电容值。
在以上任一实施例中，结构单元与导电基体之间可以形成电容(例如称为平板电容)，该平板电容可以影响绕过天线导电部件的电磁波的频段。出于产品需要(例如减小体积的需要)，可能希望减小结构单元与导电基体的间隔。但是间隔减小可能导致绕过天线导电部件的电磁波的频段提高，改变电磁波的传播 特性。
有鉴于此，在以上任一实施例的基础上，天线导电部件还可以包括电感元件，电感元件可以设在结构单元与导电基体的间隔内，并连接结构单元与导电基体，以使结构单元与导电基体电连接。电感元件可与上述的平板电容构成并联谐振电路，该并联谐振电路能使绕过天线导电部件的电磁波的频段降低。因此，设置电感元件与减小结构单元与导电基体的间隔对频段的影响可以相互抵消，使得绕过天线导电部件的电磁波的频段保持不变，从而保持电磁波的传播特性。
本实施例中，电感元件可以是导体结构件，例如金属柱，此种电感元件可以等效为电感，此种电感元件便于实现天线导电部件的机械加工。或者，电感元件可以直接为电感。
本实施例中，电感元件的位置可以根据需要设计，例如与第一电容相距一定距离，避免过于靠近。电感元件的数量可以根据需要设计，例如每个结构单元均可通过至少一个电感元件与导电基体连接，或者仅有部分结构单元通过电感元件与导电基体连接。
图25示意了一种应用本实施例的电感元件设计的天线导电部件30。如图25所示，天线导电部件30可以包括导电基体301以及至少两个结构单元302，相邻的结构单元302之间形成第一电容302a，第一电容302a的不同区域的电容值不同。结构单元302的每个侧面均通过电感元件303与导电基体301连接，每个结构单元302与导电基体301之间均设有若干个电感元件303。可以理解的，图25所示的天线导电部件30仅仅是一种举例，并非是在限定电感元件303的应用环境。
以上实施例中，天线导电部件中的第一电容的不同区域的电容值不同。在下文所述的实施例中，与上述实施例不同的是，第一电容的不同区域的电容值可以相同。可以理解的是，使得第一电容的不同区域的电容值相同也能实现电磁隐身设计。下面将列举几种第一电容的不同区域的电容值相同的方案。
例如在图26(a)与图26(b)所示的实施例中，天线导电部件40可以包括导电基体401以及环绕到导电基体401一周的至少两个结构单元402，相邻的结构单元402之间形成第一电容402a。其中，图26(a)中的导电基体401例如可以大致为圆柱状，图26(b)中的导电基体401例如可以大致为方柱状。与上述实施例不同的是，任意相邻的结构单元402之间的缝隙均可以具有同一宽度，即缝隙各处的缝隙宽度可以一致。第一电容402a的不同区域的电容值可以相同。
本实施例的第一电容402a同样能够改变波源发出的电磁波的传播方向，并将电磁波约束在其内进行传播，使得电磁波能够绕着天线导电部件40进行传播。因此，即使天线导电部件40对波源存在遮挡，但是由于存在第一电容402a，使得电磁波能够绕过天线导电部件40传播至天线导电部件40的后方，从而减少或者消除了电磁阴影。
例如在图27所示的实施例中，与图19所示的实施例相同的是：天线导电部件50包括导电基体501以及至少两个结构单元502，相邻的结构单元502之间形成第一电容。结构单元502并非是一体式结构，而是内部具有耦合缝隙，结构单元502位于耦合缝隙两侧的部分完全断开不连接，耦合缝隙两侧的部分可通过该耦合缝隙耦合。示意性的，结构单元502可以包括第一部分503、第二部分504、第三部分505和第四部分506，这四个部分可以分别位于导电基体501的不同侧面。第一部分503与第二部分504之间具有耦合缝隙502f，第二部分504与第三部分505之间具有耦合缝隙502g，第三部分505与第四部分506之间具有耦合缝隙502h，第四部分506与第一部分503之间具有耦合缝隙502i。示意性的，每个耦合缝隙均沿着导电基体501的棱边延伸。上述四个耦合缝隙可以将结构单元502分隔成四个独立的部分。当电磁波传播至结构单元502时，电磁波可以“跨过”这些耦合缝隙，因此结构单元502位于耦合缝隙两侧的部分通过耦合缝隙耦合。以上均仅仅是一种举例，并非是对本实施例的限定。根据产品需要，耦合缝隙的位置与延伸方向可以灵活设计，耦合缝隙的数量可以是至少一个。另外，可以是所有结构单元502均具有耦合缝隙，也可以仅有部分结构单元502具有耦合缝隙。
在图27所示的实施例中，与图19所示的实施例不同的是：任意相邻的结构单元502之间的缝隙均可以具有同一宽度，即缝隙各处的缝隙宽度可以一致。所构造的第一电容的不同区域的电容值可以相同。
图27所示的实施例，同样能够改善电磁阴影问题，并且能够实现结构单元502的分体组装，从而简化组装工艺，提高组装良率。另外，天线导电部件50中的耦合缝隙能够允许某些频段的电磁波通过，使得天线导电部件50具有一定的拓展隐身带宽作用。
例如在图28所示的实施例中，与图20所示的实施例相同的是：天线导电部件60包括导电基体601以及至少两个结构单元602，相邻的结构单元602之间形成第一电容。结构单元602并非是一体式结构，而是内部具有耦合缝隙602f与耦合缝隙602g，耦合缝隙602f与耦合缝隙602g可以分别位于结构单元602的相对两侧。示意性的，耦合缝隙602f与耦合缝隙602g均可以大致在结构单元602的侧面的中部，并非 是在结构单元602的棱边处。耦合缝隙602f与耦合缝隙602g可以将结构单元602分隔成第一部分603与第二部分604，第一部分603与第二部分604均可以近似呈C形结构，第一部分603与第二部分604完全断开不连接，第一部分603与第二部分604可通过耦合缝隙602f与耦合缝隙602g耦合。示意性的，所有结构单元602的同一侧的耦合缝隙可以共线。
在图28所示的实施例中，与图20所示的实施例不同的是：任意相邻的结构单元602之间的缝隙均可以具有同一宽度，即缝隙各处的缝隙宽度可以一致。所构造的第一电容的不同区域的电容值可以相同。
图28所示的实施例，同样能够改善电磁阴影问题，并且能够实现结构单元602的分体组装，从而简化组装工艺，提高组装良率。另外，天线导电部件60中的耦合缝隙能够允许某些频段的电磁波通过，使得天线导电部件60具有一定的拓展隐身带宽作用。
或者，还可以基于图15(a)、图16、图21、图22、图24等所示的实施例，得到第一电容的不同区域的电容值相同的实施例。
例如在一种实施例中，与图15(a)所示实施例相同的是，第一电容可以包括第一部分52b(由至少两段子缝隙52d依次弯折连接而成)与第二部分52c。对于第一部分52b与第二部分52c而言有(S1/d1)＞(S2/d2)。与图15(a)所示实施例不同的是，可以在第一部分52b内填充介电常数较小的绝缘介质，在第二部分52c内填充介电常数较大的绝缘介质，根据电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)，可以使得第一部分52b的电容值等于第二部分52c的电容值。由于第一电容中的第三部分与第一部分52b可以是中心对称的，第三部分的电容值可以等于第一部分的电容值；第四部分与第二部分52c可以是中心对称的，第四部分的电容值可以等于第二部分的电容值。因此，第一电容的不同区域的电容值可以相同。
例如在另一种实施例中，可以在图16所示的第一部分62b内填充介电常数较小的绝缘介质，在图16所示的第二部分62c内填充介电常数较大的绝缘介质，使得第一部分62b的电容值等于第一部分62b的电容值。由于第一电容中的第三部分与第一部分62b可以是中心对称的，第三部分的电容值可以等于第一部分的电容值；第四部分与第二部分62c可以是中心对称的，第四部分的电容值可以等于第二部分的电容值。因此，第一电容的不同区域的电容值可以相同。
例如在另一种实施例中，与图21所示实施例不同的是，可以将结构单元92之间的缝隙设置成具有同一宽度，即缝隙各处的缝隙宽度可以一致，使得第一电容的不同区域的电容值可以相同。
例如在另一种实施例中，与图22所示实施例不同的是，可以在结构单元102与导电基体101之间填充同一种绝缘介质，使得第一电容的不同区域的电容值可以相同。
例如在另一种实施例中，与图24所示实施例不同的是，可以通过以上任意方式将第一电容的不同区域的电容值设置成一致的。
上文以图4所示的基站天线2，以及图17与图18所示的基站天线2’为例，详细说明了本申请实施例中的电磁隐身设计。可以理解的是，这仅仅是一种举例，实际上该电磁隐身设计可以应用于本申请的任一实施例中。
以上对本申请实施例的详细介绍。本文中应用了具体个例对本申请的原理及实施例进行了阐述，以上实施例的说明只是用于帮助理解本申请的方法及其核心思想；同时，对于本领域的一般技术人员，依据本申请的思想，在具体实施例及应用范围上均会有改变之处。综上所述，本说明书内容不应理解为对本申请的限制。

Claims (19)

  1. 一种基站天线，其特征在于，
    包括第一天线阵列、频率选择表面、第二天线阵列和天线导电部件；
    所述频率选择表面位于所述第一天线阵列的辐射单元的第一辐射体与第二天线阵列之间，所述频率选择表面用于反射所述第一天线阵列的辐射信号，并透过所述第二天线阵列的辐射信号；
    所述天线导电部件与所述第一天线阵列位于所述第二天线阵列的阵面的同侧；所述天线导电部件包括导电基体、第一结构单元和第二结构单元；所述第一结构单元与所述第二结构单元均环绕所述导电基体一周，所述第一结构单元与所述第二结构单元间隔且相邻排布，并形成电容。
  2. 根据权利要求1所述的基站天线，其特征在于，
    所述导电基体包括馈电网络，所述馈电网络与第一天线阵列的辐射单元连接。
  3. 根据权利要求2所述的基站天线，其特征在于，
    所述频率选择表面与所述第一天线阵列及所述第二天线阵列均无电连接，和/或，所述频率选择表面与所述馈电网络无电连接。
  4. 根据权利要求2或3所述的基站天线，其特征在于，
    所述第一天线阵列与所述天线导电部件位于所述频率选择表面的同侧。
  5. 根据权利要求2或3所述的基站天线，其特征在于，
    所述第一天线阵列的辐射单元包括馈电结构，所述馈电结构连接所述第一辐射体与所述馈电网络，所述馈电结构穿过所述频率选择表面；所述第一辐射体与所述天线导电部件分别位于所述频率选择表面的相对两侧。
  6. 根据权利要求2或3所述的基站天线，其特征在于，
    所述频率选择表面包括层叠且间隔布置的第一频率选择表面与第二频率选择表面，所述第一频率选择表面位于所述第一辐射体与所述第二频率选择表面之间；所述第一天线阵列的辐射单元包括馈电结构，所述馈电结构连接所述第一辐射体与所述馈电网络，所述馈电结构穿过所述第一频率选择表面，所述第一辐射体与所述天线导电部件分别位于所述第一频率选择表面的相对两侧。
  7. 根据权利要求2或3所述的基站天线，其特征在于，
    所述频率选择表面包括层叠且间隔布置的第一频率选择表面与第二频率选择表面，所述第一频率选择表面位于所述第一辐射体与所述第二频率选择表面之间；
    所述天线导电部件穿过所述第一频率选择表面，所述第一天线阵列的辐射单元与所述第二天线阵列分别位于所述第一频率选择表面的相对两侧。
  8. 根据权利要求2-7任一项所述的基站天线，其特征在于，
    所述第一辐射体包括第二辐射体与第三辐射体，所述第二辐射体与所述第三辐射体的频段不同；所述馈电网络包括第一馈电网络与第二馈电网络，所述第一馈电网络与所述第二辐射体电连接，所述第二馈电网络与所述第三辐射体电连接。
  9. 根据权利要求1-8任一项所述的基站天线，其特征在于，
    所述第二天线阵列的辐射单元包括第四辐射体与第五辐射体，所述第四辐射体与所述第五辐射体的频段不同。
  10. 根据权利要求1-9任一项所述的基站天线，其特征在于，
    所述频率选择表面与所述天线导电部件的最小间距大于或等于所述第二天线阵列的最高工作频率对应的波长的0.1倍。
  11. 根据权利要求1-10任一项所述的基站天线，其特征在于，
    所述频率选择表面包括多个频率选择单元，所述多个频率选择单元包括第一频率选择单元，所述第一频率选择单元的结构与其他频率选择单元的结构不同，所述第一频率选择单元与所述天线导电部件在所述频率选择表面上的正投影存在重叠。
  12. 根据权利要求1-10任一项所述的基站天线，其特征在于，
    所述频率选择表面包括相连的第一部分与第二部分，所述第一部分不含导体材料，所述第一部分与所述天线导电部件在所述频率选择表面上的正投影存在重叠，所述第二部分包含导体材料。
  13. 根据权利要求1-12任一项所述的基站天线，其特征在于，
    所述基站天线包括第一天线罩与第二天线罩，所述第一天线阵列、所述频率选择表面及所述天线导电部件均位于所述第一天线罩内，所述第二天线阵列位于所述第二天线罩内。
  14. 根据权利要求1-13任一项所述的基站天线，其特征在于，
    所述电容的不同部分的电容值不同。
  15. 根据权利要求1-14任一项所述的基站天线，其特征在于，
    所述天线导电部件包括至少两个结构单元，所述第一结构单元与所述第二结构单元均为所述至少两个结构单元中的结构单元；至少一个所述结构单元设有耦合缝隙，所述结构单元分别位于所述耦合缝隙两侧的部分被所述耦合缝隙断开，并通过所述耦合缝隙耦合。
  16. 根据权利要求1-15任一项所述的基站天线，其特征在于，
    所述天线导电部件包括至少两个结构单元，所述第一结构单元与所述第二结构单元均为所述至少两个结构单元中的结构单元；所述至少两个结构单元的结构相同，任意相邻的两个所述结构单元之间存在缝隙且所述缝隙的形状相同，任意两个相邻的所述结构单元之间均形成所述电容。
  17. 根据权利要求1-15任一项所述的基站天线，其特征在于，
    所述天线导电部件包括至少两个结构单元，所述第一结构单元与所述第二结构单元均为所述至少两个结构单元中的结构单元；所述至少两个结构单元的结构不全相同，和/或，所述至少两个结构单元之间存在缝隙且所述缝隙的形状不全相同；任意两个相邻的所述结构单元之间均形成所述电容。
  18. 根据权利要求1-17任一项所述的基站天线，其特征在于，
    所述天线导电部件位于所述第一天线阵列与所述第二天线阵列之间。
  19. 一种基站，其特征在于，
    包括抱杆和权利要求1-18任一项所述的基站天线，所述基站天线固定于所述抱杆。
PCT/CN2023/117447 2022-09-08 2023-09-07 基站天线和基站 Ceased WO2024051773A1 (zh)

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