WO2024114603A1 - 信息传输方法及装置、存储介质、电子装置 - Google Patents

信息传输方法及装置、存储介质、电子装置 Download PDF

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Publication number
WO2024114603A1
WO2024114603A1 PCT/CN2023/134475 CN2023134475W WO2024114603A1 WO 2024114603 A1 WO2024114603 A1 WO 2024114603A1 CN 2023134475 W CN2023134475 W CN 2023134475W WO 2024114603 A1 WO2024114603 A1 WO 2024114603A1
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WIPO (PCT)
Prior art keywords
information
pilot
pilots
extremely sparse
reference signal
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PCT/CN2023/134475
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English (en)
French (fr)
Inventor
袁志锋
李志岗
马一华
李卫敏
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ZTE Corp
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ZTE Corp
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Priority to KR1020257020260A priority Critical patent/KR20250111166A/ko
Priority to EP23896752.5A priority patent/EP4601232A4/en
Publication of WO2024114603A1 publication Critical patent/WO2024114603A1/zh
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
    • H04L5/0051—Allocation of pilot signals, i.e. of signals known to the receiver of dedicated pilots, i.e. pilots destined for a single user or terminal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H04B7/0486—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting taking channel rank into account
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0621—Feedback content
    • H04B7/0626—Channel coefficients, e.g. channel state information [CSI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H04L1/0675—Space-time coding characterised by the signaling
    • H04L1/0693—Partial feedback, e.g. partial channel state information [CSI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0001—Arrangements for dividing the transmission path
    • H04L5/0003—Two-dimensional division
    • H04L5/0005—Time-frequency
    • H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A) or DMT
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0091—Signalling for the administration of the divided path, e.g. signalling of configuration information
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0091—Signalling for the administration of the divided path, e.g. signalling of configuration information
    • H04L5/0094—Indication of how sub-channels of the path are allocated
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W8/00—Network data management
    • H04W8/22—Processing or transfer of terminal data, e.g. status or physical capabilities
    • H04W8/24—Transfer of terminal data
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0621—Feedback content
    • H04B7/063—Parameters other than those covered in groups H04B7/0623 - H04B7/0634, e.g. channel matrix rank or transmit mode selection
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0636—Feedback format
    • H04B7/0639—Using selective indices, e.g. of a codebook, e.g. pre-distortion matrix index [PMI] or for beam selection

Definitions

  • the embodiments of the present disclosure relate to the field of communications, and in particular, to an information transmission method and device, a storage medium, and an electronic device.
  • APs low-cost access points
  • UEs user equipment
  • a large number of distributed APs can provide strong space division multiplexing capabilities, that is, the correlation between the airspace channels of different UEs to a large number of distributed APs will be relatively low. Therefore, the Cell-free system can support multiple UEs to communicate at the same frequency at the same time in a simple and efficient way.
  • the Cell-free system that deploys a large number of distributed APs is essentially an extremely large aperture antenna array (ELAA).
  • the cell-free network contains many access nodes AP.
  • a circle in Figure 1-2 represents an access node. Each node can have one or more transceiver antennas. These access nodes are usually deployed in a distributed manner and connected to the central processing unit (CPU) through a certain connection method (topology).
  • CPU central processing unit
  • FIG 1 shows that M access nodes are connected to a CPU through a radio stripe front haul.
  • Figure 2 shows that part of the M access nodes are connected to a CPU through a radio stripe front haul, and the other part is connected to the CPU through another radio stripe front haul.
  • FIG. 1 is an example of uplink multi-user transmission.
  • K UEs transmit data to the cell-free network, and there are M APs in the cell-free network connected to the CPU through a radio stripe front haul.
  • each AP has only one receiving antenna.
  • the wireless channels experienced by the L symbols transmitted by each user are the same, and the channels experienced by the symbols of different users are independent, the L data symbols received by APm are:
  • ym [ ym, 1 , ym, 2 , ... ym, L ] is a vector consisting of L data symbols received by APm, which is an L-length row vector
  • sk [ sk, 1 , sk, 2 , ... sk, L ] is a vector consisting of L data symbols transmitted by UEk, which is a row vector
  • hmk is the wireless channel from UEk to APm, which is a scalar
  • nm is the additive white Gaussian noise (AWGN) on APm, which is also an L-length row vector.
  • AWGN additive white Gaussian noise
  • the AWGN noise N is an M*L matrix.
  • a conjugate merging method is usually used: that is, APm estimates the wireless channel h mk from UEk to APm through the reference signal of UEk, and then uses the conjugate of h mk , that is, To weight the received data symbol y m , we get the data symbol related to user k Then the data symbol related to user k transmitted by the previous AP (i.e. APm-1) Adding up, that is get Then the accumulated signal is transmitted to the next AP (i.e. APm+1), and so on.
  • the data symbol related to user k transmitted by the Mth AP to the CPU is CPU where user k related signals It can also be written as in It is the conjugate transpose of the h k vector.
  • the processing of each AP is relatively simple: firstly, the user's channel is estimated according to the pilot signal, and the spatial MRC combining of the user's data symbols can be realized by a simple multiplication and accumulation operation according to the channels of different users, and then the spatial MRC combined data symbol streams of each user are transmitted to the next AP.
  • the front haul only needs to transmit the MRC combined data symbol stream of K users, and does not need to transmit the received data symbol stream of M APs. Since the number of APs M in the cell-free system is usually much larger than the number of UEs M, the above-mentioned MRC reception method based on conjugate combining can greatly reduce the bandwidth requirement of the front haul.
  • the Cell-free system based on the striped fronthaul architecture can efficiently support multiple UEs in spatial division multiplexing with very simple AP implementation and smaller fronthaul bandwidth, thus achieving low-cost deployment.
  • the mutual interference between different UEs can be relatively small, and the UE is usually close to the AP, so even under multi-user multiplexing, after spatial reception, the signal-to-interference plus noise ratio (SINR) of the UE data symbol is still relatively high, so multiple spatial division multiplexing UEs have the potential to achieve high spectral efficiency communication.
  • SINR signal-to-interference plus noise ratio
  • the ultra-large aperture antenna array based on the striped fronthaul architecture and the cell-free system based on the striped fronthaul are very similar, and the above description also applies to the ultra-large aperture antenna array based on the striped fronthaul architecture.
  • the cell-free system has strong spatial multi-user multiplexing capabilities, when facing massive connection scenarios, the capabilities of the cell-free system will be severely limited by the pilot signal.
  • the embodiments of the present disclosure provide an information transmission method and device, a storage medium, and an electronic device to at least solve the problem in the related art that there is no suitable pilot for use in a non-cell system.
  • an information transmission method which is applied to a terminal, and includes: determining W extremely sparse pilots, where W is an integer greater than 0; and transmitting the W extremely sparse pilots and target information to a cell-free system.
  • an information transmission device including: a determination module, configured to determine W extremely sparse pilots, where W is an integer greater than 0; and a transmission module, configured to transmit the W extremely sparse pilots and target information to a cell-free system.
  • a computer-readable storage medium in which a computer program is stored, wherein the computer program is configured to execute the steps of any one of the above method embodiments when running.
  • an electronic device including a memory and a processor, wherein the memory stores a computer program, and the processor is configured to run the computer program to execute the steps in any one of the above method embodiments.
  • FIG1 is a schematic diagram of the architecture of a cell-free system in the related art
  • FIG2 is another schematic diagram of the architecture of a cell-free system in the related art
  • FIG3 is a hardware structure block diagram of a terminal of an information transmission method according to an embodiment of the present disclosure
  • FIG4 is a flow chart of an information transmission method according to an embodiment of the present disclosure.
  • FIG5 is a schematic diagram of an implementation of defining a physical resource block according to an optional embodiment of the present disclosure
  • FIG6 is another schematic diagram of an implementation of defining a physical resource block according to an optional embodiment of the present disclosure.
  • FIG7 is a schematic diagram of another implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure.
  • FIG8 is a schematic diagram of an implementation of defining a demodulation reference signal using an OCC code according to an optional embodiment of the present disclosure
  • FIG9 is a schematic diagram of another implementation of defining a demodulation reference signal using an OCC code according to an optional embodiment of the present disclosure
  • FIG10 is a schematic diagram of implementing another demodulation reference signal using an OCC code according to an optional embodiment of the present disclosure
  • FIG11 is a schematic diagram of an implementation based on PRB transmission according to an optional embodiment of the present disclosure.
  • FIG12 is a schematic diagram of an implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure
  • FIG13 is a schematic diagram of yet another implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure
  • FIG14 is a schematic diagram of another implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure.
  • FIG15 is a schematic diagram of another implementation of defining a reference signal according to an optional embodiment of the present disclosure.
  • FIG16 is a schematic diagram (I) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure
  • FIG17 is a schematic diagram (II) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure
  • FIG18 is a schematic diagram of an implementation of generating a DMRS port according to an optional embodiment of the present disclosure
  • FIG19 is a schematic diagram (III) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure
  • FIG20 is a schematic diagram (IV) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure
  • FIG21 is a schematic diagram of an implementation method of an information transmission method provided according to an optional embodiment of the present disclosure.
  • FIG22 is a schematic diagram of an implementation of a constellation diagram provided according to an optional embodiment of the present disclosure.
  • FIG23 is a schematic diagram of an implementation of a PAM constellation diagram provided according to an optional embodiment of the present disclosure.
  • FIG24 is a schematic diagram of another implementation of a PAM constellation diagram provided according to an optional embodiment of the present disclosure.
  • FIG25 is a schematic diagram of implementing a cross-shaped constellation diagram according to an optional embodiment of the present disclosure.
  • FIG26 is a schematic diagram of another implementation of a cross-shaped constellation diagram according to an optional embodiment of the present disclosure.
  • FIG27 is a schematic diagram of an implementation of a rotated cross-shaped constellation diagram according to an optional embodiment of the present disclosure
  • FIG28 is a schematic diagram of an implementation of a rotated cross constellation diagram processed by AGWN according to an optional embodiment of the present disclosure
  • FIG29 is a schematic diagram of another implementation of a rotated cross constellation diagram processed by AGWN according to an optional embodiment of the present disclosure
  • FIG30 is a schematic diagram of implementing a partition according to an optional embodiment of the present disclosure.
  • FIG31 is a schematic diagram of another partition implementation provided according to an optional embodiment of the present disclosure.
  • FIG32 is a schematic diagram of a constellation after rotation and scaling according to an optional embodiment of the present disclosure.
  • FIG33 is a schematic diagram of another constellation after rotation and scaling according to an optional embodiment of the present disclosure.
  • FIG34 is a schematic diagram of another constellation after rotation and scaling according to an optional embodiment of the present disclosure.
  • FIG. 35 is a structural block diagram of an information transmission device according to an embodiment of the present disclosure.
  • FIG3 is a hardware structure block diagram of a terminal of an information transmission method of an embodiment of the present disclosure.
  • the terminal may include one or more (only one is shown in FIG3) processors 102 (the processor 102 may include but is not limited to a processing device such as a microprocessor MCU or a programmable logic device FPGA) and a memory 104 for storing data, wherein the terminal may also include a transmission device 106 and an input/output device 108 for communication functions.
  • the structure shown in FIG3 is only for illustration and does not limit the structure of the terminal.
  • the terminal may also include more or fewer components than those shown in FIG3, or have a configuration different from that shown in FIG3.
  • the memory 104 can be used to store computer programs, for example, software programs and modules of application software, such as the computer program corresponding to the information transmission method in the embodiment of the present invention.
  • the processor 102 executes various functional applications and data processing by running the computer program stored in the memory 104, that is, to implement the above method.
  • the memory 104 may include a high-speed random access memory, and may also include a non-volatile memory, such as one or more magnetic storage devices, flash memory, or other non-volatile solid-state memory.
  • the memory 104 may further include a memory remotely arranged relative to the processor 102, and these remote memories may be connected to the terminal via a network. Examples of the above-mentioned network include, but are not limited to, the Internet, an intranet, a local area network, a mobile communication network, and combinations thereof.
  • the transmission device 106 is used to receive or send data via a network.
  • the specific example of the above network may include a wireless network provided by the communication provider of the terminal.
  • the transmission device 106 includes a network adapter (Network Interface Controller, referred to as NIC), which can be connected to other network devices through a base station so as to communicate with the Internet.
  • the transmission device 106 can be a radio frequency (Radio Frequency, referred to as RF) module, which is used to communicate with the Internet wirelessly.
  • RF Radio Frequency
  • FIG. 4 is a flow chart of the information transmission method according to an embodiment of the present disclosure. As shown in FIG. 4 , the flow chart includes the following steps:
  • Step S402 determining W extremely sparse pilots, where W is an integer greater than 0;
  • Step S404 Transmit the W extremely sparse pilot signals and target information to a cell-free system.
  • the method also includes: the target information includes at least one of the following: UE_ID information (UE_ID is also UE identification), UE type information, UE capability information, the number of UE transceiver antennas, the number of transmission data streams supported by the UE, scheduling request (Scheduling Request, referred to as SR), buffer status report (Buffer Status Report, referred to as BSR), UE location information, one or more AP_ID information (AP_ID is also AP identification), one or more AP to terminal channel state information (Channel State Information, referred to as CSI).
  • UE_ID information UE_ID is also UE identification
  • UE type information UE type information
  • UE capability information the number of UE transceiver antennas
  • BSR buffer Status Report
  • UE location information one or more AP_ID information (AP_ID is also AP identification)
  • AP_ID is also AP identification
  • CSI Channel State Information
  • the channel state information when the target information includes the channel state information, includes at least one of the following: a precoding matrix indication; a channel quality indication; a rank indication; an SSB resource indication; and a reference signal power.
  • this information can cooperate with the cell-free system to better access, schedule, multi-user pairing, paging, UE mobility management, etc., and is also beneficial to the cell-free system for perception and other applications.
  • extremely sparse pilot plus information containing UE_ID that is, extremely sparse pilot plus information containing UE_ID is transmitted together to a system without a cell, which can be used for random access, that is, "extremely sparse pilot plus information containing UE_ID" can be used as Msg1 of a random access channel (RACH or PRACH).
  • RACH random access channel
  • the existing random access Msg1 is based on the Zadoff-Chu (ZC) sequence: if it is a 4-step RACH, then Msg1 only contains a ZC sequence; if it is a 2-step RACH, then Msg1 contains a ZC sequence and a data packet.
  • ZC Zadoff-Chu
  • the AP needs to increase the processing complexity, which will increase the cost and power consumption of the AP.
  • the AP does not process Msg1, but transmits Msg1 to the CPU through the radio stripe front haul, the data of all APs needs to be transmitted to the CPU separately.
  • the radio stripe front haul needs to transmit M Msg1 information. If the number of APs M is large, the transmission of Msg1 alone will occupy a large bandwidth of the radio stripe front haul.
  • the transmission of a large number of APs' Msg1 back to the CPU requires the CPU to process all Msg1 in a short time, which is also a heavy burden for the CPU.
  • the AP can continue to use the original simple channel estimation and spatial MRC combining operations to maintain the simple implementation and low power consumption of the AP; the radio stripe front haul does not need to increase too much bandwidth; and the CPU does not need to increase too much processing complexity for Msg1.
  • the extremely sparse pilot plus the information containing UE_ID can also be used as a "heartbeat signal" sent by the UE in the Cell-free system.
  • the cell-free system is assisted to more easily implement AP energy saving, UE mobility management, pilot allocation, paging and other functions.
  • the extremely sparse pilot plus the information containing UE_ID can also be used as the scheduling request sent by the UE in the Cell-free system, which can simplify the implementation of multi-user scheduling.
  • extremely sparse pilots plus UE capability information may be used for the system to perform transmissions with the UE that match the UE capability.
  • extremely sparse pilot plus information including UE_ID and BSR can realize UE uplink transmission with low signaling overhead and low latency.
  • the terminal can directly transmit "extremely sparse pilot plus information including UE_ID and BSR" to the system, so that after receiving it, the non-cell system can directly indicate an uplink transmission resource to the UE, allowing the UE to transmit its data.
  • extremely sparse pilots plus UE location information can assist the system in implementing AP energy saving, UE mobility management, pilot allocation, paging, sensing and other functions.
  • extremely sparse pilots plus one or more AP_ID information can assist the system in implementing AP energy saving, UE mobility management, pilot allocation, paging, sensing and other functions.
  • extremely sparse pilot signals plus one or more AP-to-terminal channel state information can assist the system in achieving better multi-user scheduling, multi-user pairing, resource allocation, power allocation, beam management, switching management, paging and other functions.
  • CSI channel state information
  • the channel state information includes at least a pre-coding matrix indication (PMI); a channel quality indication (CQI); a rank indication (RI); an SSB resource indication (SSBRI); a reference signal power (Reference Signal Power, referred to as RSRP).
  • PMI pre-coding matrix indication
  • CQI channel quality indication
  • RI rank indication
  • SSBRI SSB resource indication
  • RSRP Reference Signal Power
  • the receiving end and the transmitting end respectively store a set of code books containing several precoding matrices, so that the receiving end can select a target precoding matrix from the code book according to the estimated channel matrix and the preset criteria, and feed back the index value of the target precoding matrix and the quantized channel state information (i.e., channel state quantization information) to the transmitting end.
  • MIMO multiple-input multiple-output
  • the transmitting end adopts a new precoding matrix and determines the coding and modulation mode for the codeword according to the channel state quantization information fed back by the receiving end;
  • the channel quality indication refers to the index value of the channel quality corresponding to the condition of meeting a certain performance, such as the block error rate (BLER) index of 10%.
  • the index value includes information such as the current modulation mode, coding rate and efficiency of the channel.
  • the channel quality indication (CQI) is the channel quality index value corresponding to the channel quality index value corresponding to the condition of meeting a certain performance, such as the block error rate (BLER) index of 10%.
  • the channel quality indication is the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index value corresponding to the channel quality index The larger the index of CQI (Critical Quality Indicator), the higher the coding efficiency.
  • the RANK in the RANK indication is the rank in the antenna matrix in the MIMO scheme, indicating the number of parallel valid data streams.
  • the SSB resource indication can indicate the beam index and can be used for beam management.
  • (Synchronization Signal and PBCH block, SSB for short) refers to the synchronization signal and physical broadcast channel (PBCH for short) block.
  • SSB consists of three parts: primary synchronization signal (PSS for short), secondary synchronization signal (SSS for short) and PBCH block.
  • the method also includes: among the W extremely sparse pilots, only U symbols in each extremely sparse pilot are non-zero values, and the U non-zero values are carried on U adjacent resource units in time and frequency, or carried on U symbols that are successive in time, or carried on U resource units on adjacent subcarriers in the frequency domain, where U is greater than 0 and less than 5.
  • the method further includes: in the W extremely sparse pilots, the length of each pilot is greater than 24.
  • Other situations are similar, and the embodiments of the present disclosure will not be repeated.
  • the method further includes: when W is greater than 1, the W extremely sparse pilots are independent and unrelated.
  • the method further includes: the W extremely sparse pilots are determined by information in a transmitted data packet.
  • the method further includes: the W extremely sparse pilots are determined by one or more bits in a transmitted data packet.
  • each extremely sparse pilot comes from a pilot set including D extremely sparse pilots, and each extremely sparse pilot is determined from the pilot set using log2(D) bits in the transmitted data packet.
  • the value of W is 2 or 1.
  • the terminal When the terminal has no data transmission, in order to save power, it usually does not have a connection with the system all the time, that is, it is not connected to the system, that is, it is disconnected, that is, the terminal can be said to be in a non-connected state (specifically including: Non connected state, Non RRC connected state, Connectionless state, Connection-free state, Disconnected state).
  • the above-mentioned non-connected state can also be understood as an idle state (Idle state) or an inactive state (Inactive state).
  • the terminal When the terminal is originally in a non-connected state, that is, it has not yet entered the connected state, if the traditional uplink data transmission scheme is used, in order to transmit information, the terminal must first establish a connection with the system before transmission.
  • the terminal After entering the connected state (also called the active state), the terminal can further apply for uplink transmission resources from the system; after obtaining the system's resource authorization, it can actually perform data transmission. It can be seen that in order to complete a traditional uplink data transmission, the terminal needs to complete many operations in advance, which will undoubtedly increase the power consumption of the terminal and increase the signaling overhead of the system.
  • connectionless data transmission the terminal does not need to establish a connection before data transmission, nor does it need to apply for dedicated transmission resources from the system; instead, the terminal in the connectionless state is allowed to independently decide on transmission without notifying the system before transmission, and directly transmit data to the system on a preset public transmission resource. Therefore, connectionless data transmission can achieve extremely simplified data transmission, reduce transmission power consumption and delay, and save the signaling overhead required for transmission, and the advantages are very obvious.
  • the pilot/reference signal is also selected by the user autonomously from the pilot set, so different users may select the same reference signal, that is, the reference signal collides.
  • the pilot and the reference signal are equivalent. If the number of pilots or reference signals is limited, and the user load is relatively high, that is, when there are many users, the probability of a pilot/reference signal collision is very high. Once the reference signals collide, it is difficult for the CPU and the AP access point to separate the two users through the reference signal.
  • independent multi-pilot technology In order to reduce the collision of pilots, independent multi-pilot technology can be used. Independent multi-pilot technology means that two or more pilots are included in one transmission, and the pilots are independent, unrelated, or uncorrelated. In this way, under the same pilot overhead, the probability of simultaneous collision of independent multi-pilots of different terminals will be much smaller than that of a single pilot.
  • the CPU can decode the corresponding terminal's data packet through those non-colliding pilots in each round through an iterative receiver, and then reconstruct both the pilot and the data according to the pilot-related information contained in the data packet and eliminate them from the received signal, and iterate until all decodable terminal data packets are decoded. Since the probability of simultaneous collision of independent multi-pilots is much smaller than that of a single pilot, the transmission scheme using independent multi-pilots can support high terminal loads in the case of connectionless transmission.
  • each pilot needs to have a signal in the entire transmission bandwidth and time.
  • each pilot cannot be too sparse in the entire transmission bandwidth and time, and must have a certain density, so that the wireless multipath channel (that is, frequency selective channel) in the entire transmission bandwidth and frequency deviation in the transmission time can be estimated. Therefore, to ensure the transmission performance in the disconnected state, the relevant pilot scheme is used, and the overhead occupied by the pilot will increase significantly, and the detection complexity will also increase significantly.
  • the sparse pilot scheme can significantly increase the number of pilots without increasing the pilot resource overhead, thereby significantly reducing the probability of pilot collision.
  • the CPU can alleviate the pressure of sparse pilots by extracting channel information from data symbols, that is, only partial information of the wireless channel is required to be estimated from the sparse pilots, without estimating all the information of the wireless channel from the sparse pilots.
  • independent multi-pilot technology refers to a transmission containing 2 or more pilots, and the pilots are unrelated/independent. In this way, under the same pilot overhead, the probability of W independent pilots of different users colliding at the same time will be much smaller than that of a single pilot.
  • the CPU can use an iterative receiver to solve the corresponding user through those pilots that have not collided in each round, and then reconstruct its data and pilots and eliminate them from the received signal, so iterate until all solvable users are solved. Since the probability of independent multi-pilots colliding at the same time is much smaller than that of a single pilot, the transmission scheme using independent multi-pilots can support very high user loads in the case of competitive connectionless state transmission (or competitive scheduling-free transmission). In this embodiment, independent multi-pilot technology and sparse pilot technology can be combined, that is, multiple independent and irrelevant sparse pilots are used to further reduce the situation of user pilot collisions and further improve user load.
  • the information is information in a broad sense, which can be business data or data used for system control, namely signaling.
  • the bits that need to be transmitted whether they are business data bits or signaling bits, can be understood as information in the embodiment of the present disclosure.
  • the information that needs to be transmitted is also data.
  • Different English expressions: message, information, payload, are all within the protection scope of the embodiments of the present disclosure.
  • a demodulation reference signal (DMRS) set is defined, which includes 12 reference signals.
  • a demodulation reference signal can also be called a demodulation reference signal port (DMRS ports), that is, a set of 12 demodulation reference signal ports (DMRS ports) is defined.
  • FIG5 is a schematic diagram of an implementation of defining a physical resource block according to an optional embodiment of the present disclosure.
  • a defined physical resource block includes 14 orthogonal frequency division multiplexing (OFDM) (or discrete Fourier transform-spread-Orthogonal frequency division multiplexing (DFT-S-OFDM) or single-carrier frequency division multiple access (SC-FDMA)) symbols in the time domain and 12 subcarriers in the frequency domain.
  • OFDM orthogonal frequency division multiplexing
  • DFT-S-OFDM discrete Fourier transform-spread-Orthogonal frequency division multiplexing
  • SC-FDMA single-carrier frequency division multiple access
  • RE resource element
  • one resource unit can carry one symbol.
  • U symbols are carried on adjacent REs, it can also be said that these U symbols are carried on adjacent time-frequency resource symbols. Or conversely, if U symbols are carried on adjacent time-frequency resource symbols, for OFDM, it is equivalent to these U symbols being carried on adjacent REs.
  • the demodulation reference signal uses the first two OFDM symbols to carry the demodulation reference signal, that is, the first two OFDM symbols are used as the reference signal area, which means that the resource overhead occupied by the demodulation reference signal is 1/7.
  • the area outside the reference signal area is the data symbol area.
  • FIG5 is a schematic diagram of an implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure.
  • the demodulation reference signal can be divided into three groups from the perspective of the position of the occupied resource unit (RE). In FIG6, from left to right, they are the first group, the second group and the third group.
  • the non-zero symbols (or non-zero signals, useful signals, etc.) of the first group of demodulation reference signals (DMRS) (i.e., the symbols are non-zero values) are carried on the resource units (RE) of the pattern shown in the figure, and the first group of 4 DMRS ports are distinguished by OCC codes;
  • the non-zero symbols of the second group of demodulation reference signals (DMRS) are carried on the resource units (RE) of the pattern shown in the figure, and the second group of 4 DMRS ports are distinguished by OCC codes;
  • the non-zero symbols of the third group of demodulation reference signals (DMRS) are carried on the resource units (RE) of the pattern shown in the figure, and the third group of 4 DMRS ports are distinguished by OCC codes.
  • Each demodulation reference signal takes the value of 0 on the resource unit (RE) of the blank unfilled pattern as shown in the figure, or there is no signal.
  • RE resource unit
  • DMRS reference signal
  • FIG. 7 is a schematic diagram of another implementation of defining demodulation reference signals provided according to an optional embodiment of the present disclosure.
  • Fig. 8 is a schematic diagram of an implementation of defining a demodulation reference signal using an OCC code according to an optional embodiment of the present disclosure. As shown in Fig. 8, for the four demodulation reference signals in the first group in Fig. 4, four demodulation reference signal ports are separated by jointly using two long OCC codes [1, 1], [1, -1] in the time domain and two long OCC codes [1, 1], [1, -1] in the frequency domain.
  • Fig. 9 is a schematic diagram of another implementation of defining a demodulation reference signal using an OCC code according to an optional embodiment of the present disclosure. As shown in Fig. 9, for the four demodulation reference signals in the second group in Fig. 5, four demodulation reference signal ports are separated by jointly using two long OCC codes [1, 1], [1, -1] in the time domain and two long OCC codes [1, 1], [1, -1] in the frequency domain.
  • Fig. 10 is a schematic diagram of another implementation of a demodulation reference signal using an OCC code according to an optional embodiment of the present disclosure.
  • 8 represents the first reference signal unit
  • 9 represents the second reference signal unit; for the four demodulation reference signals in the third group in Fig. 5, four demodulation reference signal ports are separated by jointly using two long OCC codes [1, 1], [1, -1] in the time domain and two long OCC codes [1, 1], [1, -1] in the frequency domain.
  • a reference signal carried on several resource elements (REs) adjacent in the time and frequency domains may be referred to as a reference signal element (RSE for short), and a reference signal carried on several symbols sequentially in time may also be referred to as a reference signal element.
  • RSE reference signal element
  • a reference signal carried on four consecutive resource elements (REs) in the time and frequency domains is referred to as a reference signal element (RSE).
  • RSE reference signal element
  • a reference signal element has another characteristic: when applying the reference signal for channel estimation, each reference signal element (RSE) can estimate a channel value.
  • each reference signal has 2 reference signal elements (RSE) within 1 PRB bandwidth, so a channel value at 2 within 1 PRB bandwidth (that is, within 12 subcarrier bandwidth) can be estimated.
  • RSE reference signal elements
  • the channel values of 12 subcarriers within 1 PRB bandwidth need to be obtained by interpolation of these reference signal element estimation values.
  • Figure 11 is a schematic diagram of an implementation based on PRB transmission provided according to an optional embodiment of the present disclosure.
  • each reference signal has 2*X reference signal elements (RSE), which can estimate the channel values at 2*X equally spaced locations within the entire transmission bandwidth, and then interpolate to obtain the channel values of all 12*X subcarriers within the transmission bandwidth.
  • RSE 2*X reference signal elements
  • the 12 demodulation reference signals can be divided into three groups based on the location of occupied resource elements (REs).
  • Fig. 12 is a schematic diagram of an implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure. As shown in Fig. 12, four demodulation reference signals of the first group are distinguished by OCC codes.
  • Fig. 13 is a schematic diagram of another implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure. As shown in Fig. 13, four demodulation reference signals of the second group are distinguished by OCC codes.
  • Fig. 14 is a schematic diagram of another implementation of defining a demodulation reference signal according to an optional embodiment of the present disclosure. As shown in Fig. 14, four demodulation reference signals of the third group are distinguished by OCC codes.
  • the overhead of the reference signal is 1/7, that is, the system pays 1/7 of the resources and can only design 12 demodulation reference signals.
  • the collision probability of any two terminals autonomously selecting reference signals is 1/12, which is still very large. Therefore, the demodulation reference signal will severely limit the number of terminals transmitting data in the connectionless transmission state.
  • the reference signal also needs to estimate a certain frequency offset (Frequency Offset)
  • the resources occupied by each reference signal need to be further increased, or the density of each reference signal in the transmission signal needs to be further encrypted. For example, repeat it once in the time domain to estimate the frequency offset. In this way, the resources occupied by the reference signal double, that is, the overhead is 2/7.
  • the system pays 2/7 of the resources, and in order to estimate the frequency-selective channel and frequency offset, it can only design 12 demodulation reference signals. If further, the system also needs to deal with a certain timing offset (Timing Offset), the resources occupied by the reference signal need to be further increased, for example, 3/7 or even 4/7 of the overhead is required to design 12 demodulation reference signals. With such a large overhead, only such a small number of reference signal sets (or such a small number of reference signal ports) can be obtained, and the probability of collision in transmission without connection is very high.
  • Timing Offset Timing Offset
  • each demodulation reference signal has 3 reference signal units in each PRB bandwidth (such as 3 grids in a figurative sense), so that each PRB can have 3 estimated values, and X PRBs have 3*X estimated values, and then the channels of all subcarriers of X PRBs are obtained by linear interpolation.
  • This reference signal still accounts for 1/7 of the transmission resource overhead, but only 8 demodulation reference signals (8 demodulation reference signal ports) can be separated, which is less than the definition above. It can be seen that the channel estimation capability is usually inversely proportional to the number of reference signals.
  • reference signals are needed to estimate the frequency selection channel and time-frequency offset of the entire transmission channel, and reference signals are also needed to identify terminal users, so reference signals need to occupy more time-frequency resources to complete such heavy tasks. This leads to a serious shortage of reference signals under certain resources.
  • the number of terminals that can be supported by connectionless transmission is limited by the number of reference signals.
  • the tasks of reference signals can be greatly reduced, so the resources occupied by each reference signal can be minimized, or each reference signal can be as sparse as possible, so that the number of reference signals can be maximized, and ultimately connectionless transmission can support more terminals.
  • the embodiments of the present disclosure use data-based channel estimation technology (rather than reference signal-based) to estimate the channel of the entire transmission bandwidth and the time-frequency offset through the characteristics of the data itself, such as the geometric characteristics of the constellation diagram of the data symbol.
  • data-based channel estimation technology rather than reference signal-based
  • a block flat fading channel is taken as an example.
  • the partition matching method introduced later can be applied to estimate the channel.
  • the task of the reference signal is much smaller than that of the related scheme, so each reference signal occupies much less resources than that of the related scheme. Therefore, under a certain overhead, the number of reference signals is much greater than that of the related scheme.
  • an "extremely sparse" reference signal can be used to estimate the spatial channels experienced by each terminal signal, and then use these estimated spatial channels to perform spatial merging of the received signal.
  • the receiver uses the spatially merged data symbol sk to estimate the channel of the entire transmission bandwidth experienced by the signal of terminal k and to estimate the time-frequency offset.
  • the data symbol sk after spatial merging is then compensated for the channel and time-frequency offset.
  • the data symbol that compensates for the channel and time-frequency offset is demodulated and decoded.
  • Figure 15 is a schematic diagram of another implementation of defining a reference signal provided according to an optional embodiment of the present disclosure. As shown in Figure 15, the reference signal proposed in the embodiment of the present disclosure occupies 1 OFDM symbol.
  • a transmission contains X PRBs of time-frequency resources.
  • a physical resource block (PRB) contains 14 OFDM (or DFT-S-OFDM or SC-FDMA) symbols in the time domain and 12 subcarriers in the frequency domain.
  • the first OFDM symbol is used to carry the demodulation reference signal, that is, the first OFDM symbol is used as an extremely sparse pilot area, and 1/14 of the resources are used to transmit the reference signal, that is, 12*X resource units (REs) are used to transmit the reference signal.
  • the area other than the extremely sparse pilot area is the data symbol area.
  • Figure 16 is a schematic diagram (I) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure. As shown in Figure 16, each reference signal defined by the system has a non-zero symbol (non-zero signal, or useful signal) only on one RE resource unit, and there is no signal in the rest of the places (or the values of the rest of the places are 0).
  • FIG 17 is a schematic diagram (II) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure.
  • each reference signal defined by the system has non-zero symbols (non-zero signals, or useful signals) only on 2 RE resource units, and 2 reference signals are separated from every 2 REs through 2-length OCCs, and there is no signal in the rest of the places (or the values of other places are all 0).
  • the reference signal area that occupies 1/14 of the overhead can also separate a total of 12*X reference signals.
  • the number of extremely sparse pilots is proportional to the number of PRBs.
  • FIG 18 is a schematic diagram of an implementation of generating a DMRS port according to an optional embodiment of the present disclosure.
  • different OCC codes such as OCC code 1, i.e., [1, 1], OCC code 2, i.e., [1, -1]
  • OCC code 1 i.e., [1, 1]
  • OCC code 2 i.e., [1, -1]
  • Figure 19 is a schematic diagram (three) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure. As shown in Figure 19, the reference signal defined by the system occupies 2 OFDM symbols.
  • Figure 20 is a schematic diagram (four) of an implementation of defining a reference signal according to an optional embodiment of the present disclosure. As shown in Figure 20, each reference signal defined by the system has non-zero symbols (non-zero signals, or useful signals) only on a group of 4 adjacent RE resource units in time and frequency, but there will be 4 reference signals multiplexing a group of 4 adjacent REs. The 4 reference signals multiplexing the same group of 4 adjacent REs are distinguished by OCC codes.
  • the reference signal area that occupies 1/7 of the overhead can be divided into a total of 24*X reference signals.
  • the numerical values shown in the embodiments of the present disclosure are only exemplary descriptions and are not specifically limited.
  • the values can be adaptively adjusted according to actual conditions. It can be seen that sparse pilots actually mean that there are very few non-zero elements in each pilot in the pilot set, for example, there are only 1-4 non-zero elements, and the non-zero elements of each pilot in the pilot set are concentratedly distributed on the time-frequency resources, that is, they do not need to be spread or dispersed in the transmitted time-frequency resources. In this way, the number of pilots can be significantly increased without increasing the pilot resource overhead, thereby significantly reducing the probability of pilot collision.
  • the CPU estimates part of the information of the wireless channel from the sparse pilots, without estimating all the information of the wireless channel from the sparse pilots.
  • the CPU will further extract channel information from the data symbols, and then use this channel information to complete the equalization of the data symbols.
  • this pilot signal is only used for spatial combining, but is usually not used for equalization of all transmission channels. It can be considered as a spatial combining reference signal.
  • the extremely sparse reference signals shown in FIGS. 15-18 are all located in front of the transmission resource by 1 or 2 symbols, the embodiments of the present disclosure do not limit the location of the extremely sparse reference signal.
  • the extremely sparse reference signal may also be located in the middle symbol of the transmission resource.
  • multiple extremely sparse pilots can also be applied to further reduce the situation of terminal pilot collision and further improve the terminal load. That is, multiple extremely sparse pilots are included in one transmission, and the extremely sparse pilots are unrelated/independent. In this way, under the same pilot overhead, the probability of multiple independent pilots of different users colliding at the same time will be much smaller than that of a single pilot.
  • the CPU can use an iterative receiver to solve the corresponding user through those pilots without collision in each round, and then reconstruct its data and pilots and eliminate them from the received signal, and iterate until all solvable users are solved. Since the probability of independent multi-pilots colliding at the same time is much smaller than that of a single pilot, the transmission scheme using independent multi-pilots can support very high user loads in the case of competitive connectionless state transmission (or competitive scheduling-free transmission).
  • Figure 21 is a schematic diagram of an implementation of an information transmission method provided according to an optional embodiment of the present disclosure.
  • W extremely sparse reference signals are included in one transmission, and the data packet includes information about the W extremely sparse reference signals, such as the index number (index in the pilot set) of the W extremely sparse reference signals.
  • the information of all extremely sparse pilots used by the terminal in this transmission can be known, so that interference elimination of the pilot signal can be performed.
  • the embodiments of the present disclosure provide the following implementation scheme.
  • BPSK and QPSK modulation modes have relatively low spectral efficiency, their constellation diagrams are very simple and are not very sensitive to channel distortion. Therefore, the partition matching method introduced later can be easily applied to estimate the channel. Therefore, BPSK and QPSK can be used in scenarios with limited pilot capacity.
  • the spectral efficiency can be improved by increasing the order of the modulation method.
  • Traditional high-order modulation methods such as 16QAM, 32QAM, 64QAM, 256QAM and other digital amplitude and phase modulation methods, have constellations that are basically evenly distributed on the two-dimensional plane/complex plane, so the two-dimensional signal space of the complex signal (that is, the two-dimensional signal plane) can be more fully utilized.
  • Communication signals can usually be represented by complex numbers at the baseband, usually the I-channel signal is the real part and the Q-channel signal is the imaginary part.
  • Modulation symbols can also usually be represented by complex numbers, that is, a modulation symbol can be represented by a complex number.
  • the traditional 16QAM, its constellation diagram contains 16 points, and these 16 points are represented as complex numbers respectively: 3+3j, 3+j, 3-j, 3-3j, 1+3j, 1+j, 1-j, 1-3j, -1+3j, -1+j, -1-j, -1-3j, -3+3j, -3+j, -3-j, -3-3j.
  • the 16QAM constellation points are relatively evenly distributed.
  • the complex plane and the two-dimensional plane are equivalent, so the complex plane or the two-dimensional plane is sometimes also called the two-dimensional complex plane.
  • the real part of a complex number is equivalent to the x-coordinate of the two-dimensional plane, and the real part is equivalent to the y-coordinate of the two-dimensional plane. Therefore, complex numbers can also be represented by points on the two-dimensional plane, that is, a complex number a+j*b can be represented by a point with coordinates (a, b) on the two-dimensional plane.
  • the coordinates (a, b) indicate that the x-coordinate of the two-dimensional plane is a and the y-coordinate is b.
  • the 16 points in the 16QAM constellation diagram can also be represented by 16 coordinates on the two-dimensional plane, as follows: (3, 3), (3, 1), (3, -1), (3, -3), (1, 3), (1, 1), (1, -1), (1, -3), (-1, 3), (-1, 1), (-1, -1), (-1, -3), (-3, 3), (-3, 1), (-3, -1), (-3, -3).
  • the constellation diagram will also have a power normalization as a whole, that is, the whole will be multiplied by a normalization factor.
  • the 16 complex numbers of 16QAM will all be multiplied by the same normalization factor 1/sqrt(40).
  • the 16 points contained in the normalized 16QAM constellation diagram are expressed as complex numbers: 1/sqrt(40)*[3+3j, 3+j, 3-j, 3-3j, 1+3j, 1+j, 1-j, 1-3j, -1+3j, -1+j, -1-j, -1-3j, -3+3j, -3+j, -3-j, -3-3j].
  • the coordinates of the 16 points in the power-normalized 16QAM constellation are the coordinates obtained by multiplying the above 16 two-dimensional coordinates by 1/sqrt(40) (the x-coordinate and y-coordinate of each two-dimensional coordinate are multiplied by 1/sqrt(40)). Power normalization will only reduce the constellation as a whole, and the constellation points in the reduced constellation are still relatively evenly distributed.
  • the modulation symbols carried on the subcarrier After passing through the multipath channel, that is, the frequency-selective channel, the modulation symbols carried on the subcarrier will be weighted by a complex weight value by the channel, that is, the modulation symbols carried on the subcarrier will be distorted by the frequency-selective channel.
  • the timing deviation i.e., time offset
  • frequency deviation i.e., frequency offset
  • each small dot in the figure corresponds to a modulation symbol, where (a) of Figure 22 is the constellation corresponding to the standard 64QAM modulation; and (b) of Figure 22 is the constellation corresponding to the standard 64QAM modulation; (b) in FIG22 is the constellation corresponding to the 64QAM modulation symbol after a complex weight value (i.e., a rotation and scaling amount), that is, the constellation corresponding to the 64QAM modulation symbol after channel distortion.
  • a complex weight value i.e., a rotation and scaling amount
  • the application of the previous extremely sparse pilot scheme allows the system to support more users, and is therefore very suitable for large-connection scenarios, such as scenarios where a large number of users directly transmit data without connection, and scenarios where a large number of users transmit data based on SPS.
  • the extremely sparse pilot scheme requires the receiver to be able to perform channel estimation based on the characteristics of the data symbols themselves, and the constellation diagram of traditional high-order modulation is too dense, which is not conducive to the CPU extracting channel information through data symbols. Therefore, this patent proposes a modulation method that can support high spectral efficiency and allow the CPU or access point to more easily and accurately extract channel information through data symbols.
  • the modulation scheme of the disclosed embodiment may adopt the PAM constellation diagram shown in Figures 23-23 and the cross constellation diagram shown in Figures 25-25.
  • the so-called cross constellation diagram means that half of the constellation points are on a straight line passing through the zero point (origin), and the other half are on another straight line passing through the zero point (origin), and the two straight lines are perpendicular to each other.
  • Figures 24-25 show a 16-point cross constellation diagram in a two-dimensional signal plane, each constellation point corresponds to a modulation symbol, and each modulation symbol can carry 4 bits, that is, 4 bits will be mapped to (modulated to) a modulation symbol.
  • Figure 25 is a constellation diagram of constellation points on the x-axis (I path) and y-axis (Q path) respectively;
  • Figure 26 is a constellation diagram of constellation points on a 45° straight line passing through the origin and a 135° straight line passing through the origin.
  • the constellation diagram represented by Figure 26 can be obtained by rotating Figure 24 by 45°.
  • the PAM constellation diagram can also be regarded as a linear constellation diagram, and all constellation points are on a straight line passing through the zero point (origin).
  • each modulation symbol (that is, each constellation point) can carry multiple bits, 4 bits in Figures 23-25, which means that high-order modulation can be achieved, thereby achieving high spectral efficiency.
  • the linear constellation diagram and the cross constellation diagram corresponding to the modulation symbols have simple geometric shapes. Even if the modulation symbols received by the receiver are rotated and scaled by the channel, the constellation diagram corresponding to these modulation symbols is only a linear constellation diagram and a cross constellation diagram that have been rotated and scaled, and the geometric shape is still relatively simple. Because the linear constellation diagram is the simplest constellation diagram, the slightly more complex cross constellation diagram is used as an example below. The processing of the linear constellation diagram is usually simpler than that of the cross.
  • Figure 27 is the standard constellation diagram corresponding to the transmitted modulation symbol s
  • Figure 28 is the constellation diagram corresponding to the received modulation symbol h*s (that is, h multiplied by s, or it can also be expressed as h ⁇ s, hs) after rotation and scaling, and the rotation and scaling amount is the complex number h.
  • the constellation diagram of Figure 27 shows the constellation diagram corresponding to the received modulation symbol without AWGN.
  • Figure 29 is actually based on the constellation point of Figure 28 plus the complex number corresponding to AWGN, that is, the constellation point corresponding to the received modulation symbol h ⁇ s+n with AWGN will be around the constellation point h ⁇ s in Figure 28, according to the probability density distribution of AWGN.
  • the color changes from dark to light from the middle to the edge, which is the set of points formed by the modulation symbol corresponding to the center of the group being affected by AWGN.
  • the receiver can estimate the rotation and scaling amount of the constellation diagram using the geometric shape of the constellation diagram in FIG29, that is, to estimate h.
  • the present disclosure embodiment provides the following implementation scheme:
  • the two-dimensional plane or the two-dimensional signal plane is divided into four partitions.
  • two typical methods of dividing the two-dimensional signal plane into four partitions are:
  • the first type is to divide the partition into 4 quadrants, that is, the x-axis and y-axis are the partition lines, as shown in Figure 30.
  • the oblique line filling is partition 1
  • the fine dot filling is partition 2
  • the vertical line filling is partition 3
  • the brick-shaped filling is partition 4.
  • the second method is to rotate the four partitions of the first method by 45° to form the four partitions required, as shown in Figure 31. That is, the ray from the dot to 45° to the ray from the dot to 135° is partition 1, which is filled with oblique lines; the ray from the dot to 135° to the ray from the dot to 225° is partition 2, which is filled with fine dots; the ray from the dot to 225° to the ray from the dot to 315° is partition 3, which is filled with vertical lines; the ray from the dot to 315° to the ray from the dot to 45° is partition 4, which is filled with bricks.
  • FIG. 32 is a constellation diagram after the cross constellation diagram in Figure 27 is rotated and scaled. Taking the partition shown in Figure 30 as an example, after partitioning, the constellation points are divided into four parts, as shown in Figure 33, and then:
  • the rotation and scaling of the entire constellation diagram can be obtained through the centers of the constellation points of all partitions.
  • the centers of the four partitions calculated are c1, c2, c3, and c4, respectively, then:
  • the obtained complex number c can be used as an estimate of the rotation and scaling amount of the entire constellation diagram.
  • only two partitions can be used to calculate the rotation and scaling of the constellation diagram. For example, after the receiver divides the two-dimensional signal plane into two partitions through the x-axis, the constellation points in each partition (each constellation point corresponds to a modulation symbol) are added up, and then divided by the number of constellation points in the partition (i.e., the number of modulation symbols). The resulting constellation point is the center of the constellation point of the partition. Then, the rotation and scaling of the entire constellation diagram can be obtained through the centers of the constellation points of all partitions.
  • the complex number c can be used as a rotation and scaling value of the entire constellation diagram. estimate.
  • the two-dimensional signal plane is divided into two partitions
  • the two-dimensional signal plane is divided into two partitions
  • the receiver After the receiver estimates the rotation and scaling of the constellation diagram, it can balance the rotation and scaling experienced by the constellation diagram to obtain a constellation diagram without distortion and only affected by AWGN.
  • Cell-free network is an emerging mobile network form and an important technical direction for improving mobile communication experience in the future. It is receiving more and more attention.
  • the above embodiments of the present disclosure solve the performance problem of multi-user uplink transmission in cell-free network.
  • the technical solution of the present disclosure can be embodied in the form of a software product, which is stored in a storage medium (such as ROM/RAM, a disk, or an optical disk), and includes a number of instructions for enabling a second node device (which can be a mobile phone, a computer, a server, or a network device, etc.) to execute the methods described in each embodiment of the present disclosure.
  • a storage medium such as ROM/RAM, a disk, or an optical disk
  • an information transmission device is also provided, which is used to implement the above-mentioned embodiments and preferred implementation modes, and the descriptions that have been made will not be repeated.
  • the term "module” can implement a combination of software and/or hardware of a predetermined function.
  • the devices described in the following embodiments are preferably implemented in software, the implementation of hardware, or a combination of software and hardware, is also possible and conceivable.
  • FIG. 35 is a structural block diagram of an information transmission device according to an embodiment of the present disclosure. As shown in FIG. 35 , the device includes:
  • a determination module 340 is configured to determine W extremely sparse pilots, where W is an integer greater than 0;
  • the transmission module 342 is configured to transmit the W extremely sparse pilot signals and the target information to the cell-free system.
  • the target information includes at least one of the following: UE_ID information, UE type information, UE capability information, the number of transmitting and receiving antennas of the UE, the number of transmission data streams supported by the UE, one or more AP_ID information, scheduling request SR, cache status report BSR, and UE location information.
  • the channel state information when the target information includes the channel state information, includes at least one of the following: a precoding matrix indication; a channel quality indication; a rank indication; an SSB resource indication; and a reference signal power.
  • this information can cooperate with the cell-free system for better access, scheduling, paging, UE mobility management, etc., and is also beneficial to the cell-free system for perception and other applications.
  • extremely sparse pilot plus information containing UE_ID that is, extremely sparse pilot plus information containing UE_ID is transmitted together to a system without a cell, which can be used for random access, that is, "extremely sparse pilot plus information containing UE_ID" can be used as Msg1 of a random access channel (RACH or PRACH).
  • RACH random access channel
  • the existing random access Msg1 is based on the Zadoff-Chu (ZC) sequence: if it is a 4-step RACH, then Msg1 only contains a ZC sequence; if it is a 2-step RACH, then Msg1 contains a ZC sequence and a data packet.
  • ZC Zadoff-Chu
  • the AP needs to increase the processing complexity, which will increase the cost and power consumption of the AP.
  • the AP does not process Msg1, but transmits Msg1 to the CPU through the radio stripe front haul, the data of all APs needs to be transmitted to the CPU separately. That is, if there are M APs, the radio stripe front haul needs to transmit M Msg1 information. If the number of APs is large, the transmission of Msg1 occupies a large bandwidth of the radio stripe front haul. Moreover, the transmission of Msg1 from a large number of APs back to the CPU requires the CPU to process all Msg1 in a short time, which is also a heavy burden for the CPU.
  • the extremely sparse pilot in the embodiment of the present disclosure is added with the information containing UE_ID as Msg1 of the random access channel (RACH or PRACH), so that the AP can continue to use the original simple channel estimation and spatial MRC combining operations to keep the AP simple and low power consumption; the radio stripe front haul does not need to increase too much bandwidth, and the CPU does not need to increase too much processing complexity for Msg1.
  • the extremely sparse pilot plus the information containing UE_ID can also be used as a "heartbeat signal" sent by the UE in the Cell-free system.
  • the auxiliary system implements AP energy saving, UE mobility management, pilot allocation, paging and other functions.
  • extremely sparse pilots plus UE capability information may be used for the system to perform transmissions with the UE that match the UE capability.
  • extremely sparse pilot plus information including UE_ID and BSR can realize UE uplink transmission with low signaling overhead and low latency.
  • the terminal can directly transmit "extremely sparse pilot plus information including UE_ID and BSR" to the system, so that after receiving it, the non-cell system can directly indicate an uplink transmission resource to the UE, allowing the UE to transmit its data.
  • extremely sparse pilots plus AP_ID information can assist the system in implementing AP energy saving, UE mobility management, pilot allocation, paging, sensing and other functions.
  • extremely sparse pilots plus UE location information can assist the system in implementing AP energy saving, UE mobility management, pilot allocation, paging, sensing and other functions.
  • the transmission module is further configured to transmit the W extremely sparse pilots and target information to a cell-free system when the terminal is in a disconnected state.
  • U symbols in each extremely sparse pilot are non-zero values, and the U non-zero values are carried on U adjacent resource units in time and frequency, or on U symbols that are successive in time, or on U resource units on adjacent subcarriers in the frequency domain, where U is greater than 0 and less than 5.
  • the length of each pilot is greater than 24.
  • U 2
  • the non-zero value [p1, p2] includes: [a1, a2], or [b1, b2], wherein [a1, a2] is orthogonal to [b1, b2].
  • the W extremely sparse pilots are independent.
  • the W extremely sparse pilots are determined by information in a transmitted data packet.
  • the W extremely sparse pilots are determined by one or more bits in a transmitted data packet.
  • each extremely sparse pilot comes from a pilot set including D extremely sparse pilots, and each extremely sparse pilot is determined from the pilot set using log2(D) bits in the transmitted data packet.
  • the value of W is 2 or 1.
  • the above modules can be implemented by software or hardware. For the latter, it can be implemented in the following ways, but not limited to: the above modules are all located in the same processor; or the above modules are located in different processors in any combination.
  • An embodiment of the present disclosure further provides a computer-readable storage medium, in which a computer program is stored, wherein the computer program is configured to execute the steps of any of the above method embodiments when running.
  • the above-mentioned computer-readable storage medium may include, but is not limited to: a USB flash drive, a read-only memory (ROM), a random access memory (RAM), a mobile hard disk, a magnetic disk or an optical disk, and other media that can store computer programs.
  • An embodiment of the present disclosure further provides an electronic device, including a memory and a processor, wherein a computer program is stored in the memory, and the processor is configured to run the computer program to execute the steps in any one of the above method embodiments.
  • the electronic device may further include a transmission device and an input/output device, wherein the transmission device is connected to the processor, and the input/output device is connected to the processor.
  • modules or steps of the present disclosure can be implemented by a general-purpose computing device, they can be concentrated on a single computing device, or distributed on a network composed of multiple computing devices, they can be implemented by a program code executable by a computing device, so that they can be stored in a storage device and executed by the computing device, and in some cases, the steps shown or described can be executed in a different order than here, or they can be made into individual integrated circuit modules, or multiple modules or steps therein can be made into a single integrated circuit module for implementation. In this way, the present disclosure is not limited to any specific combination of hardware and software.

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Abstract

一种信息传输方法及装置、存储介质、电子装置。其中，该方法应用于终端，包括：确定W个极稀疏导频，其中，W为大于0的整数；将W个极稀疏导频和目标信息传输至无小区系统。解决了相关技术中无小区系统中无合适的导频进行使用的问题。

Description

信息传输方法及装置、存储介质、电子装置
本公开要求于2022年11月30日提交中国专利局、申请号为202211521114.1、发明名称“信息传输方法及装置、存储介质、电子装置”的中国专利申请的优先权，其全部内容通过引用结合在本公开中。
技术领域
本公开实施例涉及通信领域，具体而言，涉及一种信息传输方法及装置、存储介质、电子装置。
背景技术
对于Cell-free(无小区，或去小区)无线通信系统，通过大范围部署大量低成本的接入节点(access point，简称为AP)，可以让AP离用户终端(User Equipment，简称为UE)更近，减小路损，整个网络内UE的传输信号强度比较稳定。并且大量分布式的AP可以提供很强的空分复用能力，也就是不同UE到大量分布式AP的空域信道的相关性会比较低，因此Cell-free系统可以简单高效的方式支持多个UE同时同频通信。部署了大量分布式AP的Cell-free系统，实质是一个超大孔径天线阵列(Extremely Large Aperture Array，简称为ELAA)。
如图1-2所示，cell-free网络包含很多接入节点AP，图1-2中的一个圆形代表一个接入节点，每个节点可以有一根或多根收发天线，这些接入节点通常是分布式(distributed)部署的，通过一定连接方式(拓扑方式)连接到中央处理单元(central processing unit，简称为CPU)。例如，图1所示是M个接入节点通过条带状前传(radio stripe front haul)连接到一个CPU。图2所示是M个接入节点的一部分通过一条条带状前传连接到一个CPU，另一部分通过另一条条带状前传连接到CPU。
cell-free网络的无线信号的发射和接收都是通过接入节点(access point，简称为AP)来完成的。上行多用户传输以图1为例说明。设K个UE给cell-free网络发射数据，cell-free网络中有M个AP通过一条radio stripe front haul连接到CPU。为了简化，先假定每个AP只有一根接收天线。假设每个用户发射的L个符号经历的无线信道是一样的，不同用户的符号经历的信道是独立的，则APm收到的L个数据符号是：
其中ym＝[ym，1，ym，2，…ym，L]是APm收到的L个数据符号构成的矢量，是一个L长行矢量；sk＝[sk，1，sk，2，…sk，L]是UEk发射的L个数据符号构成的矢量，是一个行矢量；hmk是UEk到APm的无线信道，是一个标量，nm是APm上的加性高斯白噪声(Additive White Gaussian Noise，简称为AWGN)，也是一个L长的行矢量。
进一步，M个AP收到的信号可以写成矩阵形式：
其中是一个M*L的矩阵，有M行，第m行是ym；
是一个L*L的矩阵，第m行是ym；
hk＝[h1，k，h2，k，…hM，k]T是用户k到M个AP空域信道矢量，是一个M长列矢量，而有M行；H＝[h1，h2，…hK]，是一个M*K的矩阵。AWGN噪声N是一个M*L矩阵。
基于条带状前传架构的cell-free系统为了减少条带状前传(radio stripe front haul)的带宽，通常不会让每个AP将自己的接收信号传给CPU的，因为这样做的话，距离CPU最近的AP与CPU之间的front haul需要传输所有M个AP的接收数据，而通常M会很大，因此这样需要非常大的front haul带宽。所以，为了减少front haul的带宽，通常会基于一种共轭合并的方法：也就是APm通过UEk的参考信号来估计得到UEk到APm的无线信道hmk，然后用hmk的共轭，即来加权接收到的数据符号ym，得到与用户k有关的数据符号然后和前一个AP(即APm-1)传过来的和用户k有关的数据符号累加起来，即得到然后将这个累加后的信号传给下一个AP(即APm+1)，如此类推，最后第M个AP传给CPU的用户k有关的数据符号就是CPU那里用户k有关的信号还可以写成其中是hk矢量的共轭转置。也就是说，CPU收到K个用户的移动无线电信道(Mobile Radio Channel，简称为MRC)数据符号合起来可以写成SMRC＝HHY。可见，CPU那里得到的SMRC＝HHY＝HHsS+HHN就是一种对K个用户的数据符号的最大比合并。由于不同UE到大量分布式AP的空域信道的相关性会比较低，因此HHH相关阵中非对角线元素相对会比较小，因此cell-free系统可以简单高效的方式支持多个UE同时同频、并且互相干扰比较小地通信。
上述这种基于共轭合并的空域MRC接收方法，每个AP的处理都比较简单：先根据导频信号进行用户的信道估计，并根据不同用户的信道用简单的乘法累加运算就可以实现该用户数据符号的空域MRC合并，然后将各个用户的空域MRC合并后的数据符号流传给下一个AP就可 以了。这样front haul上只需要传输K个用户的MRC合并后数据符号流，而不需要传输M个AP的接收数据符号流，由于cell-free系统中AP数目M通常远大于UE数目M的，因此上述这种基于共轭合并的MRC接收方法可以极大减少front haul的带宽需求。
综上所述，基于条带状前传架构的Cell-free系统可以非常简单的AP实现和较小的前传带宽，就可以高效支持多个UE空分复用，因此可以实现低成本的部署。进一步，由于大量分布式AP提供的低空域信道相关度，可以使得不同UE的互相干扰比较小，而且UE通常距离AP比较近，所以最终即使多用户复用下，空域接收后，UE的数据符号的信干噪比(Signal-to-Interference plus Noise Ratio，简称为SINR)还是比较高的，因此多个空分复用UE都有潜力实现高谱效的通信。
基于条带状前传架构的超大孔径天线阵列和基于条带状前传的cell-free系统是非常类似的，上述描述同样适用于基于条带状前传架构的超大孔径天线阵列。
但是，虽然cell-free系统虽然有很强的空域多用户复用能力，但是，面向海量连接场景时，cell-free系统的能力会严重受限于导频。
针对相关技术中，无小区系统中无合适的导频进行使用的问题，尚未提供有效的解决方案。
发明内容
本公开实施例提供了一种信息传输方法及装置、存储介质、电子装置，以至少解决相关技术中无小区系统中无合适的导频进行使用的问题。
根据本公开的一个实施例，提供了一种信息传输方法，应用于终端，包括：确定W个极稀疏导频，其中，W为大于0的整数；将所述W个极稀疏导频和目标信息传输至无小区系统。
根据本公开的另一个实施例，还提供了一种信息传输设备，包括：确定模块，设置为确定W个极稀疏导频，其中，W为大于0的整数；传输模块，设置为将所述W个极稀疏导频和目标信息传输至无小区系统。
根据本公开的又一个实施例，还提供了一种计算机可读存储介质，所述计算机可读存储介质中存储有计算机程序，其中，所述计算机程序被设置为运行时执行上述任一项方法实施例中的步骤。
根据本公开的又一个实施例，还提供了一种电子装置，包括存储器和处理器，所述存储器中存储有计算机程序，所述处理器被设置为运行所述计算机程序以执行上述任一项方法实施例中的步骤。
通过本公开，由于可以将确定出的W个极稀疏导频和目标信息一起发送至无小区系统。可以解决相关技术中，无小区系统中无合适的导频进行使用的问题。进而可以向无小区系统发送合适的W个极稀疏导频供无小区系统使用。
附图说明
图1是相关技术中的无小区系统的架构示意图；
图2是相关技术中的无小区系统的另一架构示意图；
图3是本公开实施例的一种信息传输方法的终端的硬件结构框图；
图4是根据本公开实施例的信息传输方法的流程图；
图5为根据本公开可选实施例提供的一种定义物理资源块的实现示意图；
图6为根据本公开可选实施例提供的一种定义物理资源块的另一实现示意图；
图7为根据本公开可选实施例提供的另一种定义解调参考信号的实现示意图；
图8为根据本公开可选实施例提供的一种采用OCC码定义解调参考信号的实现示意图；
图9为根据本公开可选实施例提供的另一种采用OCC码定义解调参考信号的实现示意图；
图10为根据本公开可选实施例提供的又一种采用OCC码的解调参考信号的实现示意图；
图11为根据本公开可选实施例提供的一种基于PRB传输的实现示意图；
图12为根据本公开可选实施例提供的一种定义解调参考信号的实现示意图；
图13为根据本公开可选实施例提供的再一种定义解调参考信号的实现示意图；
图14为根据本公开可选实施例提供的又一种定义解调参考信号的实现示意图；
图15为根据本公开可选实施例提供的另一种定义参考信号的实现示意图；
图16为根据本公开可选实施例提供的一种定义参考信号的实现示意图(一)；
图17为根据本公开可选实施例提供的一种定义参考信号的实现示意图(二)；
图18为根据本公开可选实施例提供的一种生成DMRS端口的实现示意图；
图19为根据本公开可选实施例提供的一种定义参考信号的实现示意图(三)；
图20为根据本公开可选实施例提供的一种定义参考信号的实现示意图(四)；
图21为根据本公开可选实施例提供的一种信息传输方法的实现示意图；
图22为根据本公开可选实施例提供的一种星座图的实现示意图；
图23为根据本公开可选实施例提供的一种PAM星座图的实现示意图；
图24为根据本公开可选实施例提供的另一种PAM星座图的实现示意图；
图25为根据本公开可选实施例提供的一种十字形星座图的实现示意图；
图26为根据本公开可选实施例提供的另一种十字型星座图的实现示意图；
图27为根据本公开可选实施例提供的一种旋转后的十字形星座图的实现示意图；
图28为根据本公开可选实施例提供的一种旋转后的经AGWN处理的十字形星座图的实现示意图；
图29为根据本公开可选实施例提供的另一种旋转后的经AGWN处理的十字形星座图的实现示意图；
图30为根据本公开可选实施例提供的一种分区的实现示意图；
图31为根据本公开可选实施例提供的另一种分区的实现示意图；
图32为根据本公开可选实施例提供的一种旋转缩放后的星座示意图；
图33为根据本公开可选实施例提供的另一种旋转缩放后的星座示意图；
图34为根据本公开可选实施例提供的又一种旋转缩放后的星座示意图；
图35是根据本公开实施例的信息传输设备的结构框图。
具体实施方式
下文中将参考附图并结合实施例来详细说明本公开的实施例。
需要说明的是，本公开的说明书和权利要求书及上述附图中的术语“第一”、“第二”等是用于区别类似的对象，而不必用于描述特定的顺序或先后次序。
本公开实施例中所提供的方法实施例可以在终端、计算机设备或者类似的运算装置中执 行。以运行在终端上为例，图3是本公开实施例的一种信息传输方法的终端的硬件结构框图。如图3所示，终端可以包括一个或多个(图3中仅示出一个)处理器102(处理器102可以包括但不限于微处理器MCU或可编程逻辑器件FPGA等的处理装置)和用于存储数据的存储器104，其中，上述终端还可以包括用于通信功能的传输设备106以及输入输出设备108。本领域普通技术人员可以理解，图3所示的结构仅为示意，其并不对上述终端的结构造成限定。例如，终端还可包括比图3中所示更多或者更少的组件，或者具有与图3所示不同的配置。
存储器104可用于存储计算机程序，例如，应用软件的软件程序以及模块，如本发明实施例中的信息传输方法对应的计算机程序，处理器102通过运行存储在存储器104内的计算机程序，从而执行各种功能应用以及数据处理，即实现上述的方法。存储器104可包括高速随机存储器，还可包括非易失性存储器，如一个或者多个磁性存储装置、闪存、或者其他非易失性固态存储器。在一些实例中，存储器104可进一步包括相对于处理器102远程设置的存储器，这些远程存储器可以通过网络连接至终端。上述网络的实例包括但不限于互联网、企业内部网、局域网、移动通信网及其组合。
传输设备106用于经由一个网络接收或者发送数据。上述的网络具体实例可包括终端的通信供应商提供的无线网络。在一个实例中，传输设备106包括一个网络适配器(Network Interface Controller，简称为NIC)，其可通过基站与其他网络设备相连从而可与互联网进行通讯。在一个实例中，传输设备106可以为射频(Radio Frequency，简称为RF)模块，其用于通过无线方式与互联网进行通讯。
在本实施例中提供了一种运行于上述终端的信息传输方法，图4是根据本公开实施例的信息传输方法的流程图，如图4所示，该流程包括如下步骤：
步骤S402，确定W个极稀疏导频，其中，W为大于0的整数；
步骤S404，将所述W个极稀疏导频和目标信息传输至无小区系统。
通过上述技术方案，由于可以将确定出的W个极稀疏导频和目标信息一起发送至无小区系统。可以解决相关技术中，无小区系统中无合适的导频进行使用的问题。进而可以向无小区系统发送合适的W个极稀疏导频供无小区系统使用。
在一个示例性实施例中，所述方法还包括：所述目标信息包括以下至少之一：UE_ID信息(UE_ID也就是UE标识)，UE类型信息，UE能力信息，UE的收发天线数量，UE支持的传输数据流数，调度请求(Scheduling Request，简称为SR)，缓存状态报告(Buffer Status Report，简称为BSR)，UE的位置信息，1个或多个AP_ID信息(AP_ID也就是AP标识)，1个或多个AP到终端的信道状态信息(Channel State Information，简称为CSI)。
在一个示例性实施例中，当所述目标信息包括所述信道状态信息时，所述信道状态信息包括如下至少之一：预编码矩阵指示；信道质量指示；秩指示；SSB资源指示；参考信号功率。
在无小区系统接收到上述目标信息后，这些信息可以协作cell-free系统更好地接入、调度、多用户配对、寻呼、UE移动性管理等，也有利于cell-free系统进行感知等应用。
举例说明，极稀疏导频加上包含UE_ID的信息，也就是极稀疏导频加上包含UE_ID的信息一起传给无小区系统，可以用来做随机接入，也就是“极稀疏导频加上包含UE_ID的信息”可以作为随机接入信道(RACH或PRACH)的Msg1。
cell-free系统(相当于无小区系统)如果沿用现有的随机接入方法会有较大的问题，这是因为现有的随机接入的Msg1，都是基于Zadoff-Chu(ZC)序列的：如果是4步RACH，则Msg1只包含一条ZC序列；如果是2步RACH，则Msg1包含一条ZC序列和一个数据包。
但如果要求AP去检测Msg1的ZC序列，并且基于Msg1的ZC序列做信道估计，则AP需要增加比较多的处理复杂度，这会增加AP的成本和功耗。另一方面，如果AP对于Msg1不做处理，而是将Msg1通过radio stripe front haul传给CPU，则所有AP的数据都需要分立地传给CPU，也就是说，M个AP的话，radio stripe front haul上就需要传输M个Msg1的信息。如果AP数目M很大，则仅仅Msg1的传输就需要占用radio stripe front haul较大的带宽。而且大量AP的Msg1传回给CPU，就要求CPU在短时间内处理完所有的Msg1，这对CPU来说也是很大的负担。
因为，本公开实施例的极稀疏导频加上包含UE_ID的信息作为随机接入信道(RACH或PRACH)的Msg1，这样AP可以沿用原来的简单信道估计及空域MRC合并操作，保持AP的简单实现和低功耗；radio stripe front haul也不用增加太多带宽；CPU也不用为Msg1增加太多处理复杂度。
在另一个实施例中，极稀疏导频加上包含UE_ID的信息也可以作为Cell-free系统中UE发送的“心跳信号”。辅助无小区系统更容易地实现AP节能，UE移动性管理，导频分配，寻呼等功能。
在另一个实施例中，极稀疏导频加上包含UE_ID的信息也可以作为Cell-free系统中UE发送的调度请求。这样可以简化多用户调度的实现。
在另一个实施例中，极稀疏导频加上包含UE能力信息可以用于系统与UE进行与UE能力相匹配的传输。
在另一个实施例中，极稀疏导频加上包含UE_ID及BSR的信息可以实现低信令开销、低时延的UE上行传输。当终端有上行数据传输时，可以直接给系统传输“极稀疏导频加上包含UE_ID及BSR的信息”，这样无小区系统收到后，就可以直接给UE指示一个上行传输资源，让UE将其数据传上来。
在另一个实施例中，极稀疏导频加上UE的位置信息可以辅助系统实现AP节能，UE移动性管理，导频分配，寻呼，感知等功能。
在另一个实施例中，极稀疏导频加上1个或多个AP_ID信息可以辅助系统实现AP节能，UE移动性管理，导频分配，寻呼，感知等功能。
在另一个实施例中，极稀疏导频加上1个或多个AP到终端的信道状态信息(Channel State Information，简称为CSI)，可以辅助系统实现更优的多用户调度、多用户配对、资源分配、功率分配、波束管理、切换管理、寻呼等功能。
在一可行的实施方式，信道状态信息至少包括预编码矩阵指示(Pre-coding matrix Indication，简称为PMI)；信道质量指示(Channel Quality Indicator，简称为CQI)；秩指示，即RANK指示(Rank Indication，简称为RI)；SSB资源指示(SSBRI)；参考信号功率 (Reference Signal Power，简称为RSRP)中的至少之一。预编码矩阵指示中的预编码是多天线系统中，发射侧对传输信号做预处理所需的信息，通常是矩阵形式，在多输入多输出(Multiple-Input Multiple-Output，简称为MIMO)系统中，接收端与发送端分别存储一套包含若干个预编码矩阵的码书，这样接收端可以根据估计出的信道矩阵和预设准则从码书中选择一个目标预编码矩阵，并将该目标预编码矩阵的索引值和量化后的信道状态信息(即信道状态量化信息)反馈给发送端，在下一个时刻，发送端采用新的预编码矩阵，并根据接收端反馈的信道状态量化信息为码字确定编码和调制方式；信道质量指示指的是满足某种性能，例如满足误块率(Block Error Rate，简称为BLER)指标为10％的情况下对应的信道质量的索引值，该索引值包括信道当前的调制方式、编码速率及效率等信息，通常通道质量指示(Channel Quality Indicator，简称为CQI)的索引越大，编码效率越高；RANK指示中的RANK为MIMO方案中天线矩阵中的秩，表示并行的有效的数据流数；SSB资源指示可以指示波束索引，可以用于波束管理，(Synchronization Signal and PBCH block，简称为SSB)指的是同步信号和物理广播信道(Physical Broadcast Channel，简称为PBCH)块，SSB由主同步信号(Primary Synchronization Signals，简称为PSS)、辅同步信号(Secondary Synchronization Signals，简称为SSS)和PBCH块三部分共同组成；参考信号功率可以指示信号强度，例如L1-RSRP可以指示波束强度。
在一个示例性实施例中，所述方法还包括：在所述W个极稀疏导频中，每个极稀疏导频中只有U个符号是非零值，且U个非零值承载在时频上相邻的U个资源单元上，或者承载在时间上先后的U个符号上，或者承载在频域相邻子载波上的U个资源单元上，其中，U是大于0，且小于5。
在一个示例性实施例中，所述方法还包括：在所述W个极稀疏导频中，每个导频中的长度均大于24。
在一个示例性实施例中，所述方法还包括：所述U＝1。
在一个示例性实施例中，所述方法还包括：所述U＝2，且所述非零值[p1，p2]包括：[a1，a2]，或[b1，b2]，其中，[a1，a2]与[b1，b2]正交，即a1′*b1+a2′*b2＝0，这里a1′和a2′分别是复数a1和a2的共轭
在一个示例性实施例中，所述方法还包括：所述U＝2，且所述非零值[p1，p2]的取值情况包括以下至少之一：[p1，p2]＝[1，1]；[p1，p2]＝[1，-1]；[p1，p2]＝[1，j]；[p1，p2]＝[1，-j]。
在一个示例性实施例中，所述方法还包括：所述U＝4，且4个非零取值[p1，p2，p3，p4]的取值情况包括以下至少之一：
[p1，p2，p3，p4]＝[a1，a2，a3，a4]；[p1，p2，p3，p4]＝[b1，b2，b3，b4]；[p1，p2，p3，p4]＝[c1，c2，c3，c4]；[p1，p2，p3，p4]＝[d1，d2，d3，d4]；其中，[a1，a2，a3，a4]，[b1，b2，b3，b4]，[c1，c2，c3，c4]，[d1，d2，d3，d4]互相正交。可以理解的是，[a1，a2，a3，a4]与[b1，b2，b3，b4]正交，就是a1′*b1+a2′*b2+a3′*b3+a4′*b4＝0。其他情况类似，本公开实施例不再赘述。
在U＝4时，则4个非零值p1，p2的取值包含至少如下的情况：[p1，p2，p3，p4]＝

在一个示例性实施例中，所述方法还包括：所述W大于1时，所述W个极稀疏导频是独立无关的。
在一个示例性实施例中，所述方法还包括：所述W个极稀疏导频是通过传输的数据包中的信息确定的。
在一个示例性实施例中，所述方法还包括：所述W个极稀疏导频是通过传输的数据包中的一个或多个比特确定的。
在一个示例性实施例中，每个极稀疏导频均来自一个包含D个极稀疏导频的导频集合，且每个极稀疏导频是通过传输的数据包中的log2(D)个比特从所述导频集合中确定。
在一个示例性实施例中，所述W取值为2或1。
为了更好的理解上述信息传输方法，以下结合可选实施例对上述技术方案进行解释说明，但不用于限定本公开实施例的技术方案。
在一个可选实施例中，提供了一种针对传统导频方案的具体实现方式：
终端没有数据传输时，为了省电，通常都不会一直和系统有连接的，也就是与系统是没有连接的，也即断开连接的，也即终端可以说是处于无连接态的(具体包括：Non connected state，Non RRC connected state，Connectionless state，Connection-free state，Disconnected state)。上述无连接态也可以理解为是空闲态(Idle state)或非激活态(Inactive state)。当终端原来处于无连接态，即还没有进入连接态时，如果沿用传统的上行数据传输方案，为了传输信息，终端必须在传输前先与系统建立连接。在进入连接态(也称激活态(Active state))后，终端才能进一步去向系统申请上行传输资源；等到获得系统的资源授权后才能进行真正的数据传输。可见，终端要完成一次传统的上行数据传输，需要事先完成很多操作，这无疑会增加终端的功耗，也会增加系统的信令开销。
相反，无连接数据传输，终端在数据传输前无需建立连接，也无需向系统申请专用的传输资源；而是允许处于无连接状态下的终端，传输前无需通知系统，而是自主地决定传输，并直接在一个预设的公共的传输资源上向系统传输数据。因此无连接数据传输可以实现极简化的数据传输，减少传输的功耗和时延，也节省传输所需的信令开销，优点非常明显。
但是无连接传输，导频\参考信号也是用户自主地从导频集合里选择的，所以不同用户是有可能选择相同的参考信号的，即参考信号碰撞。本公开的可选实施例中，导频和参考信号是等价的。如果导频数量、或参考信号数量有限，而用户负载比较高即用户很多时，出现导频\参考信号碰撞的概率非常高。一旦参考信号发生碰撞，CPU和AP接入点都很难通过参考信号分离出这两个用户来。
为了减少导频的碰撞，可以采用独立多导频技术。独立多导频技术是指一次传输中包含2个或多个导频，并且导频之间是独立无关的，或无关联的，或不相关的。这样在相同的导频开销下，不同终端的独立多导频同时碰撞的概率会比单导频小很多。而CPU通过基于迭代的接收机，每轮都可以通过那些不碰撞的导频解出对应的终端的数据包，然后根据数据包中包含的导频相关的信息，CPU可以导频和数据都重构出来并从接收信号中消除掉，如此迭代直到解出所有可解的终端的数据包。由于独立多导频同时碰撞的概率会比单导频小很多，采用独立多导频的传输方案可以在无连接传输情况下支持很高的终端负载。
需要定义尽可能多的导频，也就是导频集合里的导频数量要尽可能多，而增加导频数量意味着导频的占用的开销也需要增加。另一方面，如果沿用传统的导频技术，即还要求通过每个导频来估计信道、时频偏，以此来完成数据符号的相关解调，则每个导频都需要在整个传输带宽以及时间内都有信号。或者说每个导频在整个传输带宽以及时间内不能太稀疏，要有一定的密度，这样才能估计出整个传输带宽内的无线多径信道(也即频率选择性信道)以及传输时间内的频偏。所以，要确保无连接状态下的传输性能，沿用相关的导频方案，导频所占用的开销会显著增加，检测复杂度也会显著增加。
稀疏导频方案可以在不增加导频资源开销的情况下，显著增加导频的数量，因此显著减少导频碰撞的概率，CPU通过从数据符号中提取信道信息，这样可以缓解稀疏导频的压力，即只要求从稀疏导频中估计出无线信道的部分信息，而无需从稀疏导频中估计出无线信道的全部信息。
另一方面，独立多导频技术是指一次传输中包含2个或多个导频，并且导频之间是无关联的/独立的。这样在相同的导频开销下，不同用户的W个独立的导频同时碰撞的概率会比单个导频小很多。CPU可以通过基于迭代的接收机，每轮都可以通过那些没有碰撞的导频解出对应的用户，然后将其数据和导频都重构出来并从接收信号中消除掉，如此迭代直到解出所有可解的用户。由于独立多导频同时碰撞的概率会比单导频小很多，采用独立多导频的传输方案可以在竞争的无连接状态传输(或竞争免调度传输)情况下支持很高的用户负载。本实施例中，可以结合独立多导频技术和稀疏导频技术，即采用多个独立无关的稀疏导频，来进一步减少用户导频碰撞的情况，进一步提升用户负载。
上述的信息传输，其中的信息是广义的信息，既可以是业务数据，也可以是用于系统控制的数据，即信令。或者说，需要传输的比特，不管是业务数据比特，还是信令比特，在本公开实施例度可以理解为是信息。另一个角度，需要传输的信息，也是数据。不同的英文表述：message，information，payload，都在本公开实施例的保护范围内。
在本公开的另一个可选实施例中，对于极稀疏导频，以及多个极稀疏导频提供了一种实现方案。在传统的导频方案中，定义一种解调参考信号(Demodulation Reference Signal，简称为DMRS)集合，其中包含12个参考信号。也可称一个解调参考信号为一个解调参考信号端口(DMRS ports)，也就是说，定义的一种包含12个解调参考信号端口(DMRS ports)的集合。
图5为根据本公开可选实施例提供的一种定义物理资源块的实现示意图。如图5所示，定义的一个物理资源块(Physical Resource Block，简称为PRB)，包含时域上14个正交频分复用(0rthogonal Frequency Division Multiplexing，简称为OFDM)(或者离散傅里叶变换扩展OFDM(Discrete Fourier Transform-Spread-Orthogonal Frequency Division Multiplexing，简称为DFT-S-OFDM)或者单载波频分多址(Single-carrier Frequency-Division Multiple Access，简称为SC-FDMA))符号，频域上12个子载波。其中每个小格子是一个OFDM符号的一个子载波，通常也称为一个资源单元(Resource Element，简称为RE)。也就是说图5所示的一个物理资源块(PRB)一共包含12*14＝168个资源单元(RE)。
对于OFDM来说，一个资源单元可以承载一个符号。另一方面，如果U个符号承载在相邻的RE上，也可以说这U个符号承载在相邻的时频资源符号上。或者反过来说，如果U个符号承载在相邻的时频资源符号上，对于OFDM来说，就等价于这U个符号承载在相邻的RE上。
图6所示这种解调参考信号使用前2个OFDM符号来承载解调参考信号，即前2个OFDM符号作为参考信号区域，也就是说解调参考信号占用的资源开销是1/7。除参考信号区域外的区域为数据符号区域。
图5为根据本公开可选实施例提供的一种定义解调参考信号的实现示意图。如图6所示，解调参考信号(DMRS)从占用资源单元(RE)位置来看可以分成三组，在附图6中从左到右依次为第一组，第二组和第三组，第一组解调参考信号(DMRS)的非零符号(或称为非零信号、有用信号等)(即符号是非零值)承载在如图所示图案的资源单元(RE)上，第一组4个DMRS端口通过OCC码区分；第二组解调参考信号(DMRS)的非零符号承载在如图所示图案的资源单元(RE)上，第二组4个DMRS端口通过OCC码区分；第三组解调参考信号(DMRS)的非零符号承载在如图所示图案的资源单元(RE)上，第三组4个DMRS端口通过OCC码区分。每个解调参考信号在如图所示空白未填充图案的资源单元(RE)上取值为0，或者说是没有信号的。可 见，对于每个解调参考信号来说，并不是在解调参考信号区的所有资源单元(RE)都有信号的。但是，对某个终端而言，只要他使用了某个参考信号/某个参考信号端口，虽然这个参考信号端口在参考信号(DMRS)区域的一些RE上没有信号，但是通常这个终端还是不能利用这些RE来传输数据。从这个角度来说，一个参考信号/一个参考信号端口，占用的资源开销也是1/7。
每组解调参考信号的非零符号承载在相同的资源单元(RE)上，只能通过不同取值的非零符号区分出不同的参考信号。通常可通过时域OCC码以及频域OCC码来区分出不同的参考信号端口。图7为根据本公开可选实施例提供的另一种定义解调参考信号的实现示意图。如图7所示，以图6中第一组中的4个解调参考信号为例，是通过联合使用时域上的两长OCC码[1，1]、[1，-1]，以及频域上的两长OCC码[1，1]、[1，-1]，来分出4个解调参考信号端口的；即每组DMRS端口中，通过在有图案的RE上承载不同的OCC码，来生成不同的DMRS端口。上述图6中第二组和第三组中的4个参考信号的情况也是类似的。这样，一共可以得到定义的这种解调参考信号(DMRS)集合的12个解调参考信号，也就是12个解调参考信号端口。
图8为根据本公开可选实施例提供的一种采用OCC码定义解调参考信号的实现示意图。如图8所示，对于图4中第一组中的4个解调参考信号，是通过联合使用时域上的两长OCC码[1，1]、[1，-1]，以及频域上的两长OCC码[1，1]、[1，-1]，来分出4个解调参考信号端口。
图9为根据本公开可选实施例提供的另一种采用OCC码定义解调参考信号的实现示意图。如图9所示，对于图5中第二组中的4个解调参考信号，是通过联合使用时域上的两长OCC码[1，1]、[1，-1]，以及频域上的两长OCC码[1，1]、[1，-1]，来分出4个解调参考信号端口。
图10为根据本公开可选实施例提供的又一种采用OCC码的解调参考信号的实现示意图。如图10所示，8表示第一个参考信号单元，9表示第二个参考信号单元；对于图5中第三组中的4个解调参考信号，是通过联合使用时域上的两长OCC码[1，1]、[1，-1]，以及频域上的两长OCC码[1，1]、[1，-1]，来分出4个解调参考信号端口。
本公开实施例中，可将时域及频域上相邻的若干个资源单元(RE)上承载参考信号称为一个参考信号单元(Reference Signal Element，简称为RSE)，也将时间上先后的若干个符号上承载的参考信号称为一个参考信号单元。例如图5-9中，时频域上连续的4个资源单元(RE)上承载参考信号称为一个参考信号单元(RSE)，形象地看，有图案填充下的“田字格”上的参考信号就是一个参考信号单元(RSE)。从信道估计的功能上看，一个参考信号单元(RSE)除了由时\频域上相邻的资源单元构成的特点外，还有一个特点：在应用参考信号进行信道估计时，每个参考信号单元(RSE)可以估计一个信道值。
按此定义，如图4-图10所示定义的解调参考信号(DMRS)集合，每一个参考信号在1个PRB带宽内都有2个参考信号单元(RSE)，因此可以估计出一个1个PRB带宽内(也即12个子载波带宽内)2处的信道值。1个PRB带宽内12个子载波的信道值，需要通过这些参考信号单元估计值插值得到。图11为根据本公开可选实施例提供的一种基于PRB传输的实现示意图。如图11所示，如果一次传输包含X个PRB，则这种参考信号集合的12个解调参考信号(或者12个解调参考信号端口)如图12，图13，图14所示，每个参考信号有2*X个参考信号单元(RSE)，可以估计整个传输带宽内等间隔的2*X处的信道值，然后通过插值得到传输带宽内全部12*X个子载波的信道值。
12个解调参考信号(DMRS)从占用资源单元(RE)位置来看可以分成三组。
图12为根据本公开可选实施例提供的一种定义解调参考信号的实现示意图。如图12所示，是通过OCC码区分第一组的4个解调参考信号。
图13为根据本公开可选实施例提供的再一种定义解调参考信号的实现示意图。如图13所示，是通过OCC码区分第二组的4个解调参考信号。
图14为根据本公开可选实施例提供的又一种定义解调参考信号的实现示意图。如图14所示，是通过OCC码区分第三组的4个解调参考信号。
可见，为了估计每个接入终端的整个传输带宽的信道，解调参考信号(或导频)占用的资源是比较大的，或者说解调参考信号在整个传输带宽内是需要一定的密度的，不能太稀疏。在图5-13中，可以说这种解调参考信号在整个传输带宽内的密度是每PRB有2处参考信号，或者每PRB有2个参考信号单元(RSE)。
对系统而言，参考信号的开销是1/7，也就是说，系统付出了1/7的资源，只能设计12个解调参考信号。对于无连接传输状态下的数据传输而言，任意2个终端自主地选择参考信号的碰撞概率是1/12，还是很大的。所以，解调参考信号会严重限制无连接传输状态下数据传输的终端数。如果参考信号还需要估计一定的频偏(Frequency Offset)，则每个参考信号的占用资源还需要进一步增加，或者说每个参考信号在传输信号中的密度还需要进一步加密。例如，在时域上重复一次，以估计频偏。这样参考信号的占用资源翻倍了，即开销是2/7了。也就是说，系统付出2/7的资源，为了估计频选信道和频偏，也只能设计12个解调参考信号。如果进一步，系统还需要应付一定的时偏(Timing Offset)，则参考信号占用资源需要更进一步地增加，例如，需要付出3/7甚至4/7的开销，才能设计出12个解调参考信号。这么大的开销，只能得到数量这么少参考信号集合(或者说得到这么少的参考信号端口)，无连接状态下传输的碰撞概率是非常高的。
如果多径信道在频域变化得更快一些，即频选特性更加明显，则为了保证信道估计的精度，解调参考信号在频域上的密度需要增加，就是一种频域上密度更大的解调参考信号，每条解调参考信号在每个PRB带宽内有3个参考信号单元(如形象地看有3个田字格)，这样每个PRB上可以有3处估计值，X个PRB就有3*X处估计值，然后通过线性插值得到X个PRB的全部子载波的信道。这种参考信号还是占传输资源的1/7开销，但是只能分出8个解调参考信号(8个解调参考信号端口)，比上述中定义的还要少。可见，信道估计能力通常和参考信号数量是成反比的。
因此，参考信号应用到无连接传输场景中，所面临的问题根源是参考信号的任务或责任太重了：既需要参考信号去估计整个传输信道的频选信道以及时频偏，又需要参考信号去做终端用户识别，所以参考信号需要占用较多的时频资源才能完成这么繁重的任务。这就导致了一定资源下参考信号的数量严重不足。而无连接传输可以支持的终端数又受限于参考信号的数量。
本公开实施例中，能够极大地减轻参考信号的任务，因此每个参考信号占用的资源可以最小化，或者说每个参考信号可以最稀疏，这样可以使得参考信号数量可以最大化，最终无连接传输都可以支持更多的终端。
具体而言，本公开实施例通过基于数据的信道估计技术(而不是基于参考信号)，通过数据自身的特性，例如数据符号的星座图的几何特点，来估计整个传输带宽的信道以及估计时频偏。也就是说不再需要通过参考信号来估计整个传输带宽的信道和时频偏。以信道估计为 例，为了简化描述，以块平衰(Block Flat Fading)信道为例。可以应用后面介绍的分区匹配法来估计信道。
因此本公开实施例中，参考信号的任务比相关方案小得多，所以每个参考信号占用的资源比相关方案少的多，因此一定的开销下，参考信号数量要比相关方案多得多。
另一方面，Cell-free系统有很多AP时，理论上可以提供很强大的空域能力来提高多终端接入的性能。为了获得到这个空域能力，本公开实施例中提出可以使用“极稀疏”的参考信号来估计各个终端信号所经历的空域信道，然后利用这些估计的空域信道来对接收信号做空域合并。然后接收机利用空域合并后的数据符号sk，来估计终端k的信号经历的整个传输带宽的信道以及估计时频偏。然后对空域合并后数据符号sk补偿信道和时频偏。最后对补偿信道和时频偏的数据符号进行解调译码。
所以，本公开实施例不用参考信号来估计整个传输带宽内的信道，也不用其估计时频偏。图15为根据本公开可选实施例提供的另一种定义参考信号的实现示意图，如图15所示，本公开实施例所提出的参考信号占用1个OFDM符号。一次传输包含X个PRB的时频资源，一个物理资源块(PRB)包含时域上14个OFDM(或者DFT-S-OFDM或者SC-FDMA)符号，频域上12个子载波。其中使用前1个OFDM符号来承载解调参考信号，即前1个OFDM符号作为极稀疏导频区域，1/14的资源用于传输参考信号，也就12*X个资源单元(RE)用于传输参考信号。除极稀疏导频区域外的区域为数据符号区域。图16为根据本公开可选实施例提供的一种定义参考信号的实现示意图(一)，如图16所示，系统定义的每个参考信号，都是只在一个RE资源单元上有非零符号(非零信号，或有用信号)，其余地方都是没有信号的(或者说其他地方都是取值为0)。这样占1/14开销的参考信号区域，总共可以分出12*X个参考信号。具体而言，如果6个PRB，1/14开销，可以分出6*12＝72个参考信号，远大于NR系统中的8个或者12个(这种参考信号还是占传输资源的1/7开销的)。
图17为根据本公开可选实施例提供的一种定义参考信号的实现示意图(二)。如图17所示，系统定义的每个参考信号，都是只在2个RE资源单元上有非零符号(非零信号，或有用信号)，每2个RE通过2长的OCC分出2个参考信号，其余地方都是没有信号的(或者说其他地方都是取值为0)。这样占1/14开销的参考信号区域，也是总共可以分出12*X个参考信号。具体而言，如果6个PRB，1/14开销，可以分出6*12＝72个参考信号，远大于NR系统的8个或者12个。极稀疏导频的数量与PRB的个数呈正比。
图18为根据本公开可选实施例提供的一种生成DMRS端口的实现示意图。如图18所示，在有图案的2个RE上承载不同的OCC码(如OCC码1即[1，1]、OCC码2即[1，-1])，来生成不同的DMRS端口。
图19为根据本公开可选实施例提供的一种定义参考信号的实现示意图(三)。如图19所示，系统定义的参考信号占用2个OFDM符号。图20为根据本公开可选实施例提供的一种定义参考信号的实现示意图(四)。如图20所示，系统定义的每个参考信号，都是只在一组时频上相邻的4个RE资源单元上有非零符号(非零信号，或有用信号)，不过会有4个参考信号复用一组相邻的4个RE。复用同一组相邻4个RE的4个参考信号通过OCC码来区分。这样X个PRB的传输中，占1/7开销的参考信号区域总共可以分出24*X个参考信号。具体而言，如果6个PRB，1/7开销，可以分出6*24＝144个参考信号，远大于NR系统的8个或者12个。也说明极稀疏导频的数量与PRB的个数呈正比。
本公开实施例中的所示数值仅为示例性描述，不作具体限定，取值可以根据实际情况进行适应性调整。可见，稀疏导频，其实就是导频集合里的每个导频的非零元素是很少的，例如非零元素只有1-4个，且在导频集合里的每个导频的非零元素在时频资源上是集中分布的，即不需要在传输的时频资源里面铺开或者说分散开，这样可以在不增加导频资源开销的情况下，显著增加导频的数量，因此显著减少导频碰撞的概率。CPU从稀疏导频中估计出无线信道的部分信息，而无需从稀疏导频中估计出无线信道的全部信息。CPU会从数据符号中进一步提取信道信息，进而利用这些信道信息完成对数据符号的均衡。
需要说明的是，这种导频仅仅用于空域合并，但并通常不能用于全部传输信道的均衡，可以认为是一种空域合并参考信号。
虽然图15-18中所示极稀疏参考信号都在传输资源的前面1或2个符号，但本公开实施例并不限制极稀疏参考信号的位置，例如极稀疏参考信号的位置也可以在传输资源的中间的符号。
在本实施例中，还可以应用多条极稀疏导频来进一步减少终端导频碰撞的情况，进一步提升终端负载。也即一次传输中包含多条极稀疏导频，并且极导频之间是无关联的/独立的。这样在相同的导频开销下，不同用户的多个独立的导频同时碰撞的概率会比单个导频小很多。CPU可以通过基于迭代的接收机，每轮都可以通过那些没有碰撞的导频解出对应的用户，然后将其数据和导频都重构出来并从接收信号中消除掉，如此迭代直到解出所有可解的用户。由于独立多导频同时碰撞的概率会比单导频小很多，采用独立多导频的传输方案可以在竞争的无连接状态传输(或竞争免调度传输)情况下支持很高的用户负载。
图21为根据本公开可选实施例提供的一种信息传输方法的实现示意图。如图21所示，在一次传输中包含W条极稀疏参考信号，并且数据包中包含这W条极稀疏参考信号的信息，例如包含这W条极稀疏参考信号的索引号(在导频集合中的索引)，这样，一旦某个终端的数据包译码成功后，就可以知道这个终端这次传输中使用的所有极稀疏导频的信息，从而可以进行导频信号的干扰消除。
针对正交幅度调制方法，本公开实施例提供了以下实现方案。
BPSK、QPSK调制方式虽然谱效比较低，但星座图非常简单，而且对信道的畸变不是很敏感，因此可以很容易应用后面介绍的分区匹配法来估计信道，所以BPSK、QPSK可以应用于导频能力受限的场景。
另一方面，在需要较高谱效的场景，可以通过提高调制方式的阶数来提高谱效。传统的高阶调制方式，例如16QAM，32QAM，64QAM，256QAM等数字幅相调制方式，其星座图在二维平面/复平面上基本是比较均匀地分布的，因而可以比较充分地利用复信号的二维信号空间(也就是二维信号平面)。通信信号在基带上看，通常可以用复数来表示，通常I路信号是实部，Q路信号是虚部。调制符号通常也可以用复数来表示，也就是一个调制符号可以用一个复数来表示，例如调制符号s可以表示为a+j*b，其中j是虚数，即j＝sqrt(-1)，a是s的实部，传输时在I路传输，b是s的虚部，传输时在Q路传输。例如传统的16QAM，其星座图包含16个点，这16个点表示为复数分别为：
3+3j，3+j，3-j，3-3j，
1+3j，1+j，1-j，1-3j，
-1+3j，-1+j，-1-j，-1-3j，
-3+3j，-3+j，-3-j，-3-3j。
可见在实部-3至3，虚部-3至3这个复平面或二维平面(也可以称为复信号空间或者二维信号空间)内，16QAM星座点是比较均匀分布的。
复平面和二维平面时等价的，所以复平面或二维平面，有时也可称为二维复平面。复数的实部与二维平面的x坐标，实部与二维平面的y坐标，是等价的。因此复数也可以用二维平面上的点来表示，也即一个复数a+j*b，可以用二维平面上的坐标为(a，b)的一个点表示。坐标(a，b)表示二维平面的x坐标为a，y坐标为b。所以，16QAM星座图中的16个点除了可以用16个复数来表示，还可以用16个二维平面上的坐标来表示，如下：
(3，3)，(3，1)，(3，-1)，(3，-3)，
(1，3)，(1，1)，(1，-1)，(1，-3)，
(-1，3)，(-1，1)，(-1，-1)，(-1，-3)，
(-3，3)，(-3，1)，(-3，-1)，(-3，-3)。
当然有时为了功率归一化，星座图还会整体有一个功率归一，也即整体会乘以一个归一化因子，例如16QAM的16个复数会都乘以同一个归一化因子1/sqrt(40)。归一化后的16QAM星座图包含的16个点表示为复数分别为：
1/sqrt(40)*[3+3j，3+j，3-j，3-3j，1+3j，1+j，1-j，1-3j，-1+3j，-1+j，-1-j，-1-3j，
-3+3j，-3+j，-3-j，-3-3j]。
功率归一化后的16QAM星座图包含的16个点对应的坐标，就是将上面16个二维坐标都乘以1/sqrt(40)所得的坐标(每个二维坐标的x坐标和y坐标都乘以1/sqrt(40))。功率归一化这只会让星座图有一个整体缩小，缩小后的星座图里面的星座点还是比较均匀分布的。
其他的，如32QAM，64QAM，256QAM等数字幅相调制方式，和16QAM是类似的，星座点是比较均匀分布的。因而传统的高阶调制方式可以比较充分地利用复信号的二维信号空间。进一步，这些高阶调制方式又可以用简单且性能有保证的解调方法，因此可以比较简单高效的方式去逼近传输的性能极限，即香农限。所以，这些高阶调制方式在需要高谱效的场景得到广泛应用。
但是这些高阶调制方式有个问题：一旦调制符号在传输过程中被改变或者说被畸变，解调性能就会严重恶化。
以调制符号经OFDM方式传输为例，也就是调制符号会通过OFDM的子载波来传输：
经过多径信道也即频选信道后，承载在子载波上的调制符号会被信道加权一个复数权值，也即承载在子载波上的调制符号会被频选信道畸变。
如果收发双方存在同步误差，则定时偏差(即时偏)和频率偏差(即频偏)也会导致子载波上的调制符号有一个复数加权值，也即调制符号会被同步误差畸变；
调制符号受到的这些畸变会叠加。以调制符号s经OFDM方式传输为例，设频选信道导致调制符号s上的复数加权值为g1，时频或频偏导致调制符号s上的复数加权值为g2，则如果同时存在频选信道，同步误差，则调制符号上会有一个加权值h等于g1*g2，也就是接收到的符号是y＝2*s+n＝g1*g2*s+n，其中n是加性高斯白噪声(AWGN)。接收侧如果不能将调制符号上的畸变去除，也即不能将调制符号上的复数加权值h均衡掉，则调制符号就会有一个旋转缩放。少量的旋转缩放都会严重制约高阶调制方式的性能，如下图22所示，图中每个小圆点对应一个调制符号，其中附图22的(a)是标准的64QAM调制所对应的星座情况；而附 图22中的(b)是经历了一个复数加权值(也即一个旋转缩放量)后的64QAM调制符号对应的星座情况，也即经历了信道畸变的64QAM调制符号对应的星座情况。如果接收机直接对如图22的(b)这样的被旋转缩放的星座图进行解调，则就算接收机AWGN很小，解调性能会很差。
因此传统高谱效场景非常依赖导频/参考信号去将调制符号上的复数加权值(即畸变)估计出来，也就是会将接收的数据符号y＝h*s+n中的h估计出来，然后才可以均衡掉，即将y除以h，也即y/h＝s+n/h，得到没有畸变、只受AWGN影响的星座图s+n′，从而得到好的解调性能，这里n′＝n/h。
另一方面，应用前面的极稀疏导频方案可以让系统支持更多的用户，因而非常适合大连接场景，例如海量用户在无连接状态下直接传输数据的场景，以及海量用户基于SPS的数据传输场景，都可以应用极稀疏导频方案。但是极稀疏导频方案要求接收机能够通过数据符号自身的特点来进行信道估计，而传统高阶调制的星座图过于密集，不利于CPU通过数据符号提取信道信息，所以本专利提出一种可以支持高谱效，也能让CPU或接入点可以更容易、更准确地通过数据符号提取信道信息的调制方法。
本公开实施例的调制方案可以采用如图23-23所示的PAM星座图，和图25-25所示十字形星座图。所谓十字形星座图是指星座点有一半在一条经过零点(原点)的直线上，另外一半在另一条经过零点(原点)的直线上，且两条直线互相垂直。具体地，图24-25表示的是二维信号平面中的一个16点的十字形星座图，每个星座点对应一个调制符号，每个调制符号可以承载4个比特，也就是4个比特会映射为(调制为)一个调制符号。其中图25是星座点分别在x轴(I路)和y轴(Q路)上的星座图；图26是星座点分别在经过原点的45°方向直线和经过原点的135°方向直线上的星座图。图26表示的星座图可以通过图24旋转45°而成。PAM星座图也可以看成是线性的星座图，全部星座点在一条经过零点(原点)的直线上。
详细来说，每个调制符号(也即每个星座点)可以承载多个比特，图23-25中是4个比特，也就是可以实现高阶调制，从而实现高谱效。
调制符号对应的线性星座图和十字形星座图都具备简单的几何形状，就算接收机收到的调制符号经过了信道的旋转缩放，这些调制符号对应的星座图也仅是一个经过旋转缩放的线性星座图和十字形星座，几何形状依然比较简单。因为线性星座图是最简单的星座图，下面都以稍微复杂的十字星座图为例来说明，线性星座图的处理通常要比十字的更简单。
经过信道旋转缩放的十字形星座如图27所示。其中，图27是发射调制符号s对应的标准星座图，图28是收到的经过旋转缩放的调制符号h*s(即h乘以s，或者也可以表示为h·s，hs)对应的星座图，旋转缩放量是复数h。注意，图27的星座图示意的是没有AWGN的接收调制符号对应的星座图。有AWGN的接收调制符号y＝h·s+n对应的星座图如图29所示。图29其实是在图28星座点的基础上加上AWGN对应的复数，也就是带AWGN的接收调制符号h·s+n对应的星座点会在图28星座点h·s的周围、按照AWGN的概率密度分布。图29中，颜色从中间到边缘由深到浅变化的一团，是该团中心对应的调制符号被AWGN影响形成的点的集合。由图29也可以看出，即使有AWGN，接收调制符号对应的星座图大体形状还能保持十字形。因此，接收机可以利用如由图29的星座图的几何形状来估计星座图所受到的旋转缩放量，也就是将h估计出来。本公开实施例提供了一种以下实现方案：
首先，将二维平面或者说二维信号平面分为4个分区，例如两种典型的将二维信号平面分为4个分区的方法是：
第一种，以4个象限为4分区，也即以x轴和y轴为分区线，如图30所示，斜线填充是分区1，细点填充是分区2，竖线填充是分区3，砖块状填充是分区4。
第二种是：将第一种的4个分区旋转45°形成的4个分区为所需的分区，如图31所示。也就是：以由圆点往45°射线至由圆点往135°射线为分区1，以斜线填充；以由圆点往135°射线至由圆点往225°射线为分区2，以细点填充；以由圆点往225°射线至由圆点往315°射线为分区3，以竖线填充；以由圆点往315°射线至由圆点往45°射线为分区4，以砖块状填充。
除了如图30-30所示两种分区方法，其他可以将二维平面分为4个分区的方法也是可以的，不过采用如图30-30所示两种分区方法时，判断一个星座点属于哪个分区可以仅通过对星座点坐标进行一些简单的加减法，不需要较复杂的乘法运算，因而实现更简单。
接收机将二维信号平面分为4个分区后，分别将每个分区里面的星座点(每个星座点对应一个调制符号)加起来，再除以该分区内星座点的数量(即调制符号的数量)，所得的星座点，就是该分区星座点的中心。图32是如图27那样的十字形星座图被旋转缩放后的星座图。以如图30所示的分区为例，经过分区后，星座点被分成4部分，如图33所示，然后：
将分区1里面的星座点加起来，再除以该分区内星座点的数量，得到分区1的区星座点的如图34中的中心c1。
将分区2里面的星座点加起来，再除以该分区内星座点的数量，得到分区2的区星座点的如图34中的中心c2。
将分区3里面的星座点加起来，再除以该分区内星座点的数量，得到分区3的区星座点的如图34中的中心c3。
将分区4里面的星座点加起来，再除以该分区内星座点的数量，得到分区4的区星座点的如图34中的中心c4。
然后通过所有分区的星座点中心，就可以求得整个星座图的旋转缩放量，例如以第一种分区为例，即图26为例，设算得的4个分区的中心分别为c1，c2，c3，c4，则：
分区2的中心c2顺时针旋转90°得到c2′，也即c2′＝-c2*j；
分区3的中心顺时针旋转180°得到c3′，也即c3′＝-c3；
分区4的中心逆时针旋转90°得到c4′，也即c4′＝c4*j；
然后通过计算c＝(c1+c2′+c3′+c4′)/4，得到的复数c就可以作为整个星座图的旋转缩放量的一个估计。
存在AWGN时，有些调制符号受到的AWGN比较大时，可能会发生越区。为了更准确估计旋转缩放量，通常需要用到上述两种分区方法，然后针对每种分区分别按照上述方法计算星座图的旋转缩放量，然后两个旋转缩放量模值大的一个作为星座图的旋转缩放量。
对于如图25或图26那样的线性星座图，可以只用2个分区去计算星座图的旋转缩放量，例如，接收机通过x轴将二维信号平面分为2个分区后，分别将每个分区里面的星座点(每个星座点对应一个调制符号)加起来，再除以该分区内星座点的数量(即调制符号的数量)，所得的星座点，就是该分区星座点的中心。然后通过所有分区的星座点中心，就可以求得整个星座图的旋转缩放量，设算得的x轴右边，也即x＞＝0，对应的分区的中心为c1；x轴右边，也即x＜0，对应的分区的中心c2，则：分区2的中心c2顺时针旋转90°得到c2′，也即c2′＝-c2；
然后通过计算c＝(c1+c2′)/2，得到的复数c就可以作为整个星座图的旋转缩放量的一个 估计。
然后采用下面4种不同的2分区来计算得到4个旋转缩放量，最后4个旋转缩放量模值大的一个作为星座图的旋转缩放量。
1)以x轴为分区线，将二维信号平面分成的2个分区；
2)以y轴为分区线，将二维信号平面分成的2个分区；
3)以过原点的45°直线为分区线，将二维信号平面分成的2个分区；
4)以过原点的135°直线为分区线，将二维信号平面分成的2个分区。
接收机估计到星座图的旋转缩放量后，就可以将星座图所经历的旋转缩放均衡掉，得到没有畸变、只受AWGN影响的星座图。
Cell-free网络是新兴的移动网络形态，是未来提升移动通信体验的重要技术方向，越来越受到重视，本公开上述实施例解决了cell-free网络的多用户上行传输的性能问题。
通过以上的实施方式的描述，本领域的技术人员可以清楚地了解到根据上述实施例的方法可借助软件加必需的通用硬件平台的方式来实现，当然也可以通过硬件，但很多情况下前者是更佳的实施方式。基于这样的理解，本公开的技术方案本质上或者说对现有技术做出贡献的部分可以以软件产品的形式体现出来，该计算机软件产品存储在一个存储介质(如ROM/RAM、磁碟、光盘)中，包括若干指令用以使得一台第二节点设备(可以是手机，计算机，服务器，或者网络设备等)执行本公开各个实施例所述的方法。
在本实施例中还提供了一种信息传输设备，该装置用于实现上述实施例及优选实施方式，已经进行过说明的不再赘述。如以下所使用的，术语“模块”可以实现预定功能的软件和/或硬件的组合。尽管以下实施例所描述的装置较佳地以软件来实现，但是硬件，或者软件和硬件的组合的实现也是可能并被构想的。
图35是根据本公开实施例的信息传输设备的结构框图，如图35所示，该装置包括：
确定模块340，设置为确定W个极稀疏导频，其中，W为大于0的整数；
传输模块342，设置为将所述W个极稀疏导频和目标信息传输至无小区系统。
通过上述技术方案，由于可以将确定出的W个极稀疏导频和目标信息一起发送至无小区系统。可以解决相关技术中，无小区系统中无合适的导频进行使用的问题。进而可以向无小区系统发送合适的W个极稀疏导频供无小区系统使用。
在一个示例性实施例中，所述目标信息包括以下至少之一：UE_ID信息，UE类型信息，UE能力信息，UE的收发天线数量，UE支持的传输数据流数，1个或多个AP_ID信息，调度请求SR，缓存状态报告BSR，UE的位置信息。
在一个示例性实施例中，当所述目标信息包括所述信道状态信息时，所述信道状态信息包括如下至少之一：预编码矩阵指示；信道质量指示；秩指示；SSB资源指示；参考信号功率。
在无小区系统接收到上述目标信息后，这些信息可以协作cell-free系统更好地接入、调度、寻呼、UE移动性管理等，也有利于cell-free系统进行感知等应用。
举例说明，极稀疏导频加上包含UE_ID的信息，也就是极稀疏导频加上包含UE_ID的信息一起传给无小区系统，可以用来做随机接入，也就是“极稀疏导频加上包含UE_ID的信息”可以作为随机接入信道(RACH或PRACH)的Msg1。
cell-free系统(相当于无小区系统)如果沿用现有的随机接入方法会有较大的问题，这是因为现有的随机接入的Msg1，都是基于Zadoff-Chu(ZC)序列的：如果是4步RACH，则Msg1只包含一条ZC序列；如果是2步RACH，则Msg1包含一条ZC序列和一个数据包。
但如果要求AP去检测Msg1的ZC序列，并且基于Msg1的ZC序列做信道估计，则AP需要增加比较多的处理复杂度，这会增加AP的成本和功耗。另一方面，如果AP对于Msg1不做处理，而是将Msg1通过radio stripe front haul传给CPU，则所有AP的数据都需要分立地传给CPU，也就是M个AP的话，radio stripe front haul上就需要传输M个Msg1的信息。如果AP数目很大，则传输Msg1的传输占用radio stripe front haul较大的带宽。而且大量AP的Msg1传回给CPU，就要求CPU在短时间内处理完所有的Msg1，这对CPU来说也是很大的负担。
因为，本公开实施例的极稀疏导频加上包含UE_ID的信息作为随机接入信道(RACH或PRACH)的Msg1，这样AP可以沿用原来的简单信道估计及空域MRC合并操作，保持AP的简单和低功耗；radio stripe front haul也不用增加太多带宽，CPU也不用为Msg1增加太多处理复杂度。
在另一个实施例中，极稀疏导频加上包含UE_ID的信息也可以作为Cell-free系统中UE发送的“心跳信号”。辅助系统实现AP节能，UE移动性管理，导频分配，寻呼等功能。
在另一个实施例中，极稀疏导频加上包含UE能力信息可以用于系统与UE进行与UE能力相匹配的传输。
在另一个实施例中，极稀疏导频加上包含UE_ID及BSR的信息可以实现低信令开销、低时延的UE上行传输。当终端有上行数据传输时，可以直接给系统传输“极稀疏导频加上包含UE_ID及BSR的信息”，这样无小区系统收到后，就可以直接给UE指示一个上行传输资源，让UE将其数据传上来。
在另一个实施例中，极稀疏导频加上AP_ID信息可以辅助系统实现AP节能，UE移动性管理，导频分配，寻呼，感知等功能。
在另一个实施例中，极稀疏导频加上UE的位置信息可以辅助系统实现AP节能，UE移动性管理，导频分配，寻呼，感知等功能。
在一个示例性实施例中，传输模块，还用于在所述终端处于无连接状态下，将所述W个极稀疏导频和目标信息传输至无小区系统。
在一个示例性实施例中，在所述W个极稀疏导频中，每个极稀疏导频中只有U个符号是非零值，且U个非零值承载在时频上相邻的U个资源单元上，或者承载在时间上先后的U个符号上，或者承载在频域相邻子载波上的U个资源单元上，其中，U是大于0，且小于5。
在一个示例性实施例中，在所述W个极稀疏导频中，每个导频中的长度均大于24。
在一个示例性实施例中，所述U＝1。
在一个示例性实施例中，所述U＝2，且所述非零值[p1，p2]包括：[a1，a2]，或[b1，b2]，其中，[a1，a2]与[b1，b2]正交。
在一个示例性实施例中，所述U＝2，且所述非零值[p1，p2]的取值情况包括以下至少之一： [p1，p2]＝[1，1]；[p1，p2]＝[1，-1]；[p1，p2]＝[1，j]；[p1，p2]＝[1，-j]。
在一个示例性实施例中，所述U＝4，且4个非零取值[p1，p2，p3，p4]的取值情况包括以下至少之一：
[p1，p2，p3，p4]＝[a1，a2，a3，a4]；[p1，p2，p3，p4]＝[b1，b2，b3，b4]；[p1，p2，p3，p4]＝[c1，c2，c3，c4]；[p1，p2，p3，p4]＝[d1，d2，d3，d4]；其中，[a1，a2，a3，a4]，[b1，b2，b3，b4]，[c1，c2，c3，c4]，[d1，d2，d3，d4]互相正交。
在一个示例性实施例中，所述W大于1时，所述W个极稀疏导频是独立无关的。
在一个示例性实施例中，所述W个极稀疏导频是通过传输的数据包中的信息确定的。
在一个示例性实施例中，所述W个极稀疏导频是通过传输的数据包中的一个或多个比特确定的。
在一个示例性实施例中，每个极稀疏导频均来自一个包含D个极稀疏导频的导频集合，且每个极稀疏导频是通过传输的数据包中的log2(D)个比特从所述导频集合中确定。
在一个示例性实施例中，所述W取值为2或1。
需要说明的是，上述各个模块是可以通过软件或硬件来实现的，对于后者，可以通过以下方式实现，但不限于此：上述模块均位于同一处理器中；或者，上述各个模块以任意组合的形式分别位于不同的处理器中。
本公开的实施例还提供了一种计算机可读存储介质，该计算机可读存储介质中存储有计算机程序，其中，该计算机程序被设置为运行时执行上述任一项方法实施例中的步骤。
在一个示例性实施例中，上述计算机可读存储介质可以包括但不限于：U盘、只读存储器(Read-Only Memory，简称为ROM)、随机存取存储器(Random Access Memory，简称为RAM)、移动硬盘、磁碟或者光盘等各种可以存储计算机程序的介质。
本公开的实施例还提供了一种电子装置，包括存储器和处理器，该存储器中存储有计算机程序，该处理器被设置为运行计算机程序以执行上述任一项方法实施例中的步骤。
在一个示例性实施例中，上述电子装置还可以包括传输设备以及输入输出设备，其中，该传输设备和上述处理器连接，该输入输出设备和上述处理器连接。
本实施例中的具体示例可以参考上述实施例及示例性实施方式中所描述的示例，本实施例在此不再赘述。
显然，本领域的技术人员应该明白，上述的本公开的各模块或各步骤可以用通用的计算装置来实现，它们可以集中在单个的计算装置上，或者分布在多个计算装置所组成的网络上，它们可以用计算装置可执行的程序代码来实现，从而，可以将它们存储在存储装置中由计算装置来执行，并且在某些情况下，可以以不同于此处的顺序执行所示出或描述的步骤，或者将它们分别制作成各个集成电路模块，或者将它们中的多个模块或步骤制作成单个集成电路模块来实现。这样，本公开不限制于任何特定的硬件和软件结合。
以上所述仅为本公开的优选实施例而已，并不用于限制本公开，对于本领域的技术人员 来说，本公开可以有各种更改和变化。凡在本公开的原则之内，所作的任何修改、等同替换、改进等，均应包含在本公开的保护范围之内。

Claims (17)

  1. 一种信息传输方法，其特征在于，应用于终端，包括：
    确定W个极稀疏导频，其中，W为大于0的整数；
    将所述W个极稀疏导频和目标信息传输至无小区系统。
  2. 根据权利要求1所述的方法，其中，所述方法还包括：
    所述目标信息包括以下至少之一：UE_ID信息，UE类型信息，UE能力信息，UE的收发天线数量，UE支持的传输数据流数，调度请求SR，缓存状态报告BSR，UE的位置信息，1个或多个AP_ID信息，1个或多个AP到终端的信道状态信息CSI。
  3. 根据权利要求2所述的方法，其中，当所述目标信息包括所述信道状态信息时，所述信道状态信息包括如下至少之一：
    预编码矩阵指示；
    信道质量指示；
    秩指示；
    SSB资源指示；
    参考信号功率。
  4. 根据权利要求1所述的方法，其中，所述方法还包括：
    在所述W个极稀疏导频中，每个极稀疏导频中只有U个符号是非零值，且U个非零值承载在时频上相邻的U个资源单元上，或者承载在时间上先后的U个符号上，或者承载在频域相邻子载波上的U个资源单元上，其中，U是大于0，且小于5。
  5. 根据权利要求4所述的方法，其中，所述方法还包括：
    在所述W个极稀疏导频中，每个导频中的长度均大于24。
  6. 根据权利要求4所述的方法，其中，所述方法还包括：
    所述U＝1。
  7. 根据权利要求4所述的方法，其中，所述方法还包括：
    所述U＝2，且所述非零值[p1，p2]包括：[a1，a2]，或[b1，b2]，其中，[a1，a2]与[b1，b2]正交。
  8. 根据权利要求4所述的方法，其中，所述方法还包括：
    所述U＝2，且所述非零值[p1，p2]的取值情况包括以下至少之一：
    [p1，p2]＝[1，1]；
    [p1，p2]＝[1，-1]；
    [p1，p2]＝[1，j]；
    [p1，p2]＝[1，-j]。
  9. 根据权利要求4所述的方法，其中，所述方法还包括：
    所述U＝4，且4个非零取值[p1，p2，p3，p4]的取值情况包括以下至少之一：
    [p1，p2，p3，p4]＝[a1，a2，a3，a4]；
    [p1，p2，p3，p4]＝[b1，b2，b3，b4]；
    [p1，p2，p3，p4]＝[c1，c2，c3，c4]；
    [p1，p2，p3，p4]＝[d1，d2，d3，d4]；其中，[a1，a2，a3，a4]，[b1，b2，b3，b4]，[c1，c2，c3，c4]，[d1，d2，d3，d4]互相正交。
  10. 根据权利要求1所述的方法，其中，所述方法还包括：
    所述W大于1时，所述W个极稀疏导频是独立无关的。
  11. 根据权利要求1所述的方法，其中，所述方法还包括：
    所述W个极稀疏导频是通过传输的数据包中的信息确定的。
  12. 根据权利要求11所述的方法，其中，所述方法还包括：
    所述W个极稀疏导频是通过传输的数据包中的一个或多个比特确定的。
  13. 根据权利要求1所述的方法，其中，
    每个极稀疏导频均来自一个包含D个极稀疏导频的导频集合，且每个极稀疏导频是通过传输的数据包中的log2(D)个比特从所述导频集合中确定。
  14. 根据权利要求1所述的方法，其中，
    所述W取值为2或1。
  15. 一种信息传输设备，包括：
    确定模块，设置为确定W个极稀疏导频，其中，W为大于0的整数；
    传输模块，设置为将所述W个极稀疏导频和目标信息传输至无小区系统。
  16. 一种计算机可读的存储介质，所述存储介质中存储有计算机程序，其中，所述计算机程序被设置为运行时执行所述权利要求1至14任一项中所述的方法。
  17. 一种电子装置，包括存储器和处理器，所述存储器中存储有计算机程序，所述处理器被设置为运行所述计算机程序以执行所述权利要求1至14任一项中所述的方法。
PCT/CN2023/134475 2022-11-30 2023-11-27 信息传输方法及装置、存储介质、电子装置 Ceased WO2024114603A1 (zh)

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