EP0113901A2 - Filtre de mode - Google Patents

Filtre de mode Download PDF

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Publication number
EP0113901A2
EP0113901A2 EP83112784A EP83112784A EP0113901A2 EP 0113901 A2 EP0113901 A2 EP 0113901A2 EP 83112784 A EP83112784 A EP 83112784A EP 83112784 A EP83112784 A EP 83112784A EP 0113901 A2 EP0113901 A2 EP 0113901A2
Authority
EP
European Patent Office
Prior art keywords
waveguide
wave
inner conductor
switch according
type switch
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP83112784A
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German (de)
English (en)
Other versions
EP0113901A3 (en
EP0113901B1 (fr
Inventor
Eberhardt Dr.-Ing. Schuegraf
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Siemens AG
Siemens Corp
Original Assignee
Siemens AG
Siemens Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from DE19828236106 external-priority patent/DE8236106U1/de
Application filed by Siemens AG, Siemens Corp filed Critical Siemens AG
Priority to AT83112784T priority Critical patent/ATE61498T1/de
Publication of EP0113901A2 publication Critical patent/EP0113901A2/fr
Publication of EP0113901A3 publication Critical patent/EP0113901A3/de
Application granted granted Critical
Publication of EP0113901B1 publication Critical patent/EP0113901B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/16—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H01Q25/04—Multimode antennas

Definitions

  • the invention relates to a wave type switch for the selective coupling out of certain wave types from a waveguide, in particular a round waveguide.
  • a wave-type-selective coupling is achieved.
  • One method is that the type of wave to be coupled out of the waveguide at at least two points on the circumference, e.g. of a circular waveguide, usually not fully broken down into a corresponding number of partial waves, but is only partially coupled in consideration of the signal waves that also couple here and continue to travel in the waveguide.
  • the partial waves of the wave type to be decoupled are then ideally completely recombined - that is, only after the actual coupling process - in their phase position, which only corresponds to this wave type, with an especially necessary microwave network, which is designed in the manner of a bridge circuit.
  • those of other types of waves e.g.
  • the second method of wave-type-selective coupling is based on the fact that the wave-type to be coupled out of the waveguide is coupled with one of its field strengths Components of such a type and at such a location of the waveguide that none of the wave types to be excluded from the decoupling process has the same field strength component.
  • This method which is called field-selective in the following, makes the coupling process itself wave-type-selective, independent of the frequency, and avoids any direct influence on other wave types, for example the signal waves traveling on in the waveguide.
  • the field-selective coupling method if it can be used at all in terms of the field configuration, can usually be implemented with relatively simple means and has the better electrical properties compared to the network-selective method.
  • an E 01 - H 11 -wave type switch in which the E 01 shaft used as a DF shaft is decoupled from a circular waveguide by means of a coaxial line with an extended inner conductor (longitudinal probe).
  • This longitudinal probe is arranged in the central longitudinal axis of the circular waveguide adjoining the antenna.
  • the capacitive longitudinal probe on the axis of this crossover waveguide is completely decoupled from the H 11 waves of any polarization, for example, and without any selection network.
  • E 01 - H 11 crossovers are only able to do this with circular polarization of the signal waves, uie to provide complete information about the storage of the main beam direction of an antenna from the radiation source, for example a satellite.
  • the wave-type-selective coupling of the H21 wave and the H 01 wave in the circular waveguide as well as the H 20 , H 02 and E 11 waves in the square waveguide is of direct technical importance, since these wave types are zero when the signal waves are incident axially with 180 0- phase jump and their amplitudes for small deposits are proportional to the deposit angle. Furthermore, in certain combinations they are suitable for supplying the complete storage information even in the case of linear polarization of the signal waves.
  • H 21A and H 21B waves are understood to mean two mutually orthogonal H 21 waves.
  • E 01 + H 01 - and the H 21A + H 21B Duo are characterized by the above-mentioned combinations in that they provide the complete storage information regardless of the position of the polarization plane of the signal waves.
  • the double switches for these last two combinations of wave types do not need to be rotated when the polarization plane varies.
  • the invention has for its object to provide new and simple wave type decoupling options, so that usable for linearly polarized signal waves double switches for each individual wave type to be coupled out of the waveguide and in the waveguide signal waves to be guided essentially meet the requirements of a completely field-selective decoupling, as is already the case according to the arrangement according to DE-OS 28 04 132 for the E 01 -H 11 switches for operation with circular double polarization.
  • the wave type switch according to the invention should be implemented in such a way that the decoupling of two DF shaft types to be decoupled from one another is at least 20 dB.
  • a hollow inner conductor is attached in a section of the waveguide, that the inner conductor on one or more , with regard to the field of the respective shaft to be coupled out, has coupling elements which are geometrically suitably selected and which couple into the interior of the hollow inner conductor and which, in terms of their geometrically reduced size, correspond to those coupling elements which are also applied or applicable to the outer side of the waveguide - coupling there reversely to the outside - and that the outcoupled partial waves, each converted into a different line wave type, are recombined starting from the coupling elements and are led out into the space outside the waveguide.
  • the hollow inner conductor When coupling out certain types of wave (H 01 wave) in the circular waveguide, it is advantageous to arrange the hollow inner conductor coaxially with the central longitudinal axis of the waveguide. In addition, in most cases there are more favorable results if the cross-sectional dimensions of the hollow inner conductor in the Compared to the cross-sectional dimensions of the waveguide are small. In the case of a round waveguide, this means that the diameter of the hollow round inner conductor is small in comparison to the inner diameter D of the round waveguide, for example D / d e5.5.
  • a central conductor is advantageously provided in the hollow inner conductor on its longitudinal axis, so that the hollow inner conductor and the central conductor running in it result in a coaxial inner line within the hollow conductor.
  • the respective decoupled shaft can be led out via this coaxial inner line after the conversion into the coaxial basic shaft type.
  • a not only field-selective, but also network-selective mode switch according to the invention can be created if, for the interconnection of several coupling elements, a line network is arranged inside the hollow inner conductor, consisting of combination lines, the combination lines of which originate from a coupling element. These combination lines can then, at their ends facing away from the coupling elements, run geometrically directly into a star point, which is located on the longitudinal axis of the inner conductor, on which the central conductor is optionally arranged and connected to the star point.
  • a resonance slot running axially in the inner conductor wall is provided, on the one long side of which a conductive sheet metal is fastened to the inner conductor wall, which is attached to it opposite side is mechanically and electrically connected to the central conductor running in the inner conductor.
  • the inner conductor wall can also have one or more axially extending resonance slots which, in their entirety, are arranged uniformly distributed around the circumference of the inner conductor.
  • the H0 1 coupler has a conductive plate attached to the longitudinal side of the slot, which is always on the same side with respect to the slot, on the inner conductor wall directly at the edge of the slot, which is mechanically and electrically connected on the opposite side to the Inner conductor extending central conductor is connected.
  • the coupling elements are arranged at a short distance that results in a maximum coupling, for example ⁇ H / 4, in front of such a waveguide region in which the cross section of the waveguide tapers or abruptly narrows in such a way that the wave type decoupled by means of the coupling elements no longer is spreadable as a wave.
  • the hollow inner conductor is expediently held exactly in the center of the waveguide by means of several support struts.
  • One of these support struts can then be used to lead the respective wave type to be coupled out and converted out of the waveguide.
  • the H 01 internal coupler can be integrated with certain polarization switches that have a free center, so that the coaxial line can be led out undisturbed to the rear.
  • the waveguide wall is abandoned when searching for new field-selective coupling possibilities.
  • the following solution is found.
  • H 01 shaft completely on the circular waveguide axis by coupling only with the H z component, for example with respect to the H 11 waves, that is to say completely or independently of them.
  • This H 01 coupling is also completely field-selective compared to the E 01 wave, because this, like the H 11 waves of any polarization, has no magnetic longitudinal field strength on the waveguide axis.
  • the H curve results for the H 11 wave by multiplying the H z curve in FIG. 1 by cos ⁇ and in the H 21 wave by the factor cos 2 ⁇ .
  • the invention is now based on the pure H z coupling found to be opportune on the waveguide axis or in space close to the axis.
  • the practical implementation of this coupling according to the invention consists in the idea of inserting a metallic inner conductor in sections into the previously empty, round waveguide (round waveguide), the diameter d of which is small compared to the outer inner diameter D of the now coaxial waveguide, for example about d ⁇ D / 5.
  • Such an inner conductor only slightly changes the field states of the individual H-wave types only in the vicinity of the inner conductor and in no way fundamentally.
  • the field strength components on the inner conductor surface adapt to the known laws, according to which the electric field must be perpendicular to the conductor surface and the magnetic field must run parallel to it.
  • the progress that can be achieved with the introduction of the inner conductor coupler according to the invention can be summarized as follows.
  • the interconnection of several coupling points is possible with the inner conductor coupler with cable lengths that are more than an order of magnitude shorter than with the previous outer coupler; as the combination of lines running from its origin at the respective coupling point starting directly toward and therefore on shortest paths ( ⁇ 0/10 and below), are connected together in a star point as in Figure 3, on the axis of the inner conductor, for example.
  • Such a circuit acts, as will be explained later on using the example, in a very simple manner and with very little frequency dependence on the network.
  • the very short line lengths in the inner selection network have the further advantage that the individual coupling elements only act on the wave types that are not to be coupled with the sum of their pure reactances, i.e. without the long, short additional external cables at the end.
  • These pure reactances have a significantly lower frequency response than in the known external coupler and can therefore be compensated for in broadband, even if the individual coupling element with partially or only weakly field-selective arrangements for the purpose of complete decoupling of the requested wave type also with the wave type not to be decoupled is strongly coupled.
  • This means that the type of wave to be decoupled is almost completely available at the turnout output and nevertheless the reactance effect exerted by the strong coupling on the type of wave not to be decoupled can be compensated for. It even seems possible that this reactance for the wave type not to be coupled can be used to create other reactances for this wave type, e.g. the post crosses according to DE-OS 28 04 132, to compensate at least partially.
  • the inner conductor In switches designed according to the invention, the inner conductor must be held in its exactly central position with a holding device.
  • the DF shaft type or two after conversion e.g. into the form of the coaxial fundamental wave inside the inner conductor for further use in the space outside the outer conductor of the coaxial waveguide.
  • an inner conductor holder with coaxial lead-out with good properties e.g. according to the principles and exemplary embodiments shown in DE-OS 28 04 132.
  • This H 01 coaxial wave converter consists of a relatively short, outer tubular conductor 1, which can be seen in the foreground of FIG.
  • This outer pipe conductor 1 is initially closed at the rear by a metallic plate 2.
  • the function of this short-circuit plate 2 can be replaced at any time for the H 01 shaft in the circular waveguide by a conical or abrupt transition to a narrower circular waveguide, in which the H 01 field can only be damped aperiodically in the frequency range under consideration, while the H 11 -wave is still well spreadable even in the narrower circular waveguide.
  • the H 01 coaxial shaft transition is expanded to an H 01 -H 11 shaft type switch.
  • Such a wave-type switch is shown in FIG. 5, which will be explained later.
  • An inner conductor 4 is pushed through an axial bore 3 in the short-circuit plate 2 of the arrangement according to FIG.
  • a central conductor 5 is accommodated coaxially inside this inner waveguide 4.
  • This central conductor 5 - hereinafter referred to as coaxial inner conductor 5 - is conductively connected to a transverse plate 6 which branches symmetrically to the left and right as a band-shaped inner conductor.
  • the strip conductor-like sheet 6 runs along the horizontal inner diameter in the inner waveguide 4 and is conductively connected to the inner wall of the inner waveguide 4 on two diametrically opposite longitudinal lines.
  • this current of the coaxial inner conductor 5 branches into two equal partial flows, which continue to flow to the right or left on the transverse plate 6 to the inner wall of the inner waveguide 4.
  • Each of these partial currents flows half according to its origin, for example from the upper semicircle of the inner conductor 5 visible in FIG. 2 on the upper surface of the transverse plate 6, while the other half flows on the lower surface of the plate.
  • Two longitudinal slots 7 and 8 visible in FIG. 2 in the wall of the inner waveguide 4 are thought to be temporarily closed in a conductive manner.
  • the currents of the transverse plate 6 then meet the inner wall of the inner waveguide 4, the currents flowing on the upper side of the plate 6 from the right and left to the wall are deflected upwards and the currents on the underside of the plate 6 downwards.
  • the currents flow circumferentially upwards and downwards on both sides of the sheet, then bend continuously backwards in the longitudinal direction and are finally distributed in quadrants evenly over the circumference of the inner surface of the inner waveguide 4.
  • Fig. 2 shows a coupling arrangement with two longitudinal slots 7 and 8 in the inner shaft wall 4, namely the left slot 7 runs directly above the current-carrying cross plate 6, the right slot 8, however, immediately below.
  • the diameter on which the coupling slots 7 and 8 lie diametrically opposite one another thus has a slight oblique position, but this is insignificant because of the rotational symmetry of the H 01 shaft type to be excited.
  • a vertically polarized H 11v wave in the arrangement according to FIG. 2 excites the individual resonance slots 7 and 8, respectively, with its wall currents flowing on the inner waveguide 4, which meet the resonance slots 7 and 8 transversely, but advantageously in relation to the H 01 wave with a much smaller amplitude.
  • This is shown by the H z comparison in FIG. 1 with the same power of these two shaft types.
  • the second part of the H 11v decoupling is based on the fact that the H z components of the H 11v wave are directed opposite one another at the location of the two resonance slots 7 and 8.
  • the currents passing from the two resonance slots 7 and 8 to the transverse plate 6 and directed towards the tube axis then always have the same direction and, in the case of a symmetrical structure, the same amplitude in accordance with the flow law. Therefore, these radial currents on the transverse plate 6 are always mutually equal, and there is no differential current that could flow backwards on the coaxial inner conductor 5, ie the fundamental wave of the coaxial line is completely decoupled from the H 11v wave.
  • the partial waves of the H 11v wave emanating from the two resonance slots 7 and 8 are in phase opposition to one another.
  • Your electrical field strengths therefore meet in the Putties always facing each other on both the top and bottom of the cross plate 6.
  • the electric fields of both partial waves therefore always cancel each other out in the vertical longitudinal section plane running through the axis. There is a zero point of the resulting electric field strength, ie a spatially stationary short-circuit plane is created, so that the coaxial fundamental wave cannot be excited in the coaxial line connected here.
  • the cross plate 6 is a prime example of a very simple, but nevertheless very effective, internal selection network.
  • H z components which have the same direction in the area of the two resonance slots 7 and 8, produce oppositely directed radial currents on the transverse plate 6.
  • the maximum differential current - that is the scalar sum of these two radial currents - forces an optimal excitation of the coaxial line wave.
  • the H Z components of the H 11v shaft which are oppositely directed at the resonance slots 7 and 8, always produce radial currents in the same direction on the transverse plate, which compensate one another on the transverse plate 6 without a coaxial differential current.
  • the equalizing current flowing on the transverse plate 6 leads to the excitation of an H 11 field inside the inner waveguide 4, ie to a reduced image of the generating H 11v wave in the outer, coaxial waveguide 1. Since the outer waveguide 1 with its H 01 or H11 cutoff frequency determines the operating frequency range, the much thinner inner waveguide 4 provides a strong aperiodic damping for the H 11 field generated in it. In addition to this physical reason for the high decoupling of the H 11 wave from the fundamental wave of the coaxial line, it should be pointed out that the Coaxial line 4.5 still spreading H 11 field remains are totally decoupled from the coaxial fundamental wave.
  • This reactance is represented by the parallel connection of the pure resonance slot 7 or 8 and the inhomogeneous line system connected to it in the inner waveguide 4, consisting of the right or left half of the transverse plate 6 in FIG. 2 and the inner surface of the right or left half cylinder on the inner wall of the inner waveguide 4.
  • the two mutually identical resonance slots 7 and 8 each behave in the vicinity of their resonance like a strongly damped parallel resonance circuit. They are therefore high-impedance, so that the wall currents striking the resonance slot 7 or 8 are only approximately the reactance at the input of the above inner conduit system in the inner waveguide 4.
  • This inner line system is formed from the inner surface of the right half cylinder of the inner shaft conductor 4 as the "outer conductor” and the respective half of the transverse plate 6 as the “inner conductor”. This line system is short-circuited at the end, specifically in the arrangement of FIG. 2 in the vertical longitudinal section plane running through the axis.
  • the H 11v wall currents on the inner waveguide 4 are not disturbed when the short circuit prevailing in the central plane is transformed via the inner line system to the location of the resonance slots 7 and 8. This is ereicht at operating frequencies at which half the length of the dash panel 1 r 6 either is small compared with the wavelength - about l r ⁇ o / 10 -, or r 1 ⁇ 0 .A n / 2.
  • n the spatial position of the return locations of this short circuit varies more and more when the frequency changes.
  • This influence on the wall currents of the H 11v wave is alleviated by the fact that, due to the slot length 1 s > 2 1 r, the slot resonance is far below the H 11v reflection maximum, and therefore the slot 7 or 8 is no longer high-impedance here.
  • the H 01 coaxial wave converter according to FIG. 2 can be expanded in the following way to an H 01 - H 11 partial wave crossover, as shown in an oblique view in FIG. 5.
  • the short-circuiting plate 2 in the background of the arrangement according to FIG 5 by a sudden, continuous or stepped transition 16 to a waveguide 17. or waveguide such that only an aperiodically decaying H 01 field can propagate in this continuing waveguide 17, while H 11 - Waves here far enough above their cut-off frequency, and therefore can propagate undamped aperiodically.
  • Such transitions are dimensioned according to known principles.
  • the inner waveguide 4 is either extended to the rear until it is possible at a suitable termination, for example on a polarization switch with a free center, to lead the coaxial line out of the waveguide using the converted H 01 wave. If this is not possible due to the interposition and the pulling through of a shaft inner conductor 4 which complicates elements such as manifolds, the shaft inner conductor 4 is kept as short as possible and is held in its central position with struts extending radially or obliquely to the outer conductor 1. These struts, which are also suitable for leading the inner coaxial line out, can be dimensioned according to the principles set out in DE-OS 28 02 132.
  • the resulting H 01 -H 11 crossover is not exactly rotationally symmetrical with respect to any polarized H 11 waves, although the degree of asymmetry is due to differences in reflection (see H 11v - or H 11h Behavior) and in the electrical length of the switch passage paths for orthogonal H 11 waves, because of the relatively very low coupling of the H 11 waves (FIG. 1) is not high.
  • this asymmetry becomes smaller in the H 01- H 11 switch with two resonance slots 7 and 8 according to FIG. 2, the thinner the inner waveguide 4 is made compared to the outer conductor 1 of the coaxial waveguide.
  • Absolute rotational symmetry is achieved with the H 01 -H 11 switch outlined in an oblique view in FIG. 3, even with relatively large diameters of the inner waveguide 4.
  • the switch in FIG. 3 works on the same principle of field-selective H coupling as the switch in Fig.2.
  • a vertical cross plate 9 likewise consisting of two halves 9 ′ and 9 ′′ is introduced in the arrangement according to FIG. 3, which is contacted in the same way with the inner conductor 5 of the rearward coaxial line as the horizontal transverse plate 6.
  • the newly added, vertical transverse plate 9 feeds two further resonance slots 10 and 11 in the wall of the inner shaft conductor 4.
  • the upper resonance slot 10 is shown in FIG. 3 immediately to the right of the transverse sheet metal section 9 ′ and the lower slot 11 to the left of the transverse sheet metal section 9 ′′.
  • the four resonance slots 7, 8, 10 and 11 in FIG. 3 thus lie on the same side of their respective cross from the tube axis sheet section.
  • a current coming from behind on the central coaxial inner conductor 5 is due to the symmetry of the arrangement in four mutually equally strong and in-phase partial currents on the four radially outwardly extending sheet metal sections 6; 6 ", 9 'and 9" split.
  • each H z - Excite components of the same strength and direction.
  • This field configuration in turn corresponds to that of the H 01 wave of the round, coaxial waveguide.
  • the switch according to FIG. 3 behaves exactly the same with respect to horizontally polarized H 11 h waves as with vertically polarized H 11v waves, namely as described for the switch according to FIG. 2 for H 11v waves .
  • the arrangement according to FIG. 3 thus represents a completely rotationally symmetrical H 01 -H 11 switch with regard to reflection and electrical length for arbitrarily polarized H 11 waves.
  • any depolarization is linear or circular polarized H 11 waves excluded.
  • the turnout arrangement according to FIG. 3 is particularly suitable for higher frequencies and at very high frequencies Decoupling requirements between dual circular polarizations.
  • the switch according to Figure 3 has the following new property.
  • the crossed transverse plates 6 and 9 of this switch act not only as an internal selection network for H 11 waves of any polarization, but also with respect to the H 21 wave.
  • the H 21 wave On the outer surface of the inner waveguide 4, the H 21 wave has, at diametrically opposite locations, H z components of mutually equal strength and direction.
  • H Z components which according to FIG. 1 are very small in comparison to those of the H 01 shaft, would in themselves be capable of a small differential current through the two resonance slots 7, 8 of the one, for example horizontal, transverse plate 6 to generate in the coaxial line.
  • the coupler according to FIG. 2 the H 21 selectivity of which is “only” based on the field-selective effect which can be seen, for example, from FIG.
  • the H 21 wave with its second pair of H z components in front of the two resonance slots 10 and 11 of the other, for example, vertical transverse plate 9 produces a differential current which is just as small as the two H components considered first. Since the first and the second H z component pair in the H 21 wave have the same amplitude but always opposite directions, as is the case with any H21 polarization from the H 21 field image of the coaxial waveguide, this also applies to the corresponding ones Residual currents. These differential currents, which flow in one and the same coaxial line, therefore always cancel each other out.
  • the H 21 wave is thus decoupled from the coaxial line not only with its bare field selectivity, depending on the diameter of the inner waveguide 4, but also with the network selectivity that the crossed transverse plates 6 and 9 have over the crossover according to FIG H 21 wave is coming.
  • This network selectivity is arbitrarily high with full symmetry of the arrangement.
  • a fundamental change in function namely to the H 21 coaxial wave converter, can be brought about with the following simple change.
  • Both resonance slots of one and the same, any transverse plate 6 or 9 are attached to the position shown in Figure 3 on the other side of this transverse plate 9 or 6.
  • a primary current from the coaxial line then generates in the coaxial waveguide 4.1 in front of the resonance slots 7, 8, 10 and 11 H Z components which have alternating directions in a cyclic order.
  • This H z configuration now matches the H 21 wave that is excited.
  • this alternating H z component sequence is contrary to the H 01 wave and also to H 11 waves of any polarization.
  • This modified inner selection network now couples the H 21 wave to the coaxial line 5.4 and decouples it from the H 01 wave and from all H 11 waves.
  • the network selectivity is reduced here by a negative contribution by "field selectivity", since an H 01 wave running in the coaxial waveguide according to FIG. 1 still excites the individual resonance slots 7, 8, 10 and 11 much more strongly than the H 21 - Wave.
  • the tubular conductor 1 is not terminated by a metallic short-circuit plate, as in the example according to FIG. 2, but rather passes over to a narrower circular waveguide 17 by means of a conical transition piece 16.
  • this narrower circular waveguide 17 for example, the H 01 field can only spread aperiodically damped, whereas the H 11 wave can still propagate well there.

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EP19830112784 1982-12-22 1983-12-19 Filtre de mode Expired - Lifetime EP0113901B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT83112784T ATE61498T1 (de) 1982-12-22 1983-12-19 Wellentypenweiche.

Applications Claiming Priority (5)

Application Number Priority Date Filing Date Title
DE8236106U 1982-12-22
DE19823247592 DE3247592A1 (de) 1982-12-22 1982-12-22 Wellentypenweiche
DE3247592 1982-12-22
DE19828236112 DE8236112U1 (de) 1982-12-22 1982-12-22 Wellentypenweiche
DE19828236106 DE8236106U1 (de) 1982-12-22 1982-12-22 Wellentypenweiche

Publications (3)

Publication Number Publication Date
EP0113901A2 true EP0113901A2 (fr) 1984-07-25
EP0113901A3 EP0113901A3 (en) 1986-03-26
EP0113901B1 EP0113901B1 (fr) 1991-03-06

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ID=27190591

Family Applications (1)

Application Number Title Priority Date Filing Date
EP19830112784 Expired - Lifetime EP0113901B1 (fr) 1982-12-22 1983-12-19 Filtre de mode

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EP (1) EP0113901B1 (fr)
DE (2) DE3247592A1 (fr)

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4212871A1 (de) * 1992-04-16 1993-10-21 Hirschmann Richard Gmbh Co Anordnung zum Ein- oder Auskoppeln von Wellen in ein oder aus einem Koaxialleitungssystem
US9531048B2 (en) 2013-03-13 2016-12-27 Space Systems/Loral, Llc Mode filter

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4038837C2 (de) * 1990-12-06 1995-05-11 Kernforschungsz Karlsruhe Helixförmig berandete Aperturantenne

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE1076208B (de) * 1958-09-29 1960-02-25 Siemens Ag Koppelvorrichtung fuer einen Koaxialleitungsabschnitt
DE1154842B (de) * 1959-06-02 1963-09-26 Philips Nv Einrichtung mit einer koaxialen Leitung
US3815136A (en) * 1972-09-11 1974-06-04 Philco Ford Corp Coaxial tracking signal coupler for antenna feed horn

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4212871A1 (de) * 1992-04-16 1993-10-21 Hirschmann Richard Gmbh Co Anordnung zum Ein- oder Auskoppeln von Wellen in ein oder aus einem Koaxialleitungssystem
US9531048B2 (en) 2013-03-13 2016-12-27 Space Systems/Loral, Llc Mode filter

Also Published As

Publication number Publication date
DE8236112U1 (de) 1986-04-10
DE3247592A1 (de) 1984-06-28
EP0113901A3 (en) 1986-03-26
EP0113901B1 (fr) 1991-03-06

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