EP0452716A2 - Appareil pour la régulation continue des dispositifs électriques suivant le principe de découpage de phase, notamment régulateur de luninosité, et l'utilisation d'un tel appareil - Google Patents

Appareil pour la régulation continue des dispositifs électriques suivant le principe de découpage de phase, notamment régulateur de luninosité, et l'utilisation d'un tel appareil Download PDF

Info

Publication number: EP0452716A2
Authority: EP; European Patent Office
Prior art keywords: ignition pulse; switching element; semiconductor switching; switched; generator circuit
Prior art date: 1990-04-17
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.): Granted

Application number

EP91104831A

Other languages

German (de)

English (en)

Other versions

EP0452716A3 (en

EP0452716B1 (fr

Inventor

Dieter Dr. Draxelmayr

Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)

Siemens AG

Siemens Corp

Original Assignee

Siemens AG

Siemens Corp

Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)

1990-04-17

Filing date

1991-03-26

Publication date

1991-10-23

1991-03-26 Application filed by Siemens AG, Siemens Corp filed Critical Siemens AG

1991-10-23 Publication of EP0452716A2 publication Critical patent/EP0452716A2/fr

1992-03-11 Publication of EP0452716A3 publication Critical patent/EP0452716A3/de

1994-07-27 Application granted granted Critical

1994-07-27 Publication of EP0452716B1 publication Critical patent/EP0452716B1/fr

2011-03-26 Anticipated expiration legal-status Critical

Status Expired - Lifetime legal-status Critical Current

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Classifications

- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B39/00—Circuit arrangements or apparatus for operating incandescent light sources
- H05B39/04—Controlling
- H05B39/08—Controlling by shifting phase of trigger voltage applied to gas-filled controlling tubes also in controlled semiconductor devices

Definitions

the invention relates to a device for the stepless control of electrical consumers according to the leading edge principle according to the preamble of claim 1 and the use of such a device.
Devices for the stepless control of electrical consumers according to the phase gating principle are known in principle and are described, inter alia, in DE-OS 23 62 225, DE-PS 24 29 763, DE-PS 25 43 370 and the article "electronic brightness controller with touch button" by Kern / Strehle, 8136 Component Report Siemens, year 15 / no. 5 (1977.10), pages 168 to 170.
Such devices usually have a semiconductor switching element, for example a triac, in the main current path. This semiconductor switching element is controlled by ignition pulses, so that the current in the main current path or the output current of this control device can be controlled as a function of the phase angle of the ignition pulse.
DE-OS 38 36 128 shows a brightness control circuit for incandescent lamps, a self-blocking field-effect transistor being provided instead of a triac.
a transformer can be provided to convert the voltage.
the control device feeds the primary winding of the transformer as if the primary winding was a normal load.
the actual load operated with a different operating voltage is then arranged in the secondary circuit of this transformer.
Such a burden can be, for example, a halogen lamp which is operated at low voltage and is fed from a public network with, for example, 220 V AC voltage via a transformer and can be steplessly controlled by a control device.
a heat sensor being arranged on the transformer, for example, which prevents further ignition pulses on the control device when a permissible transformer temperature is exceeded. It is also conceivable to detect the current flowing in the electrical consumer and to switch it off when a permissible maximum current is exceeded.
DE-OS 38 39 373 describes a brightness control circuit according to DE 38 36 128 with a protection and limiting circuit, the output current of the brightness control circuit being measured and being switched off when a limit value is exceeded.
protective circuits do not always respond reliably in the event of a malfunction in the event of an unfavorable current conduction angle.
a reliable circuit of this type contains a fuse, which must be replaced in the event of a lamp failure, so that such a circuit is very uncomfortable.
a device with a semiconductor switching element for the stepless control of electrical consumers according to the phase gating principle is conceivable, which switches off safely at high currents caused by the type of load, without the need to replace a fuse.
further control of the semiconductor switching element is prevented when the current flow duration of a half-wave exceeds a predetermined, maximum permissible value.
an impermissibly high current only occurs in one half-wave, which usually does not yet lead to the destruction of components.
the object of the invention is to improve known devices for controlling electrical consumers in such a way that the above-mentioned faults can be prevented with sufficient certainty without an impermissibly high current flowing.
the invention is based on the consideration that impermissibly high currents due to an inductive load component when the load is controlled by a device with a semiconductor switching element for the stepless control of electrical consumers according to the phase gating principle can only occur if the period of time during which a semiconductor contained in the control device occurs Switching element leads a current corresponding to a current half-wave exceeds a value based on the supply voltage to be controlled, which corresponds to an angle of 180 °.
a device recognizes these two circumstances before the corresponding drive pulses are switched to the semiconductor switching element and can thus prevent the semiconductor switching element from being driven before a disturbingly large current flows.
control device may be desirable for the control device to automatically check the load state after an interruption of the control in the event of a load-related malfunction to be expected and for the control to automatically resume when an allowable load state is present. It may also be desirable for the control device to automatically carry out a certain number of start-up attempts after the control has been interrupted, however, after several unsuccessful start-up attempts, i.e. if the load condition has not normalized within a certain period of time, a further start-up is only possible through external action. It may also be necessary to switch on manually after a fault.
a control device can be designed so that it can either be switched on again only by external action after the control of the semiconductor switching element has been interrupted, or that it switches on again automatically when it detects a normal load state, or that it is present over a certain period of time when an impermissible load state is present no longer switches on automatically but must be switched on by external action.
an AC voltage source U feeds an electrical consumer 2.
a transformer 3 is shown here, the primary winding of which is fed by the AC voltage source U and to whose secondary winding an ohmic consumer, for example a lamp 4, is connected.
the primary winding of the transformer 3 is in this case directly connected to a connection terminal of the AC voltage source U and connected via a control device 1 to the other connection terminal of this AC voltage source U.
a semiconductor switching element 5 switched into the current path between the alternating voltage source U and the electrical load 2 in such a way that it can control the current flow.
a triac is shown as a semiconductor switching element 5 in FIG. This triac is controlled by a control circuit 6 via an ignition pulse output terminal b.
the control circuit 6 is connected via a connecting terminal a on one side of the semiconductor switching element 5 and connected via a connecting terminal c on the other side of the semiconductor switching element 5.
the control circuit includes a detector F for detecting the polarity of the instantaneous output voltage of the voltage source U or the polarity of the instantaneous value of the alternating voltage to be switched by the semiconductor switching element 5.
Such a detector F provides a logic signal at its output, which is dependent on the instantaneous polarity of the supply voltage of the electrical consumer to be controlled.
a conceivable embodiment of such a detector consists of a Schmitt trigger fed by the alternating voltage source U or the polarity of the instantaneous value of the alternating voltage to be switched by the semiconductor switching element 5, which thus detects whether the alternating voltage to be switched has a positive or a negative half-wave . If, as shown in FIG. 1, this Schmitt trigger detects the voltage across the semiconductor switching element 5 via the connection terminals a and c, its hysteresis must be designed in such a way that the previously detected information is received at the Schmitt trigger output when the semiconductor switching element is activated remains.
control circuit 6 contains an ignition pulse pre-generator circuit VS which, depending on a preselected variable, such as, for example, the power of a motor or the brightness of a lamp and in dependence on the supply voltage provided by the AC voltage source U, generates ignition pulses with a specific control angle, based on the Zero crossing of the supply voltage, so to speak as a proposal at its output.
the ignition pulse pre-generator circuit 6 can be implemented in a known manner, for example as it is in devices according to the above-mentioned state of the art Technology can be used. In such ignition pulse pre-generator circuits 6, the phase information of the AC voltage to be switched is often simulated via a phase locked loop, a so-called PLL, which then controls the phase angle in dependence on certain parameters.
the signal output of the ignition pulse pre-generator circuit VS and the signal output of the detector F are each connected to an input of a decision stage ES.
This decision stage ES is designed in such a way that when two ignition pulse suggestions occur at the output of the ignition pulse pre-generator circuit VS within one half-wave of the supply voltage and in the absence of a ignition pulse proposal at the output of the ignition pulse pre-generator circuit VS during at least one output at one output Lock signal delivers.
the control circuit 6 in FIG. 1 also includes a switching and driver unit DS, the output of which is connected to the ignition pulse output terminal b and thus to the control input of the semiconductor switching element 5.
An input of the switching and driver unit DS is connected to the output of the ignition pulse pre-generator circuit VS, another input of the switching and driver unit DS is connected to an output of the decision stage ES which provides a blocking signal in the event of a fault.
the switching and driver unit DS is designed in such a way that it may switch the ignition pulse suggestions provided at the output of the ignition pulse pre-generator circuit VS to the ignition pulse output terminal b, and at least when a blocking signal is present at its input connected to the decision stage ES, switching the Proposed ignition pulse of the ignition pulse pre-generator circuit to the ignition pulse output terminal b prevented.
FIG. 1 shows a particular exemplary embodiment of a control circuit 6, in which a holding stage HS is also included, which independently of the interruption of the control carried out by the switching and driver unit DS in a malfunction recognized by the decision stage ES of the semiconductor switching element 5 can also act on the ignition pulse pre-generator circuit VS. If such a holding stage HS is provided, it can prevent, for example, the issuance of further ignition pulse suggestions by the ignition pulse pre-generator circuit VS at least for a certain time or until the occurrence of any particular event.
the automatic restart of a device according to the invention can also be controlled with the aid of a holding stage HS, which is activated by the decision stage ES after a malfunction has been recognized.
a holding stage HS In order to interrupt the output of an ignition pulse to the ignition pulse output terminal b after the ignition pulse suggestion has been made by the ignition pulse pre-generator circuit VS and the malfunction subsequently determined by the decision stage ES, such a holding stage HS is not necessary.
a holding stage HS can also be part of the decision stage ES or, if an output signal is fed to the decision stage of the ignition pulse pre-generator circuit VS, it can be part of the ignition pulse pre-generator circuit VS.
phase information of the AC voltage to be switched is simulated via a PLL which controls the phase gating angles of the ignition pulse suggestions provided by the ignition pulse pre-generator circuit 6, it is recommended for safe operation of a device according to the invention that the phase gating angles of the ignition pulses provided at the ignition pulse output terminal b can be changed continuously or in stages from a small current flow value to a larger current flow value until the desired phase angle is reached, ie the control device 1 is not switched on immediately with the desired phase angle.
a small current flow causes a phase gating angle of almost 180 °, based on the previous zero crossing of the AC voltage to be switched.
the phase locked loop of the ignition pulse pre-generator circuit VS can namely only one Recognize zero crossing of the AC voltage to be switched when the current through the semiconductor switching element 5 has become zero or is almost zero.
the zero crossing of the AC voltage to be switched and the zero crossing of the switched current are the same.
the current zero crossing is delayed compared to the zero crossing of the AC voltage to be switched. The delay is dependent on the inductive portion of the load and on the phase angle of the ignition pulse that controls the semiconductor switching element 5.
the zero crossings detected by the phase locked loop depend on the type of load and on the phase gating angle with which the semiconductor switching element 5 is driven.
phase gating angle with which the semiconductor switching element 5 is driven is dependent on the zero crossings detected by the phase locked loop of the ignition pulse pre-generator circuit VS.
This interaction which occurs at least in control devices 1 connected in two-wire arrangements, can advantageously be used in circuits according to the invention.
the behavior of a control device according to the invention for various load conditions is considered below, on the condition that the control device starts up in the form of a so-called soft start after each switch-on, which means that each time the control device 1 is switched on, the control circuit 6 fires pulses to the semiconductor switching element 5 emits whose phase gating angle is changed such that immediately after switching on, the current carrying time of the semiconductor switching element is short per half-wave and then continuously or gradually increases until the desired phase gating angle and thus the desired current flow in the semiconductor switching element 5 is reached.
control circuit 6 controls the semiconductor switching element 5 with increasing current without problems until the desired phase angle and thus the desired current is reached.
control device 1 Even if a control device 1 according to the invention controls an ohmic-inductive load or an inductive load as an electrical consumer 2 and the desired phase gating angle would not lead to an impermissibly high current when the selected consumer is controlled, the control device 1 also starts up smoothly and the control device also operates the corresponding load at the corresponding, uncritical phase angle.
the desired phase gating angle would lead to an impermissibly high current, that is to say, at this phase gating angle either two firing pulses would be delivered to the semiconductor switching element 5 within one half-wave of the AC voltage to be controlled, or no firing pulse would be given to the semiconductor switching element, a soft start should be possible until a critical phase gating angle is reached if the phase-locked loop in the ignition pulse pre-generator circuit VS would snap directly onto the output voltage of the supplying AC voltage source U, which is possible with a three-wire arrangement.
control device 1 and the electrical consumer 2 are connected in a two-wire arrangement and there is the above-mentioned interaction between the alternating voltage to be switched and the phase angle of the ignition pulses switched to the semiconductor switching element, a control oscillation occurs in control devices 1 according to the invention with a phase locked loop, which oscillation occurs in a phase oscillation of the phase locked loop.
the decision stage ES recognizes a network half-wave without an ignition pulse shortly after the start of the soft start. Since this is a criterion for the detection of a faulty operating state, the semiconductor switching element is controlled further via the switching and driver unit DS 5 at least temporarily prevented.
FIG. 2 shows in the form of a basic circuit diagram particularly favorable embodiments of a decision stage ES, a holding stage HS and the part of a switching and driver unit DS essential to the invention.
the decision stage ES shown in FIG. 2 has a signal input terminal d to which the output signal of the detector F of the polarity of the instantaneous output voltage of the voltage source U is applied.
the signal input terminal d is connected to the signal input D of a D flip-flop FF1 via an inverter IV1. This inverter is not necessary for the functioning of the circuit, but it does not interfere either.
the flip-flop FF1 and three further flip-flops FF2, FF3 and FF4 are D-flip-flops triggered on the rising edge.
the clock input CH of these four D flip-flops FF1, FF3 and FF4 is each connected to a signal input terminal e.
This signal input terminal E is acted upon by ignition pulse suggestions, which an ignition pulse pre-generator circuit from FIG. 1 provides.
the signal input D of the D flip-flop FF3 is connected to a signal input terminal g which is permanently supplied with a potential defining a logic one.
the signal output QH of the D flip-flop FF3 is connected to the signal input D of the D flip-flop FF4.
the signal output QH of the D flip-flop FF4 is connected to an input of a first NAND gate 1.
the D flip-flop FF3 and the D flip-flop FF4 are resettable and for this purpose each have a reset signal input RH. If an H is contained in the reference number in the logic circuits shown in FIG.
the reset signal inputs RH of the flip-flop FF3 and the flip-flop FF4 are connected together to a signal input terminal f which is acted upon with a logic signal depending on the switched-on state of the control device 1 according to FIG. 1 such that the flip-flops are switched on each time the control device is switched on FF3 and FF4 are reset. This ensures that after switching on the control device 1 according to FIG. 1 in a decision stage ES according to FIG.
an input of the first NAND gate NAND1 is only released via the flip-flop FF4 when the second ignition pulse proposal from an ignition pulse pre-generator circuit VS was connected to the signal input terminal e.
the signal output QH of the flip-flop FF1 in FIG. 2 is connected directly to an inverting input of an EXNOR gate EXNOR. It is also connected via an inverted IV2 to the signal input D of the flip-flop FF2 and also to a non-inverting input of the EXNOR gate EXNOR. Another non-inverting input of the EXNOR gate EXNOR is connected to the signal output QH of the flip-flop FF2.
the inverter IV2 can be omitted in this case, the inverting input of the EXNOR gate EXNOR being omitted.
the signal output of the EXNOR gate EXNOR is connected to a second signal input of the first NAND gate NAND1.
the circuit described provides a logic zero at the signal output of the first NAND gate NAND1 whenever at least two ignition pulse suggestions have been made available at the signal input terminal e after the control device has been switched on and the flip-flops FF3 and FF4 have been reset, and if this has been accomplished the detector F is not connected to the signal input terminal d when there are two successive ignition pulse suggestions connected to the signal input terminal e differentiates its logic level.
the signal output of the first NAND gate NAND1 is therefore suitable as a signal output of a decision stage ES according to FIG. 1, a 1 at the output of this decision stage enabling the proposed ignition pulse to be switched through by the switching and driver unit DS.
the signal output of the decision stage ES connected to the switching and driver unit DS is formed by the signal output of an AND gate AND.
An input of this AND gate AND is connected to the output of the first NAND gate NAND1.
the other input of this AND gate AND is connected to a signal input terminal h via an inverter IV3.
the input terminal h can be supplied with a logic signal that always represents a logic one when the semiconductor switching element 5 is in the ignited state.
information about the state of the AC voltage to be switched is present at the signal input terminal d in FIG.
the two flip-flops FF1 and FF2 form a shift register in which this information is shifted on.
An ignition pulse proposal provided by the ignition pulse pre-generator circuit VS forms the shift clock.
the decision stage ES provides a logic one or a logic zero at its output. Since a correct accident detection by the decision stage ES is only possible after the control device 1 is switched on after the second ignition pulse, the output of the decision stage ES is blocked via the flip-flops FF3 and FF4 for the first ignition pulse after the control device 1 is switched on.
the embodiment of a decision stage ES shown in FIG. 2 also has a signal output for connection to a holding stage HS on.
the signal output of the first NAND gate NAND1 could be provided as the signal output.
the signal level indicating an accident may be erroneously briefly present at the output of the first NAND gate NAND1.
the decision stage ES is provided as a signal output for applying the holding stage HS to the signal output of a NOR gate NOR, an input of this NOR gate being connected to the signal input terminal e and the other input of this NOR gate is connected to the output of the first NAND gate NAND1. This prevents the holding stage HS from being activated during a pushing operation, that is to say when a high level is present at the signal input terminal e.
the switching and driver unit DS shown in FIG. 2 represents only a basic circuit diagram of the part of the switching and driver unit DS that is essential to the invention. It is assumed that the resettable D flip-flop FF5 shown is suitable at its signal output QH, which is the Ignition pulse output terminal b forms an ignition pulse required to drive a semiconductor switching element.
the signal input D of the D flip-flop FF5 is connected to the output of the AND gate of the decision stage ES.
the clock input CH of the flip-flop FF5 is connected via an inverter IV4 to the signal input terminal e and is thus acted upon by the ignition pulse suggestions of the ignition pulse pre-generator circuit VS from FIG. 1.
the reset signal input RH of the flip-flop FF5 is connected to a signal input terminal i.
the signal input terminal i is acted upon by a clock signal which is coupled to the clock of the ignition pulse pre-generator circuit VS in such a way that it is suitable to reset the flip-flop FF5 after switching through each ignition pulse.
the flip-flop FF5 then only switches an ignition pulse proposal pending at the signal input terminal e to the ignition pulse output terminal b, if the decision stage ES switches a corresponding signal to the signal input D of the D flip-flop FF5, if the decision stage ES therefore does not detect an accident.
the embodiment of a holding stage HS shown in FIG. 2 consists primarily of a resettable counter which locks at a certain counter reading and only starts to run again after a reset signal has occurred.
the embodiment shown uses four counter basic elements CE1, CE2, CE3 and CE4, which are each formed from a resettable D flip-flop, the signal output QH of which is fed back to the signal input D via an inverter, the signal input D being the output of the Basic counter element CE1, ... forms and the clock input CH of a basic counter element CE2, CE3 and CE4 is connected to the signal output of the previous basic counter element CE1, CE2 or CE3 and the clock input CH of the first basic counter element CE1 is connected to a Clock signal is applied.
An output terminal 1 is provided as the output of the holding stage HS, which is connected to the signal output of a second NAND gate NAND2 and is also connected to a signal input of a third NAND gate NAND3.
the other input of this third NAND gate NAND3 is connected to a signal input terminal k, to which a clock signal is applied.
This clock signal should usually have a fixed relationship to the frequency of the AC voltage to be switched.
the output of the third NAND gate NAND3 is connected to the clock input CH of the first basic counter element CE1. It is thereby achieved that a blocking signal at the output terminal 1 of the holding stage HS prevents the counter from counting further.
the signal inputs of the second NAND gate NAND2 are each connected to signal outputs QH of flip-flops contained in basic counter elements CE2, CE4.
FIG. 2 shows only exemplary embodiments of possible logic circuits. Of course, the person skilled in the art can implement the same logical relationships by using any logic elements. If only one connection is shown in FIG. 1 and FIG. 2 as the ignition pulse output terminal b, this does not exclude that, depending on the type of semiconductor switching element 5 that should be controlled by this ignition pulse output terminal, a terminal with two connections can also be provided.
the holding stage HS can be activated by the decision stage ES when a malfunction is detected and can prevent a further output of ignition pulse suggestions by the ignition pulse pre-generator circuit VS for the time of its activation. This process can be limited in time by a corresponding design of the holding stage HS, so that after a certain time, the ignition pulse pre-generator circuit VS again delivers ignition pulse suggestions and the control circuit 6 thus attempts to start up. If there is still a malfunction during this start-up attempt, no ignition pulses are switched to the ignition pulse output terminal b and the holding stage HS once again prevents the ignition pulse suggestions from being output by the ignition pulse pre-generator circuit VS for a certain time. If there is no longer a fault when the system is switched on again after the blocking time specified in the holding stage HS has elapsed, the control device 1 can operate in normal operation.
a device according to the invention is used for the stepless control of an electric motor based on the phase gating principle, then the automatic restart after an accident may be advisable, at least for a limited number of restart attempts.
a device according to the invention is used for the stepless control of incandescent lamps according to the phase gating principle, that is to say as a brightness controller, the control circuit must be switched on again after detection of an accident according to the invention, at least when the incandescent lamp is actuated via a transformer, this does not always make sense. If a malfunction is detected due to a defective incandescent lamp and the control of the semiconductor switching element 5 was prevented in a device according to the invention, it may be desirable that after the defective incandescent lamp is replaced by an intact incandescent lamp, it does not immediately after being inserted into the socket is controlled. In this case, it makes sense that the control circuit 6 does not switch on again automatically after an accident occurs.

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Power Conversion In General (AREA)
Electronic Switches (AREA)
Circuit Arrangement For Electric Light Sources In General (AREA)
Supply And Distribution Of Alternating Current (AREA)
Remote Monitoring And Control Of Power-Distribution Networks (AREA)

EP91104831A 1990-04-17 1991-03-26 Appareil pour la régulation continue des dispositifs électriques suivant le principe de découpage de phase, notamment régulateur de luninosité, et l'utilisation d'un tel appareil Expired - Lifetime EP0452716B1 (fr)

Applications Claiming Priority (2)

Application Number	Priority Date	Filing Date	Title
DE4012255		1990-04-17
DE4012255		1990-04-17

Publications (3)

Publication Number	Publication Date
EP0452716A2 true EP0452716A2 (fr)	1991-10-23
EP0452716A3 EP0452716A3 (en)	1992-03-11
EP0452716B1 EP0452716B1 (fr)	1994-07-27

Family

ID=6404532

Family Applications (1)

Application Number	Title	Priority Date	Filing Date
EP91104831A Expired - Lifetime EP0452716B1 (fr)	1990-04-17	1991-03-26	Appareil pour la régulation continue des dispositifs électriques suivant le principe de découpage de phase, notamment régulateur de luninosité, et l'utilisation d'un tel appareil

Country Status (4)

Country	Link
US (1)	US5148098A (fr)
EP (1)	EP0452716B1 (fr)
AT (1)	ATE109320T1 (fr)
DE (1)	DE59102312D1 (fr)

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number	Priority date	Publication date	Assignee	Title
US5245272A (en) *	1991-10-10	1993-09-14	Herbert David C	Electronic control for series circuits
DE69523314T2 (de) *	1994-07-10	2002-07-04	Benjamin Barber	Leistungssteuerung auf niederspannungsnetzen

Family Cites Families (10)

* Cited by examiner, † Cited by third party
Publication number	Priority date	Publication date	Assignee	Title
US3626250A (en) *	1970-10-16	1971-12-07	Gen Electric	Protective circuit for current regulator
DE2362225B2 (de) *	1973-12-14	1980-07-03	Deutsche Itt Industries Gmbh, 7800 Freiburg	Vorrichtung zur Helligkeitswahl der Raumbeleuchtung
DE2429763C3 (de) *	1974-06-21	1978-12-07	Insta Elektro Gmbh & Co Kg, 5880 Luedenscheid	Schaltungsanordnung zur gesteuerten Speisung einer Last aus einem Wechselstromnetz
DE2543370C3 (de) *	1975-09-29	1981-11-26	SIEMENS AG AAAAA, 1000 Berlin und 8000 München	Vorrichtung zur stufenlosen Steuerung elektrischer Verbraucher nach dem Phasenanschnittprinzip insbesondere Helligkeitsregler
US4396869A (en) *	1979-03-05	1983-08-02	Leviton Manufacturing Company, Inc.	Time responsive variable voltage power supply
JPS60153525A (ja) *	1984-01-23	1985-08-13	Canon Inc	交流制御回路用安全回路
US4688161A (en) *	1986-07-16	1987-08-18	Vari-Lite, Inc.	Regulated power supply apparatus and method using reverse phase angle control
DE3836128A1 (de) *	1987-12-12	1989-07-20	Insta Elektro Gmbh & Co Kg	Helligkeitssteuerschaltung fuer gluehlampen und schaltnetzteile
DK13489A (da) *	1988-03-30	1989-10-01	Insta Elektro Gmbh & Co Kg	Lysstyrkereguleringskredsloeb til gloedelamper og netkoblingsdele med et beskyttelses- og begraensningskredsloeb til opnaaelse af en elektronisk sikring
DE3839373C2 (de) *	1988-03-30	1996-09-12	Insta Elektro Gmbh & Co Kg	Helligkeitssteuerschaltung für Glühlampen und Schaltnetzteile mit einer Schutz- und Begrenzungsschaltung zum Erhalt einer elektronischen Sicherung

1991
- 1991-03-26 AT AT91104831T patent/ATE109320T1/de not_active IP Right Cessation
- 1991-03-26 EP EP91104831A patent/EP0452716B1/fr not_active Expired - Lifetime
- 1991-03-26 DE DE59102312T patent/DE59102312D1/de not_active Expired - Lifetime
- 1991-04-17 US US07/686,619 patent/US5148098A/en not_active Expired - Lifetime

Also Published As

Publication number	Publication date
ATE109320T1 (de)	1994-08-15
US5148098A (en)	1992-09-15
EP0452716A3 (en)	1992-03-11
EP0452716B1 (fr)	1994-07-27
DE59102312D1 (de)	1994-09-01

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