EP0483327A1 - Circuit mutateur et son procede de commande - Google Patents

Circuit mutateur et son procede de commande

Info

Publication number
EP0483327A1
EP0483327A1 EP91909696A EP91909696A EP0483327A1 EP 0483327 A1 EP0483327 A1 EP 0483327A1 EP 91909696 A EP91909696 A EP 91909696A EP 91909696 A EP91909696 A EP 91909696A EP 0483327 A1 EP0483327 A1 EP 0483327A1
Authority
EP
European Patent Office
Prior art keywords
switch
circuit
controllable switches
voltage
converter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP91909696A
Other languages
German (de)
English (en)
Inventor
Jan Abraham Ferreira
Jacobus Daniel Van Wyk
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
ABB Ceag Licht und Stromversorgungstechnik GmbH
CEAG Licht und Stromversorgungstechnik GmbH
Original Assignee
ABB Ceag Licht und Stromversorgungstechnik GmbH
CEAG Licht und Stromversorgungstechnik GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by ABB Ceag Licht und Stromversorgungstechnik GmbH, CEAG Licht und Stromversorgungstechnik GmbH filed Critical ABB Ceag Licht und Stromversorgungstechnik GmbH
Publication of EP0483327A1 publication Critical patent/EP0483327A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/505—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/515—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H02M7/523—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with LC-resonance circuit in the main circuit
    • H02M7/5233—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with LC-resonance circuit in the main circuit the commutation elements being in a push-pull arrangement
    • H02M7/5236—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with LC-resonance circuit in the main circuit the commutation elements being in a push-pull arrangement in a series push-pull arrangement

Definitions

  • the present invention relates to a converter and a method for its control.
  • the intermediate circuit resonant converter comprises a two-stage resonant circuit with a single inductor (induction coil) and two capacitors, one of which is switched on by means of an additional switch during the continuous switch-on state of one of the switches.
  • the inductor has a relatively high nominal effective current and the semiconductor switches are oversized relative to the supply voltage.
  • the resonance pole converter has an oscillating circuit in the form of a non-saturating inductor and a capacitor connected in parallel. Because of the resonant circuit and
  • a converter circuit for supplying an inductive load with a first controllable switch which can be connected to a positive connection of a direct voltage supply and a second controllable switch which can be connected to a negative connection of the direct voltage supply, the first and second controllable switches in Row are arranged; first and second diodes connected antiparallel to the corresponding first and second controllable switches, and a resonant circuit to which an output between the first and second switches is connected, the resonant circuit comprising a saturable inductor and a wiring capacitor connected in parallel, with turn-off losses of of the converter circuit can be reduced by commutating the inductor and load current to the capacitor during the switching off of one of the switches and switch-on losses in the one switch can be reduced in that before switching on the one switch by permitting saturation of the inductor reverse recovery of the other switch's diode is effected.
  • the converter circuit has a fixed duty cycle, the switching frequency being determined by the saturation properties of the inductor.
  • an actuator is provided in the resonant circuit, the actuator applied stabilizing the voltage applied to the resonant circuit and pulse width modulation being achieved by adjusting this voltage.
  • the actuator is preferably in the form of a smaller controllable converter source, which is connected to a voltage divider in the form of at least one capacitor connected between the positive or negative connections of the DC voltage supply and the output of the actuator. Two capacitors are expediently connected in series between the positive and negative connections of the DC voltage supply.
  • the invention extends to a method for converting a DC voltage supply with the following steps: providing first and second controllable switches connected in series to the DC voltage supply, providing first and second diodes connected antiparallel to the corresponding first and second controllable switches, providing one Oscillating circuit with an output between the first and second controllable switches, the oscillating circuit comprising a circuit capacitor and a saturable inductor connected in parallel, reducing the turn-off losses by commutating current to the circuit capacitor during the switching off of one of the switches and reducing the switch-on losses in that before the switch is turned on, the reverse recovery of the diode of the other switch is effected by permitting the saturation of the saturable inductor.
  • the method preferably includes the further steps of allowing a current to flow through the other switch before switching on the one switch, then switching off the other switch and thus causing a current to flow through the diode of the one switch.
  • the converter circuit described above belongs to a single-phase branch. A large number of converter circuits can be connected to one another in order to provide a plurality of phase branches and thus to form a large number of pulse-width converters.
  • the saturable inductor is preferably an inductor with a closed core or an inductor on which an air gap is provided, with a core that is almost closed.
  • the converter circuit according to the invention is preferably suitable for use in the kW range.
  • the maximum rated voltages and currents of the switches are close to the maximum voltage and current values applied to the inductive load.
  • the normalized ratio between the corresponding nominal voltages and currents of the switches and the maximum voltage and current applied to the inductive load is in each case in the range from 1.0 to 1.2.
  • FIG. 1 shows a circuit diagram of a first embodiment according to the invention, namely a converter with a fixed duty cycle
  • FIG. 2 shows a circuit diagram of a second embodiment according to the invention with a converter with pulse width modulation
  • a controllable semiconductor switch S1 is connected at one end to the positive connection 10 for receiving a positive source voltage Vs / 2 and a controllable semiconductor switch S2 is connected at one end to the negative terminal 12 for receiving a negative source voltage Vs / 2.
  • the switches can be selected from various semiconductor switches including bipolar transistors, IGBTs, MOSFETs and GTOs.
  • the first and second free-wheeling diodes D1 and D2 are connected antiparallel to the corresponding switches S1 and S2.
  • a resonant circuit 16 in the form of a saturable inductor L and a circuit capacitor C connected in parallel therewith is connected with an output between the switches S1 and S2 and connected with an input to a zero voltage output 18 of the direct voltage supply 14.
  • the converter circuit feeds an inductive load 20 which is connected to the resonant circuit 16 at a point between the switches S1 and S2.
  • the inductive load can take many forms, including an electrical machine or a filter of a power supply.
  • the pulse width modulated converter circuit shown in FIG. 2 differs from FIG. 1 in that a pulse width modulated output is provided for supplying the inductive load, which results in a load current with a sinusoidal or any other desired waveform.
  • the converter of FIG. 1 provides an output with a fixed duty cycle, which is determined by the saturation behavior of the inductor. In this case, the resulting load current cannot be controlled by the converter. In the figure 2 becomes a.
  • the modulated output is achieved by providing a voltage divider consisting of two capacitors C1 and C2 connected in series to the DC voltage supply 14.
  • An actuator 22 is connected to a common node 24 between the capacitors C1 and C2 and the resonant circuit 16.
  • the actuator which can take the form of a smaller controllable converter or a linear current source, serves the double functions of stabilizing the voltage at node 24 and achieving pulse width modulation by adjusting the voltage at node 24.
  • switch S1 is switched on and current II flows through the switch.
  • switch S1 is switched off.
  • the wiring capacitor C is charged by commutating the load and inductor current, which delays the voltage rise at the switch S1 when it is switched off and limits the product of the switching voltage and current during the switching peak.
  • capacitor C is fully charged and freewheeling diode D2 can now switch through.
  • the current 12 through the diode D2 consists of the source current Is and the unsaturated inductor current 12 and rises slightly during this period due to the build-up of the inductor current.
  • the inductor operates with a relatively high effective inductance in the unsaturated mode.
  • inductor L saturates and its effective inductance drops drastically.
  • the amplitude of the Inductor current quickly until it reaches a greater value than the source current Is through the diode D2, so that the combined current 12 changes direction and is briefly passed through the switch S2.
  • the effect of this current reversal is therefore to "block" the source current Is through the diode, which causes the diode D2 to reverse in reverse before the switch S1 is switched on.
  • the saturable inductor can also be caused to saturate just before the switch S1 is switched off. If the inductor is saturated before switching off, the "depth" of the saturation is less than the "depth” of the saturation before switching on. In other words, the inductor is allowed to saturate for a shorter period of time before switching off. By saturating the inductor before switching off, the current required to stabilize the voltage Vcs at 24 is reduced. After the current 12 has built up sufficiently, the switch S2 is switched off. During the period 5, the charging of the capacitor C causes the switch S2 to be switched off smoothly. At the end of period 5, the capacitor C is fully charged; and the freewheeling diode D1 therefore begins to conduct current.
  • the switch 1 can now be switched on without load.
  • the inductor current IL drops rapidly and the inductor L returns to the unsaturated state after the switch S1 conducts again.
  • the cycle is now complete and period 1 begins.
  • the converter according to the invention is intended. Switching with low losses when switching on and off switches S1 and S2 can be achieved, which means that the converter can work with a high switching frequency.
  • the resonant circuit is passive and, apart from the previously existing switches and their anti-parallel diodes, no further semiconductor components are incorporated into the circuit introduced. During the operation of the circuit, the energy stored in the wiring capacitor is not dissipated, but simply transferred to the saturable inductor, which in turn leads it back to the wiring capacitor during the next cycle. The resonant circuit therefore does not dissipate power loss.
  • the converter circuit is intended to use semiconductor switches with the lowest possible nominal voltages and currents in order to increase the cost effectiveness.
  • the normalized nominal voltage would be 1.0 for a typical switch, while the nominal current could be between 1.0 and 1.2 times the load current. Normalized means in each case based on the maximum voltage and the current applied to the inductive load.
  • the nominal kVA of the capacitor and inductor of the resonant circuit is only a fraction of the kVA of the converter. Cost effectiveness is achieved by using a relatively small capacitor and inductor in one
  • Another feature of the invention is that reverse recovery of the reactive power diodes does not increase the switching losses during switching and in particular during switching on, as is often the case with other converters, since the reverse recovery occurs before switching.
  • circuit diagrams of Figures 1 and 2 represent only single-phase branches. Both the circuit with a fixed duty cycle and the circuit with pulse width modulation are generally used in two, four or six pulse converters in order to provide a one, two or three-phase AC voltage supply in the case of the pulse width modulated circuit.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Logic Circuits (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un circuit mutateur pour l'alimentation d'une charge inductive et un procédé de commande du mutateur. L'objet de l'invention est d'obtenir un circuit et un procédé de commande de celui-ci qui sollicitent de manière particulièrement réduite les commutateurs commandables du circuit et entraînent des pertes minimes de commutation. A cet effet, un mutateur à résonance comprend un circuit résonant avec un inducteur saturable, ce qui permet la régénération en sens inverse de diodes connectées en antiparallèle aux commutateurs commandables. Ce mutateur est particulièrement utile pour des applications dans des plages élevées de puissance à plusieurs kilowatts.
EP91909696A 1990-05-18 1991-05-17 Circuit mutateur et son procede de commande Withdrawn EP0483327A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
ZA903840 1990-05-18
ZA903840 1990-05-18

Publications (1)

Publication Number Publication Date
EP0483327A1 true EP0483327A1 (fr) 1992-05-06

Family

ID=25580120

Family Applications (1)

Application Number Title Priority Date Filing Date
EP91909696A Withdrawn EP0483327A1 (fr) 1990-05-18 1991-05-17 Circuit mutateur et son procede de commande

Country Status (3)

Country Link
EP (1) EP0483327A1 (fr)
JP (1) JPH05501196A (fr)
WO (1) WO1991018442A2 (fr)

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DK174165B1 (da) 2000-10-13 2002-08-05 American Power Conversion Denm Resonanskonverter
CN113659822B (zh) * 2021-08-17 2023-09-22 重庆大学 一种基于饱和电感降低软开关功率变换器损耗的方法

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE1413550A1 (de) * 1963-09-30 1969-01-09 Licentia Gmbh Schwingkreiswechselrichter
FI64026C (fi) * 1981-02-13 1983-09-12 Kemppi Oy Inverterkoppling

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO9118442A2 *

Also Published As

Publication number Publication date
JPH05501196A (ja) 1993-03-04
WO1991018442A3 (fr) 1991-12-26
WO1991018442A2 (fr) 1991-11-28

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