EP0683607A2 - Dispositif pour le traitement d'un signal de télévision analogique à valeurs réelles - Google Patents

Dispositif pour le traitement d'un signal de télévision analogique à valeurs réelles Download PDF

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Publication number
EP0683607A2
EP0683607A2 EP95106412A EP95106412A EP0683607A2 EP 0683607 A2 EP0683607 A2 EP 0683607A2 EP 95106412 A EP95106412 A EP 95106412A EP 95106412 A EP95106412 A EP 95106412A EP 0683607 A2 EP0683607 A2 EP 0683607A2
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EP
European Patent Office
Prior art keywords
complex
signal
digital
frequency
real
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP95106412A
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German (de)
English (en)
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EP0683607B1 (fr
EP0683607A3 (fr
Inventor
Heinz Dr. Göckler
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Robert Bosch GmbH
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Robert Bosch GmbH
ANT Nachrichtentechnik GmbH
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Application filed by Robert Bosch GmbH, ANT Nachrichtentechnik GmbH filed Critical Robert Bosch GmbH
Publication of EP0683607A2 publication Critical patent/EP0683607A2/fr
Publication of EP0683607A3 publication Critical patent/EP0683607A3/de
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Publication of EP0683607B1 publication Critical patent/EP0683607B1/fr
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N5/00—Details of television systems
    • H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
    • H04N5/4446—IF amplifier circuits specially adapted for B&W TV
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N5/00—Details of television systems
    • H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
    • H04N5/60—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals

Definitions

  • the invention relates to a device for processing a modulated real-valued analog television signal which is in the intermediate frequency position.
  • EP 62 872 B1 shows the signal processing of a sampled intermediate frequency signal as a complex digital signal.
  • the older patent application P 43 37 134 discloses a method for processing a digital frequency division multiplex signal from television channel signals.
  • the channel signals are oversampled, filtered using a complex half-band filter and shifted in frequency using a complex mixer for further processing.
  • This complex half-band filter is also used for decimation by a factor of 1/2.
  • the object of the invention is to design the device so that digital demodulation of the television signals is possible with little effort. This object is achieved by the features of one of claims 1 to 3. Advantageous embodiments are in the subclaims shown.
  • the device according to the invention allows a complete, uniform digital implementation of an image and sound demodulator for television signals.
  • the common preprocessing into a complex-value output signal permits flexible further processing. In this way, image and sound components can be processed largely together with little effort or separately in order to keep interference or filter tolerances low.
  • the block diagram according to FIG. 1 shows a possible embodiment of the signal preprocessing for the subsequent picture and sound demodulation devices, for example consisting of the demodulator DMF for the picture parts with an upstream mixer FUTV and the demodulators DMT1 and DMT2 for the separate processing of the sound parts with corresponding upstream mixers FUT1 and FUT2.
  • the input signal for the signal preprocessing according to FIG. 1 is an analog real-value television signal FBAS TT , which in Intermediate frequency position is present - with an image carrier, preferably at 38.9 MHz (CCIR standard).
  • the FBAS TT signal is sampled closed by means of a scanning unit - A / D converter.
  • Figure 4 shows the television signal before and after sampling (a) and after filtering and decimation (b).
  • the sampled real-valued television signal is converted into a complex-valued digital signal by means of a digital preprocessing stage VV and shifted spectrally so that the center frequency of the complex-valued digital signal appears at the frequency 0 (FIG. 1a).
  • VV digital preprocessing stage
  • FIG. 1a the corresponding signal paths and assemblies are marked with double dashes in the figures.
  • the complex digital filter CHBFT extracts the signal spectrum in the normal position as it is required for the subsequent TV demodulation. If necessary, further processing can also be carried out in the reverse position.
  • the complex digital filter CHBFT is preferably in the form of an L band Filter (complex Nyquist filter), where L is an integer decimation factor.
  • L is an integer decimation factor.
  • the mean coefficient is real 1 / L or purely imaginary j / L for the most cost-effective case.
  • the average coefficient becomes 1/2 or j / 2 (half-band filter).
  • the assemblies of the preprocessing stage according to FIG. 1 partially match the implementation according to P 43 37 134.
  • the principle of the complex half-band filter CHBFT itself is described in DE-PS 36 21 737.
  • is shown in Figure 4, together with the sampling frequencies f A e or f A and the band limits.
  • the respective position of the picture carrier is marked with BT and the position of the sound carrier with TT.
  • the output signal of the complex mixing device ME1 is fed to a pair of identical low-pass filters RTP with real coefficients, which can be implemented recursively or non-recursively. One low pass is intended for the real part, the other for the imaginary part of the complex signal to be processed.
  • the output signal of the preprocessing stage VV is further processed in three branches - with two provided sound carriers - in a first branch for the picture demodulation and in two further branches for the two sound signals T1 and T2 (FIG. 1b). If there is only one sound carrier to be processed, the third branch is of course omitted.
  • a first complex mixing device FUTV is provided, the mixing frequency of which is selected such that the image carrier f BT appears at the frequency 0 after the mixing.
  • the complex mixing device is followed by a complex digital demodulator DMF for the picture portion of the television signal, by means of which the CVBS signal, sampled in the example with 14.138 18th ⁇ MHz, is extracted.
  • the complex mixing device FUTV is equipped with a frequency and / or phase locked loop AFC / PLL1, which makes it possible for the image carrier BT to lie exactly at the frequency 0 and to have the correct phase (locked state).
  • a digital demodulator DMT1 is provided for processing the first sound carrier T1, which, fed by the preprocessing stage VV, first has a complex mixing device FUT1 for processing the sound carrier T1.
  • the complex carrier oscillation for the mixing device FUT1 is derived via the frequency and / or phase locked loop AFC2.
  • the third branch which is constructed like the second branch, but is used for processing the sound carrier T2, there is the digital demodulator DMT2 with the input-side mixing device FUT2.
  • the complex carrier vibration for this mixing device FUT2 is derived via the frequency and / or phase locked loop AFC3.
  • Such decimation filter devices are, for example, in multirate digital signal processing by RE Crochiere and LR Rabiner, Prentice-Hall Inc. Englewood Cliffs, NJ. USA. Recursive or non-recursive FIR filters that can be efficiently implemented as polyphase filters are possible.
  • the decimation is preferably carried out in three stages with the decimation factors 5, 3 and 2.
  • the output signals of the decimation filter devices DZ1 and DZ2 are each forwarded to a complex tone FM demodulator FMDE1 or FMDE2 for each of the tone signals T1, T2.
  • complex tone FM demodulators with complex input and real output signals are known per se (Signal Processing 9, 1985, North Holland, pages 263-276 "Equalization Problems in a Digital FM Receiver"; DE 42 41 965.4) and therefore require no further explanation.
  • the frequency control loops AFC2 and AFC3 can be of grade 1. Alternatively, a combined frequency and phase locked loop can also be provided.
  • the frequency control loops AFC2 and AFC3 can be implemented with a frequency error detector, e.g. B. according to IEEE Transactions on Communications, Vol. 37, No.
  • the frequency control loops AFC2 and AFC3 process the output signals of the two FM demodulators FMDE1 and FMDE2 into two complex carrier oscillations of the frequency - (f BT + f T1 ) respectively. - (f BT + f T2 ) .
  • the image carrier f BT which the control loops AFC2 and AFC3 require as a reference frequency, can be derived from the output signal of the mixing device FUTV or from a signal in its control loop AFC / PLL1, or is set as a nominal initial value in the control loops AFC2 and AFC3. The latter also applies to the nominal values of the sound carrier frequencies f T1 and f T2 .
  • decimation filter devices DZ3 and DZ4 are provided, which preferably decimate first by a factor of 2 and then by a factor of 11/81.
  • FIG. 2 shows an alternative both for the preprocessing stage VV (FIG. 2a) and for the subsequent image and sound demodulation (FIG. 2b).
  • the configuration of the preprocessing stage according to FIG. 1a can be combined with the configuration of the image and sound demodulation according to FIG. 2b .
  • the downstream digital filter CHBFT works with the same sampling rate f A. It is designed as a complex half-band filter for converting the oversampled real-value television signal into a complex-value output signal.
  • the filter CHBFT is designed so that it performs a sampling rate conversion by a factor of 1/2, ie the oversampling by a factor of 2 of the A / D converter is canceled again.
  • Some coefficients of this complex half-band filter CHBFT are identical to 0.
  • the output signal of the filter CHBFT is now processed together in relation to the two or more sound components (two sound carriers TT are assumed in the exemplary embodiment).
  • the branch for the image demodulation is configured as in FIG. 1b with the difference that the frequency and / or phase locked loop has a second output for providing the mixing frequency of the complex mixing device FUTT at the input of the demodulator DMT for the joint processing of the sound components.
  • the complex carrier vibration for the mixing device FUTT is thus derived from the carrier vibration of the mixing device FUTV.
  • the frequency and / or phase locked loop AFC / PLL1 is designed so that the image carrier frequency f BT appears for the mixer FUTV at its first output and the arithmetic mean of the two sound carrier frequencies f T1 and f T2 offset image carrier frequency f BT + 1/2 [f T1 + f T2 ] .
  • separate control loops AFC2 and AFC3 can be used as before, the nominal starting value of which is fixed.
  • a complex TT signal can again be derived in the above-mentioned frequency range either with the help of one of the described CHBF filters (L-band) with subsequent frequency conversion or with the Weaver method.
  • This complex carrier oscillation (mixer frequency: -1/2 (f T1 + f T2 )) can be generated by converting a real carrier oscillation - for example using a CHBF filter or the Weaver method - into the complex area.
  • a storage device Sp with a sin / cos table is used for this.
  • the memory device can either be designed as a ROM or RAM standard chip, where the sample values of the sin / cos values are either stored permanently or in a variable manner.
  • This decimation filter device can be constructed analogously to the decimation filter device according to DE PS 36 21 737.
  • Such decimation filter devices are as before also mentions generally in Multirate Digital Signal Processing by RE Crochiere and LR Rabiner, Prentice-Hall Inc. Englewood Cliffs, NJ. USA. Recursive or non-recursive FIR filters that can be efficiently implemented as polyphase filters are possible.
  • the decimation is preferably carried out in two stages with the decimation factors 5 and 3.
  • the output signal of the decimation filter device DZ1 is fed in parallel branches separately for the two tone signals T1 and T2 to a third and fourth complex mixing device FUT1 and FUT2.
  • the carrier vibrations for the two mixing devices FUT1 and FUT2 can, as will be explained, be processed together.
  • the two mixing devices FUT1 and FUT2 each have a decimation filter device DZ2 or DZ3 for converting the sampling rate by a factor of 2, ie to 471, 27 ⁇ kHz downstream. This is followed by a complex tone FM demodulator FMDE1 or FMDE2 for each of the tone signals T1, T2.
  • At least one frequency control loop AFC2 of at least first order is provided to derive the mixing frequencies for the third and fourth mixing devices FUT1 and FUT2 at the correct frequency.
  • a combined frequency and phase locked loop can also be provided.
  • the frequency control loop AFC2 can be implemented with a frequency error detector in accordance with IEEE Transactions on Communications, Vol. 37, No. 2, 1989, pages 159-163.
  • the frequency control loop AFC2 processes the output signal of at least one of the two FM demodulators FMDE1 and FMDE2 into two complex carrier oscillations Frequency + 1/2 (f T2 - f T1 ) respectively. - 1/2 (f T2 - f T1 ) , which each result from the differences between the two sound carrier frequencies, but differ in their signs.
  • sin / cos tables are again used in the frequency control loop. In contrast to a separate sound processing according to the configuration according to FIG. 1, the effort is less. Only a decimation filter is required for decimation by a factor of 15.
  • the decimation filter devices DZ4 and DZ5 are provided, which preferably decimate first by a factor of 2 and then by a factor of 11/81.
  • the preprocessing stage VV according to FIG. 3a like the exemplary embodiment in FIG. 1a, has a complex digital filter CHBFT behind the A / D converter, which is preferably also designed as an L-band filter with a decimation factor of 2.
  • the mixing device ME1 is omitted and the digital filter pair RTP3 / RTP4 for band limitation of the complex digital signal now has complex coefficients.
  • a block diagram for this pair of filters is shown in FIG. It consists of four sub-filters, two of which are identical. As FIG.
  • FIG. 5 shows, two identically constructed partial filters for the real and imaginary part of the complex coefficients (RTP3, RTP4) are linked on the output side, in such a way that a pair of filters separates the real part and the other filter pair supplies the imaginary part of the output signal of the preprocessing stage VV, the respective filter pair being fed with the complex digital signal.
  • each of the variants of the preprocessing stage shown in FIGS. 1 to 3 can be combined with each variant for further processing - separate or common sound signal processing with different preparation of the mixing frequency of the mixer / s FUT1, FUT2 or FUTT.
  • FIG. 6 Another possible variant for demodulating the image and sound components is shown in FIG. 6.
  • the digital demodulator DMF for processing the image components has an additional output for removing the sound components and for forwarding them to the demodulator (s) DMT or DMT1 and DMT2.
  • the sound components can be taken from the DMF demodulator in real or complex form. In the former case they have to be converted again, at ⁇ 14 MHz or already decimated.
  • the versions according to FIG. 1b or FIG. 3b are particularly suitable as sound demodulators, with some or all of the decimation by a factor of 15 being eliminated in the branch of sound signal processing (depending on the transfer sampling frequency of the demodulator DMF for the picture components).
  • the demodulator for the picture components becomes more complex, since the sound carriers TT not only have to be suppressed, but have to be transferred undisturbed.
  • this version offers a maximum of joint signal processing analogous to the intercarrier method.
  • a device ID is provided, which is preferably connected to one of the further or additional decimation filter devices DZ2, DZ3, DZ4, DZ5.
  • DZ2, DZ3, DZ4, DZ5 A particularly advantageous implementation of the ID device with little effort is described in the applicant's application BK 93/96.
  • a known solution is suitable as a demodulator DMF for the image portion, e.g. according to DE 33 05 918 C2.
  • a particularly advantageous demodulator for processing the image portion is described in the applicant's application BK 93/26.
  • the invention makes it possible to design all filters as FIR filters with a linear phase. This means that a universal filter module can be used for all different filter functions (DE 43 05 075.1).

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  • Engineering & Computer Science (AREA)
  • Multimedia (AREA)
  • Signal Processing (AREA)
  • Television Receiver Circuits (AREA)
  • Television Systems (AREA)
EP95106412A 1994-05-20 1995-04-28 Dispositif pour le traitement d'un signal de télévision analogique à valeurs réelles Expired - Lifetime EP0683607B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE4417723 1994-05-20
DE4417723A DE4417723A1 (de) 1994-05-20 1994-05-20 Einrichtung zum Verarbeiten eines modulierten reellwertigen analogen Fernsehsignals

Publications (3)

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EP0683607A2 true EP0683607A2 (fr) 1995-11-22
EP0683607A3 EP0683607A3 (fr) 1996-01-03
EP0683607B1 EP0683607B1 (fr) 1999-01-20

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EP95106412A Expired - Lifetime EP0683607B1 (fr) 1994-05-20 1995-04-28 Dispositif pour le traitement d'un signal de télévision analogique à valeurs réelles

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US (1) US5568206A (fr)
EP (1) EP0683607B1 (fr)
DE (2) DE4417723A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0781040A1 (fr) * 1995-12-22 1997-06-25 THOMSON multimedia Circuit pour réaliser un filtrage de Nyquist numérique de signaux à fréquence intermédiare FI

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DE4444870C1 (de) * 1994-12-16 1995-10-26 Ant Nachrichtentech Demodulator für ein komplexwertiges Restseitenbandsignal
GB9511568D0 (en) * 1995-06-07 1995-08-02 Discovision Ass Signal processing apparatus and method
GB9511551D0 (en) * 1995-06-07 1995-08-02 Discovision Ass Signal processing system
US6738734B1 (en) 1996-08-12 2004-05-18 The United States Of America As Represented By The Administrator Of The National Aeronautics And Space Administration Empirical mode decomposition apparatus, method and article of manufacture for analyzing biological signals and performing curve fitting
US6381559B1 (en) * 1996-08-12 2002-04-30 The United States Of America As Represented By The Administrator Of The National Aeronautics And Space Administration Empirical mode decomposition apparatus, method and article of manufacture for analyzing biological signals and performing curve fitting
US6147713A (en) * 1998-03-09 2000-11-14 General Instrument Corporation Digital signal processor for multistandard television reception
US7054359B2 (en) * 2001-06-05 2006-05-30 Koninklijke Philips Electronics N.V. VSV-MOE pre-equalizer for 8-VSB DTV
CN100414844C (zh) * 2002-03-12 2008-08-27 Nxp股份有限公司 具有信号通路的接收机及方法
US6990436B1 (en) 2003-11-28 2006-01-24 The United States Of America As Represented By The Administrator Of The National Aeronautics And Space Administration Computing frequency by using generalized zero-crossing applied to intrinsic mode functions
DE102005046245A1 (de) * 2005-09-28 2007-04-05 Atmel Germany Gmbh Vorrichtung zum Überführen eines komplexwertigen Bandpaßsignals in ein digitales Basisbandsignal
GB0900045D0 (en) * 2009-01-05 2009-02-11 Astrium Ltd A signal pre-processor for an amplifying system

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EP0204849B1 (fr) * 1985-06-01 1990-08-16 Deutsche ITT Industries GmbH Configuration de circuit pour le filtrage et la démodulation d'un signal modulé en fréquence avec au moins un signal son
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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0781040A1 (fr) * 1995-12-22 1997-06-25 THOMSON multimedia Circuit pour réaliser un filtrage de Nyquist numérique de signaux à fréquence intermédiare FI
FR2742956A1 (fr) * 1995-12-22 1997-06-27 Thomson Multimedia Sa Circuit pour realiser un filtrage de nyquist numerique de signaux a frequence intermediaire fi
US5963273A (en) * 1995-12-22 1999-10-05 Thomson Multimedia S.A. Circuit for carrying out digital Nyquist filtering of IF intermediate frequency signals

Also Published As

Publication number Publication date
DE4417723A1 (de) 1995-11-23
EP0683607B1 (fr) 1999-01-20
DE59504861D1 (de) 1999-03-04
US5568206A (en) 1996-10-22
EP0683607A3 (fr) 1996-01-03

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