EP1479162A2 - Filtre passe-bande voies de signalisation parall les - Google Patents

Filtre passe-bande voies de signalisation parall les

Info

Publication number
EP1479162A2
EP1479162A2 EP03743000A EP03743000A EP1479162A2 EP 1479162 A2 EP1479162 A2 EP 1479162A2 EP 03743000 A EP03743000 A EP 03743000A EP 03743000 A EP03743000 A EP 03743000A EP 1479162 A2 EP1479162 A2 EP 1479162A2
Authority
EP
European Patent Office
Prior art keywords
resonators
filter
main signal
signal paths
input
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP03743000A
Other languages
German (de)
English (en)
Inventor
Uwe Rosenberg
Smain Amari
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Ericsson AB
Original Assignee
Marconi Communications GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Marconi Communications GmbH filed Critical Marconi Communications GmbH
Publication of EP1479162A2 publication Critical patent/EP1479162A2/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/205—Comb or interdigital filters; Cascaded coaxial cavities
    • H01P1/2053—Comb or interdigital filters; Cascaded coaxial cavities the coaxial cavity resonators being disposed parall to each other
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H01P1/2084—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators

Definitions

  • the present invention relates to a bandpass filter for an electrical or electromagnetic signal, in particular for a high-frequency signal.
  • filters play an important role in the design of components for modern telecommunications systems.
  • the requirements that are generally placed on such filters include steep filter edges, high blocking attenuation, uniform phase shift in the passage area, etc.
  • Different types of filters such as Cauer, Tschebyscheff, Butterworth or Bessel filters, are distinguished, each of which is one or meet other of these requirements particularly well.
  • All these filters have in common that they are made up of one or more resonators.
  • the individual resonators are connected in series, so that there is a single signal path through the filter, on which a signal passes through all the resonators in sequence.
  • the slope, blocking damping etc. that can be achieved with such an arrangement of resonators is determined, inter alia, by the number of resonators.
  • Filters synthesized with such methods always have a main signal path that runs through all resonators of the filter and in addition to the main signal path one or more secondary signal paths which run from the input to the output of the filter via at least one coupling between resonators which are not adjacent on the main signal path and which therefore detect a smaller number of resonators than the main signal path.
  • B1 bandpass filters which have two main signal paths, i.e. two first signal paths, for which a second signal path does not exist, as does the secondary signal paths of the conventional filter structures, which runs through all the resonators of the first path in the same order and which has one or more further resonators between at least two resonators immediately following one another on the first path.
  • These main signal paths of these known filters each have an input or output resonator connected to the input or the output in common.
  • the object of the present invention is to provide a bandpass filter, the structure of which allows a simpler, faster and therefore cheaper filter implementation than previous filter structures.
  • the filter according to the invention is characterized in that the plurality of main signal paths which run from its input to its output do not have any common resonators at the input and / or at the output, that is to say that they are connected to the input and / or the output via different resonators in each case are.
  • a change made to one of the main signal paths can influence the behavior of the other main signal path at most via a single common resonator at the input or output of the filter and is therefore easy to handle in a simulation.
  • the main signal paths preferably have no common resonators at either the input or the output of the filter. Then there is no mutual influence on the main signal paths and they can be optimized completely independently of one another.
  • the advantage of the filter structure according to the invention is that its main signal paths can be implemented with less effort than those of the conventional filter due to their smaller number of circles, and that changes that are made in the course of the optimization on a resonator that only belongs to one of the main signal paths essentially only affect the transfer function of this main signal path and leave the other main signal paths unaffected. So the problem of realizing an n-pole filter are broken down into the implementation of a plurality of sub-filters, each with a smaller number of circles, corresponding to a main signal path, these sub-filters each having free parameters that can be optimized without changing the transfer functions of the other sub-filters.
  • the filter structure according to the invention is applicable to a large number of filter types, which are described below in conjunction with the figures using
  • FIG. 3 shows the transmission and reflection function of a filter which can be implemented with the structure according to FIG. 1 a or according to FIG. 2;
  • Figure 5 is a schematic perspective view of a filter according to the invention with rectangular cavity resonators.
  • FIG. 6 shows a perspective, partially cut-open view of a filter with four dielectric loaded resonators
  • 7a, b show two sections through a first modification of the filter from FIG. 6; 8a, b show two sections through a second modification of the filter from FIG. 6;
  • FIG. 9 is a perspective, partially cutaway view of a filter with four coaxial resonators
  • FIG. 10 shows a view of a filter with four stripline resonators and the structure according to FIG.
  • FIG. 11 is a schematic perspective view of a filter with cavity resonators using higher wave types.
  • FIG. 12 shows a schematic illustration of the magnetic fields in the resonators of the filter from FIG. 10.
  • Figs. 1 a to 1 b each show a filter structure according to the invention in comparison to the conventional filter structure of FIG. 2.
  • a signal path extends from the input S of the filter to the output L, which passes through all four resonators 1 to 4 of the filter in sequence.
  • the resonators 1 to 4 of the main signal path are each strongly coupled to one another, so that the comparatively weak direct coupling of the resonators 1 and 4 to one another via the secondary signal path 5 shown in broken lines in the calculation of the behavior of the filter as a disturbance of the filter essentially characterized by the main signal path can be treated.
  • the filters of Figs. la, lb no main signal path to which all resonators belong. Instead, there are two main signal paths, which in the case of FIG. 1 a are formed by the resonators 1, 2 or 3, 4 and in the case of FIG. 1 b by the resonator 1 or the resonators 2 to 4.
  • FIG. 3 shows the course of the transmission characteristic, shown as a solid curve 8, and the reflection characteristic, shown as a dashed curve 9, of a filter with four resonators.
  • the characteristics 8, 9 are with a filter of the structure shown in Fig. 2 by means of that shown in Fig. 4a
  • Matrix of coupling coefficients achievable The elements of the matrix that are in the positions directly adjacent to the main diagonal correspond to the coupling coefficients of the main signal path. Since all of these positions have non-zero values, the filter has exactly one main signal path. All elements of the matrix that are neither in these positions nor on the main diagonal represent overcouplings of secondary signal paths. In FIG. 4a, these are elements 14 and 41, respectively, which describe a coupling of resonators 1 and 4.
  • the direct coupling between the resonators 1 and 4 is substantially smaller than the coupling coefficients of the main signal path, so that the direct coupling can be understood as a small correction of the signal transmitted mainly on the main signal path.
  • the course of transmission and reflection functions shown in FIG. 3 can also be achieved with the filter structure according to FIG. 1 a, on the basis of the coupling matrix shown in FIG. 4 b.
  • the coupling coefficients of the two main signal paths S, 1, 2, L and S, 3, 4, L have magnitudes of a similar magnitude, although the product of the coupling coefficients on the signal path S, 1, 2, L is positive on the signal path S, 3, 4, L, however, is negative.
  • Fig. 5 shows a practical embodiment of a filter with the structure shown in Fig. La.
  • Input and output S and L are designed as connectors 15 and 16 for a rectangular waveguide for the transmission of a microwave signal.
  • two iris diaphragms IS1, IS2 are formed, each of which opens onto a cuboid resonator cavity 11 or 13, which embodies the resonator 11 or 13 of FIG.
  • a microwave signal present at the input connector 15 thus excites the HiQi wave type of the resonator cavities 11 and 13, respectively.
  • the coupling coefficients between the input and the resonators 1 and 3 are due to the shape of the
  • Iris diaphragms ISl and IS3 defined.
  • the iris diaphragms IS1, IS3 extend from a broad side on which the resonator cavities 11, 13 lie opposite, from about half the height (in the y direction) of the cavities and centered in the width direction (x direction) approximately half of their width.
  • the coupling of the two resonators 1, 3 to the input S is therefore predominantly inductive, which by convention can be equated to a coupling coefficient with a positive sign.
  • Iris diaphragms 112 are located in an opposite end face of the resonator cavities 11, 13 or 134, which open into cavities 12, 14 arranged in series and embodying the resonators 2 and 4, respectively. Except for the amount of the coupling coefficient, the position and shape of the iris diaphragm 112 corresponds to that of ISl, so that the coupling between the resonators 1 and 2 is again inductive; the iris diaphragm 134, on the other hand, is slit-shaped and extends in the immediate vicinity of a side wall of the cavity walls 13, 14 over its entire width (in the x direction) and is therefore capacitive. A negative coupling coefficient between the resonators 3, 4 is thus obtained.
  • Iris diaphragms I2L, I4L which couple the resonator cavities 12, 14 to the output connection 16, in turn have the same shape as the iris diaphragms IS1, IS3. Adjustments to the resonator frequencies of the cavities 11 to 14, which may be necessary due to the different couplings between the resonators, are achieved by adjusting the widths of the cross sections or other tuning means known from the prior art, e.g. Screws, pins etc.
  • Output L requires only minor corrections because the interaction between the two is small.
  • the development or production is thus reduced to the implementation of two partial filters, consisting of the resonators 1, 2 or 3, 4, which is considerably simpler than the conventional development or the adjustment of a filter with four resonators connected in series, and also the sensitivity of the behavior of a finished Filters against manufacturing scatter decrease because the effects of such scatter in one main signal path are essentially limited to this and do not affect the second or possibly other main signal paths that may be present in more complex filter structures than the one shown here.
  • FIG. 6 shows a second exemplary embodiment of a filter according to the invention with the structure shown schematically in FIG.
  • a housing 20 surrounds an interior which is divided into four chambers 22 to 25, which form the four resonators 1, 2, 3, 4, by a centrally arranged intermediate wall 21 with a cruciform plan.
  • a dielectric body 26 is held firmly on the bottom of the housing 20 via a spacer 27, and a tuning body 28 is slidably held opposite the dielectric body 26 in the ceiling of the housing 20.
  • the resonance frequency of each resonator is essentially determined by the dielectric body 26, a possibly necessary fine adjustment of the frequency by the respective tuning body 28 being possible.
  • the spacer element 27 is made of a dielectric material, but with a significantly lower dielectric constant than the body 26.
  • the input and output S, L of the filter are formed by coaxial line sections 30 and 31, the outer conductors 32 of which are each connected to the housing 20, while their inner conductor 33 is short-circuited on the intermediate wall 21.
  • the coupling coefficients between the input S, the various resonators 1, 2, 3, 4 and the output L can be adjusted with the aid of tuning screws 34, 35.
  • Tuning screws 34 guided through the bottom of the housing 20 at a short distance from the inner conductor 33 determine the Coupling from the input S to the resonators 1, 3.
  • Screws arranged in mirror image to the screws 34 in the vicinity of the output L for adjusting the coupling between the resonators 2 and 4 and the output L are hidden in the figure and not visible.
  • the tuning screws 35 which are embedded in the side walls of the housing 20 and each have their tips opposite a transverse plate of the cross-shaped intermediate wall 21, serve to set the coupling between the resonators 1 and 2 or between 3 and 4.
  • Figs. 7a, 7b show a first modification of the filter from FIG. 6. Elements which correspond to one another are identified by the same reference symbols. Between the chambers 22 and 23 or 24 and 25, the intermediate wall 21 is enlarged, so that only a circular hole 29 remains as a coupling opening between the chambers 22, 23 and 24, 25, respectively. A metal wire 36 or 37 is passed through each of these holes 29 and connected at its two ends to opposite surfaces of the wall 21. The metal wires 36, 37 each produce a loop coupling between the pairs of chambers operated as H ⁇ o ⁇ resonators.
  • the metal wire 36 is circularly curved in a horizontal plane, its two ends touching the wall 21 are facing each other.
  • the metal wire 37 is bent in an S-shape in the same horizontal plane; its two ends touch the wall 21 on opposite sides of the hole 29 through which it is guided. If one assumes that the wave types excited in the chambers 22, 24 are each in phase, it is easy to understand that the different geometries of the metal wires 36, 37 in the chambers 23, 25 each have magnetic fields with opposite directions of rotation or a phase difference of ⁇ are excited, ie the coupling coefficients between the resonators 1, 2 on the one hand and the Resonators 3, 4, on the other hand, have opposite signs.
  • the intermediate wall 21 is here the same as in the variant of FIGS. 8a, 8b, a metal wire 38 or 39 running through the holes 29 of the intermediate wall 21 is not connected at its ends to the wall 21, but is respectively held in its hole 29 by a dielectric body which fills the hole 29 and transmits the electromagnetic waves , and its ends protrude freely into the chambers.
  • FIG. 9 shows a third embodiment of a microwave filter with the structure of FIG.
  • Input S and output L of the filter are formed by rectangular waveguide sections 40, 41 with a reduced height compared to subsequent waveguide sections 42.
  • the waveguide sections 40, 41 forming the input or output are connected by two passages 43, 44.
  • Each of these passages 43, 44 comprises two resonators 1, 2 and 3, 4, respectively in the form of a conductive, here cylindrical resonator body 45, which is galvanically connected to a bottom of the passage 43, 44 and which becomes electrical by a microwave signal present at the input S.
  • each resonator body 45 is determined by its dimensions and the distance from it Tuning screw 47 arranged opposite in an upper wall 46 of the filter. Tuning screws 47 are shown in FIG. 7 only for the resonator body 45 of the passage 43, but corresponding tuning screws, not shown, are also for the
  • Resonator body 45 of the passage 44 is present.
  • the passage 43 is free between the resonator body 45, apart from a tip of a tuning screw 48 which is inserted into the passage and which serves to tune the coupling between the two resonators of the passage 43.
  • the passage 44 is blocked between its two resonator bodies 45 on part of its cross section by a partition 49.
  • a tuning screw, not shown, which is arranged in the wall 46 in the same way as the tuning screw 48 shown for the passage 43 and lies opposite the upper edge of the partition 49, enables the coupling coefficient between the resonators 3, 4 of the passage 44 to be matched.
  • the partition 49 in the passage 44 achieves a capacitive coupling of the resonators 3, 4.
  • FIG. 10 shows the application of the principle of the invention to a filter in which resonators 1, 2, 3, 4 are formed by strip conductors 61 to 64 of length ⁇ / 2 structured on a substrate 60, where ⁇ is the wavelength of a propagating in the strip conductors Signal is in the passband of the filter.
  • the stripline resonators 61, 62, 63, 64 couple to one another and to an input conductor S or an output conductor L by extending parallel and closely adjacent over part of their length.
  • the stripline S, 61, 62, L are formed by the stripline S, 61, 62, L.
  • Main signal path the strip conductors 61, 62 are each arranged in such a way that the signal propagation direction from the input S to the output L, each represented by arrows, is oriented in the same direction in the mutually coupling sections of the strip conductors. In this way, the same sign of the for all couplings on the main signal path S, 61, 62, L
  • the length of the stripline resonators can be n ⁇ / 2, where n is a small natural number. If n is greater than 1, it is also possible to achieve different signs of the coupling coefficients on the main signal paths
  • FIG. 11 and 12 show a further exemplary embodiment of a filter according to the invention which, like the exemplary embodiment of FIG. 5, is constructed from cavity resonators.
  • This filter shown in a perspective view in FIG. 12 comprises only three
  • 12 shows a schematic sectional illustration of the basic field distribution in the resonators.
  • the Hl03 wave type is used in the cavity resonators 2, 3, 4, illustrated by magnetic field lines running in three closed circles in the resonators.
  • the coupling coefficients on the individual iris diaphragms are determined by their position relative to the field distribution in the cavities that connect them, and by their cross-sectional area.
  • the apertures IS2, IS3 each couple the last half-wave of the input S in the signal propagation direction (from left to right in FIG. 12) to the first half-wave of the resonators 2 and 3, respectively.
  • the magnetic fields of the first half-waves excited in the resonators accordingly have one to the last Half wave of the input S opposite direction of rotation, indicated by the arrows marked on the circles.
  • the diaphragms 124 and 134 are placed in such a way that the first half-wave of the resonator 4 essentially couples to the third half-wave of the resonator 3 and the second half-wave of the resonator 2, i.e. to half-waves with opposite signs. Coupling coefficients with different signs for the coupling to the aperture 134 and to the aperture 124 on the other hand can also be realized in this way.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Filters And Equalizers (AREA)

Abstract

L'invention concerne un filtre passe-bande comprenant une pluralité de résonateurs (1, 2, 3, 4) interconnectés entre une entrée (S) et une sortie (L) du filtre, à au moins deux voies de signalisation principales (S, 1, 2, L ; S, 3, 4, L) menant de l'entrée (S) à la sortie (L). Les au moins deux voies de signalisation principales (S, 1, 2, L ; S, 3, 4, L) présentent des bandes de passage qui se chevauchent et sont reliées à l'entrée (S) et/ou à la sortie (L) par l'intermédiaire de différents résonateurs (1, 3 ; 2, 4).
EP03743000A 2002-02-28 2003-02-28 Filtre passe-bande voies de signalisation parall les Withdrawn EP1479162A2 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE10208666 2002-02-28
DE10208666A DE10208666A1 (de) 2002-02-28 2002-02-28 Bandpassfilter mit parallelen Signalwegen
PCT/IB2003/001061 WO2003073606A2 (fr) 2002-02-28 2003-02-28 Filtre passe-bande à voies de signalisation parallèles

Publications (1)

Publication Number Publication Date
EP1479162A2 true EP1479162A2 (fr) 2004-11-24

Family

ID=27675107

Family Applications (1)

Application Number Title Priority Date Filing Date
EP03743000A Withdrawn EP1479162A2 (fr) 2002-02-28 2003-02-28 Filtre passe-bande voies de signalisation parall les

Country Status (6)

Country Link
US (1) US7317365B2 (fr)
EP (1) EP1479162A2 (fr)
CN (1) CN1639973A (fr)
AU (1) AU2003209928A1 (fr)
DE (1) DE10208666A1 (fr)
WO (1) WO2003073606A2 (fr)

Families Citing this family (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE10304524A1 (de) * 2003-02-04 2004-08-12 Tesat-Spacecom Gmbh & Co.Kg Topologie für Bandpassfilter
EP1538692A1 (fr) * 2003-12-05 2005-06-08 Alcatel Filtre en guide rectangulaire à pôles extraits
EP2056394B1 (fr) * 2007-10-31 2013-09-04 Alcatel Lucent Résonateur à cavité
RU173175U1 (ru) * 2016-11-18 2017-08-15 Общество с ограниченной ответственностью "Научно-технологическое бюро "Радиационно-технологическое проектирование" Высокоизбирательный полосно-пропускающий фильтр
US11211676B2 (en) * 2019-10-09 2021-12-28 Com Dev Ltd. Multi-resonator filters
CN112652871A (zh) * 2020-12-16 2021-04-13 吉林大学 一种三阶环形宽带带通等波纹滤波器及其设计方法
CN113241507A (zh) * 2021-05-10 2021-08-10 南京智能高端装备产业研究院有限公司 一种基于堆叠结构的矩形腔体带通滤波器

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Also Published As

Publication number Publication date
DE10208666A1 (de) 2003-09-04
CN1639973A (zh) 2005-07-13
US20050212622A1 (en) 2005-09-29
WO2003073606A2 (fr) 2003-09-04
WO2003073606A3 (fr) 2003-11-13
AU2003209928A1 (en) 2003-09-09
AU2003209928A8 (en) 2003-09-09
US7317365B2 (en) 2008-01-08

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