EP2109183A1 - Amélioration portant sur l'isolation d'une antenne - Google Patents

Amélioration portant sur l'isolation d'une antenne Download PDF

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Publication number
EP2109183A1
EP2109183A1 EP09445009A EP09445009A EP2109183A1 EP 2109183 A1 EP2109183 A1 EP 2109183A1 EP 09445009 A EP09445009 A EP 09445009A EP 09445009 A EP09445009 A EP 09445009A EP 2109183 A1 EP2109183 A1 EP 2109183A1
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EP
European Patent Office
Prior art keywords
antenna element
feeders
dual polarized
polarized antenna
compensation line
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
EP09445009A
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German (de)
English (en)
Inventor
Björn LINDMARK
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Intel Corp
Original Assignee
Powerwave Technologies Sweden AB
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Powerwave Technologies Sweden AB filed Critical Powerwave Technologies Sweden AB
Publication of EP2109183A1 publication Critical patent/EP2109183A1/fr
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0428—Substantially flat resonant element parallel to ground plane, e.g. patch antenna radiating a circular polarised wave
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means
    • H01Q9/0457—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means electromagnetically coupled to the feed line

Definitions

  • the present invention relates to a dual polarized antenna element and an antenna array, in which the antenna element includes:
  • Dual polarised or X-polarised antennas are today commonly used in cellular systems for mobile communication.
  • the use of such antennas allows the use of polarisation diversity techniques to combat signal fading in the system.
  • Compared to the use of vertical polarised antennas and space diversity techniques the number of antennas needed is reduced to half, which saves costs and reduces the size and the visual appearance of the antenna installations.
  • One important performance measure for dual polarised antennas is the isolation between the two antenna ports feeding the two polarisations. Typically, an isolation of more than 30 dB between the ports is wanted, which corresponds to a power coupling of less than 1/1000 between the ports.
  • An aperture coupled patch antenna element is a commonly used antenna type for dual polarised systems.
  • one or more metallic patches are fed by a micro strip feeding arrangement through a cross shaped aperture in a ground plane, as is shown in figure 1 .
  • the antenna element 101 includes a radiating patch 103, fed through an aperture 109 by a microstrip feed line 105 positioned between a shielding cage 102 and a printed circuit board.
  • Isolation between a transmitting and a receiving signal path in a dual polarized antenna has been described in, for instance, prior art document US6509883 .
  • a signal being transmitted from a first antenna element having one polarisation is received by a second antenna element having another polarisation, thereby causing an unwanted signal to be received by the second antenna element.
  • a compensation path is arranged between the transmitting and receiving signal paths, where the compensation path has a length such that the compensation signal travelling through the compensation path and the unwanted signal have equal magnitude and opposite phase when they meet in the receiving signal path.
  • the compensation path as well as the transmitting and receiving signal paths have to be adapted to have certain lengths in order to be able to cancel out the unwanted signal, having been transmitted from the first antenna and received by the second antenna, since a difference in length of an odd number of half wavelengths has to be present between the paths travelled by the unwanted signal and the compensation signal.
  • the antenna element shown in this document has to have a certain size to achieve efficient cancellation, which is disadvantageous.
  • the present invention aims to provide a dual polarised antenna element, which offers improved antenna isolation for all kinds of essentially capacitive couplings between the feeders.
  • the present invention thus aims to provide compensation for capacitive coupling between the feeders, also including a capacitive coupling occurring via the radiating part, for example a radiating patch, of the antenna element.
  • the object is for a dual polarized antenna element achieved by the use of:
  • the object is also achieved by an antenna array including at least two such dual polarized antenna elements.
  • the present invention achieves compensation of mutual coupling in dual polarized antenna elements using a compensation line being connected between the input ports.
  • this compensation line is short in relation to the wavelength, this connection will act as an inductive element well suited to compensate for the capacitive mutual coupling in the antenna element.
  • the dual polarised antenna element according to the present invention has the advantage that it can provide good antenna isolation through an efficient compensation for essentially all types of capacitive coupling between the feeders in the antenna element, including capacitive coupling between the feeders and the radiating part of the antenna element.
  • the compensation is achieved by the use of a compensation line, which is small in size, not costly to produce, easy to implement and which efficiently cancels out the capacitive coupling being present by its inductive character.
  • the dual polarized antenna element is of the aperture coupled patch antenna type.
  • Each feeder here includes a pair of feed lines extending along slots of a cross shaped aperture such that the feed lines cross each other at a mutual distance, resulting in a capacitive coupling between the feeders.
  • Such a crossing can be arranged as an air-bridge.
  • this capacitive coupling is cancelled by the high impedance connection between the feeders.
  • Dual polarized antenna elements commonly suffer from imbalance due to mutual coupling for various reasons. Even though an antenna element may show a geometrical symmetry to a large extent, including the radiating part and the majority of the feed network, we typically have one or more points of asymmetry causing mutual coupling.
  • Fig. 2 shows one example of this for a patch antenna element including a ground plane 202, a top patch 203 and a lower patch 204.
  • an electromagnetically coupled patch element is fed by two orthogonal feeders 205, 206, both with a capacitive coupling to the two stacked patches.
  • the antenna element is here not symmetrical, since the feeder connections are not symmetrical. For example, if we look into the element along for example the feeder 205 at the bottom of the figure, we see that only one side (the left side) of the other sides of each patch is loaded by another feeder 206, while the other sides (for instance the right side) have an open circuit. Thus, the antenna element is not symmetrical around the plane of the dashed line 207, since there is no feeder connection at the right side of the antenna element.
  • each of the feeders 305, 306, feeding a polarization includes a pair of feed lines 307, 308 extending in parallel along the cross shaped aperture 309, respectively, such that a two of those feed lines cross each other in one point 310.
  • This at least one crossing 310 is typically achieved by using an air bridge for one of the polarizations. This air bridge crossing destroys the symmetry of the antenna element and imposes a capacitive coupling between the two feeders 305, 306.
  • These antenna elements 401 are dual polarized antenna elements and include a first feeder 405 for feeding said antenna element 401 in a first polarization direction.
  • the first feeder 405 has a connection port P1.
  • the antenna elements 401 further have a second feeder 406 for feeding said antenna element 401 in a second polarization direction, also being provided with a connection port P2.
  • Fig. 4a schematically illustrates a general dual polarized antenna element 401, being fed by two feeders 405, 406, having mutual coupling between them.
  • each one of the feeders 405, 406 includes a pair of feed lines 407, 408 extending in parallel along the cross shaped aperture 409, on each side thereof, respectively, such that two of those feed lines 407, 408 cross each other in one point 410, typically being arranged as an air bridge.
  • Such an antenna structure could also result in more than one crossing of feed lines, depending on the shape of the feed lines.
  • a compensation line 420 is arranged between said first and said second feeders 405, 406.
  • the compensation line 420 should be connected to the first and second feeders 405, 406 in a point on each of the feeders that is in close proximity to a radiating part of the antenna element.
  • the mutual coupling between the feeders is of an essentially capacitive character and can be cancelled by the compensation line 420, if the compensation line 420 has an essentially inductive character.
  • This is, according to the present invention, achieved by arranging the compensation line 420 such that its electrical length ⁇ is short and that it is thin such that it has high impedance relative to an impedance of the first and second feeders 405, 406.
  • the electrical length ⁇ of the compensation line 420 should be small, preferably being less than 2n/3 rad, thus ⁇ ⁇ 2n/3 rad.
  • the electrical length ⁇ of the compensation line 420 should be small, preferably being less than 2n/3 rad, thus ⁇ ⁇ 2n/3 rad.
  • other lengths than this could be advantageous for different implementations.
  • the compensation line 420 should have an impedance that is at least twice as high as the impedance for the feeders 405, 406.
  • the electrical length ⁇ is, as is well known for a person skilled in the art, a length that is related to the wavelength of the signal being transmitted.
  • the compensation line 420 being connected between the first and second feeders 405, 406 a novel method of coupling the polarisations together via an essentially inductive connection is used, in such way that the magnitude and phase of this coupling cancels the mutual coupling in other parts of the antenna element.
  • a required isolation level is achieved at low cost, which is small in size and easy to implement.
  • the compensation line 420 is implemented by a high impedance microstrip line in close proximity of the radiating patch 403.
  • the compensation line 420 should have a short electrical length ⁇ and have an impedance, which is much higher than the impedance for the feeders.
  • the feeders 405, 406 can have an impedance of around 50 ⁇ , whereas the compensation line has an impedance of around 220 ⁇ .
  • the compensation line is connected to the first feeder 405 at a first distance D 1 from the radiating part of the antenna element, for instance a radiating patch.
  • the compensation line is also connected to the second feeder 406 at a second distance D 2 from the radiating part.
  • the first and second distances should be very short relative to the wavelength of the transmitted signal.
  • the first and second distances should preferably be much less than half of the wavelength of the transmitted signal, and more preferably much less than a quarter of the wavelength of the transmitted signal, in order to efficiently cancel the capacitive coupling between the feeders.
  • D 1 ⁇ ⁇ /2 and D 2 ⁇ ⁇ /2 preferably D 1 ⁇ ⁇ /4 and D 2 ⁇ ⁇ /4.
  • Such a capacitive coupling can occur in any situation where a feeder or a feed line of one polarization is close to a feeder or a feed line of another polarization. Such a situation can thus occur in an air-bridge, but also somewhere else in the antenna element, where feeders run in close distance to each other. Also, as is exemplified below, there can be a capacitive coupling between one or both of the feeders and the radiating part of the antenna.
  • An antenna element with two input ports is represented by a scattering matrix S or by an impedance matrix Z , both being of the dimension 2 X 2.
  • Each port here corresponds to one of the two orthogonal polarizations of the radiated wave.
  • S 21 2 ⁇ Z 21 ⁇ Z 0 Z 11 + Z 0 ⁇ Z 22 + Z 0 - Z 12 ⁇ Z 21
  • Fig. 5 we have a second 2 X 2 matrix defined by S M or Z M .
  • S M loss-less matrix
  • Z M the coupling from port 1' to 2' is zero. This could be done by using, e.g., a directive coupler.
  • the mutual coupling often includes capacitive coupling between at least one of the first and second feeders and the radiating part, here being a patch, of said antenna element.
  • Fig. 6a shows an antenna element defined by a matrix Z with mutual coupling represented by a capacitance C. Note that the ground reference line in Fig. 5 here has been removed for clarity. Fig 6a also shows a compensation connection in the form of an inductance L, in accordance with the present invention.
  • Equation (7) shows that, in order to have zero coupling when X is real, we need to have X ⁇ ⁇ .
  • this inductive compensation line can be implemented as a connection between the feeders having a short electrical length and being thin, such that it has a high impedance in relation to the feeder impedance.
  • a high impedance transmission line should correspond to a large inductance.
  • High impedance means high impedance relative to the impedance of the feeders used for feeding the polarizations.
  • the electrical length ⁇ of the compensation line should be much less than 1 rad, in order to a result in an approximated expression.
  • the electrical length ⁇ should preferably be less than 2n/3 rad, thus ⁇ ⁇ 2n/3 rad. This electrical length also results in a compensation line having an essentially inductive character.
  • the electrical length ⁇ of the essentially inductive compensation line is longer than 2n/3 rad.
  • the feeders can have an impedance of 50 ⁇
  • the compensation line can have an impedance of more than twice the feeder impedance, for instance 220 ⁇ .
  • the compensation line can, for instance, be implemented as a 0.5 mm wide microstrip line.
  • the patches can have a size of, for instance, 66 mm or 56 mm.
  • the antenna element of the present invention has been designed and simulated for signals in the frequency interval 1800 MHz to 2200 MHz.
  • the inventive idea of the present invention may, however, also be implemented in other frequency intervals, as is clear to a skilled person.
  • dual polarised antenna elements of the present invention are arranged in an antenna array.
  • the two polarisations of two patches of two antenna array elements are each fed by a first feeder and a second feeder.
  • a compensation line between the first and second feeders in close proximity of each of the patches, respectively, thereby enhancing the antenna isolation of the antenna elements of the array.
  • such an antenna array can include essentially any number of dual polarized antenna elements according to the present invention.
  • the antenna isolation of the present invention is combined with other techniques for improving antenna isolation, being any one of the techniques of parasitic impedances and/or shield wall and/or asymmetrical/ rectangular patches and/or diagonal apertures and/or shifted feed positions.
  • Such a combination has the advantage of even further enhancing the level of isolation.
  • the present invention can be used on essentially any dual polarised antenna element, although, for illustrational reasons, it is mainly described in terms of patch antennas, such as aperture coupled patch antennas, in this specification.
  • Figs. 8-10 show simulations of coupling, reflection and radiation patterns for a dual polarised patch antenna element according to prior art and according to the present invention.
  • Figs. 8a , 9a and 10a show simulations for a prior art antenna, basically an antenna element as the one shown in fig. 2 .
  • Figs. 8b , 9b , and 10b show simulations for an antenna element according to the present invention, more specifically for an antenna element as the one shown in fig. 4c , having a compensation line arranged between the feeders.
  • a microstrip line has been used as the compensation line 420, the microstrip line being implemented as a 0.5 mm wide line resulting in an impedance of 220 ⁇ for the compensation line 420.
  • the first and second feeders 205, 206, 405, 406 feeders here have an impedance of 50 ⁇ .
  • a current division between the 50 ⁇ impedance of the first and second feeders 405, 406 and the 220 ⁇ impedance of the compensation line 420 will take place in the antenna element according to the present invention.
  • the mutual coupling 830 is much lower for the antenna element of the present invention (shown in fig. 8b ), as for the prior art antenna element (shown in fig. 8a ). Note here that the two diagrams have differing scales.
  • the antenna element of the present invention thus has a coupling being around 30 dB between the feeder ports.
  • the reflection 840 is more or less similar for the prior art antenna element and the antenna element of the present invention.
  • the cross polarisation, E_cross is greatly improved for the antenna element according to the present invention ( fig. 9b ), as compared to the prior art antenna element ( fig. 9a ).
  • THETA is here defined as the angle from a z-axis being perpendicular to both the x-axis and y axis in the system of coordinates defined in fig. 4c .
  • the radiation pattern in the direction of the polarisation, E_co, is very similar for both the prior art antenna element ( fig. 9a ) and for the antenna element of the present invention ( fig. 9b ). This tells us that that we have not deteriorated that characteristic of the radiation at the same time as we have gained a lot for the cross polarisation.
  • the radiation pattern in the direction of the polarisation, E_co, is also here not deteriorated by the compensation line of the present invention.
  • the coupling isolation (E_cross) for the radiation pattern for the antenna array has shown to be more than 23 dB.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Waveguide Aerials (AREA)
EP09445009A 2008-04-11 2009-03-27 Amélioration portant sur l'isolation d'une antenne Ceased EP2109183A1 (fr)

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SE0800827A SE532279C2 (sv) 2008-04-11 2008-04-11 Förbättrad antennisolation

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Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102842755A (zh) * 2012-07-11 2012-12-26 桂林电子科技大学 适用于无线局域网的双极化天线及其制作方法
CN102842756A (zh) * 2012-09-24 2012-12-26 桂林电子科技大学 双极化mimo天线阵
CN110996496A (zh) * 2019-12-24 2020-04-10 珠海纳睿达科技有限公司 电路板、天线组件和双极化天线
EP3560111A4 (fr) * 2016-12-21 2020-12-02 Intel Capital Corporation Technologie de communication sans fil, appareils, et procédés
CN113555674A (zh) * 2020-04-24 2021-10-26 深圳市万普拉斯科技有限公司 天线装置及移动终端

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111355029B (zh) * 2020-04-09 2021-09-28 西安电子科技大学 用于第五代通信系统的高性能双极化微带天线

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Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102842755A (zh) * 2012-07-11 2012-12-26 桂林电子科技大学 适用于无线局域网的双极化天线及其制作方法
CN102842755B (zh) * 2012-07-11 2015-07-22 桂林电子科技大学 适用于无线局域网的双极化天线及其制作方法
CN102842756A (zh) * 2012-09-24 2012-12-26 桂林电子科技大学 双极化mimo天线阵
CN102842756B (zh) * 2012-09-24 2015-07-22 桂林电子科技大学 双极化mimo天线阵
EP3560111A4 (fr) * 2016-12-21 2020-12-02 Intel Capital Corporation Technologie de communication sans fil, appareils, et procédés
US11424539B2 (en) 2016-12-21 2022-08-23 Intel Corporation Wireless communication technology, apparatuses, and methods
TWI782936B (zh) * 2016-12-21 2022-11-11 美商英特爾公司 無線通訊之技術、設備及方法
US11955732B2 (en) 2016-12-21 2024-04-09 Intel Corporation Wireless communication technology, apparatuses, and methods
US12237589B2 (en) 2016-12-21 2025-02-25 Intel Corporation Wireless communication technology, apparatuses, and methods
CN110996496A (zh) * 2019-12-24 2020-04-10 珠海纳睿达科技有限公司 电路板、天线组件和双极化天线
CN113555674A (zh) * 2020-04-24 2021-10-26 深圳市万普拉斯科技有限公司 天线装置及移动终端
CN113555674B (zh) * 2020-04-24 2023-03-17 深圳市万普拉斯科技有限公司 天线装置及移动终端

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SE0800827L (sv) 2009-10-12

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