EP2289165A2 - Procédé de fonctionnement d'un circuit oscillant comportant au moins deux commutateurs électroniques et circuit oscillant correspondant - Google Patents

Procédé de fonctionnement d'un circuit oscillant comportant au moins deux commutateurs électroniques et circuit oscillant correspondant

Info

Publication number
EP2289165A2
EP2289165A2 EP09757587A EP09757587A EP2289165A2 EP 2289165 A2 EP2289165 A2 EP 2289165A2 EP 09757587 A EP09757587 A EP 09757587A EP 09757587 A EP09757587 A EP 09757587A EP 2289165 A2 EP2289165 A2 EP 2289165A2
Authority
EP
European Patent Office
Prior art keywords
circuit
resonant
resonant circuit
current
switches
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP09757587A
Other languages
German (de)
English (en)
Inventor
Thomas Komma
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
BSH Hausgeraete GmbH
Original Assignee
BSH Bosch und Siemens Hausgeraete GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by BSH Bosch und Siemens Hausgeraete GmbH filed Critical BSH Bosch und Siemens Hausgeraete GmbH
Publication of EP2289165A2 publication Critical patent/EP2289165A2/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type

Definitions

  • the invention relates to a method for operating a resonant circuit with at least two electronic switches, in particular MOSFETs, and such a resonant circuit.
  • a wireless energy transfer can be made inductively by using special transformers whose primary and secondary sides are separable by the user during operation.
  • One possibility for generating the primary voltage is formed by resonant converters, in which a resonant circuit is excited by means of electronics and a sinusoidal voltage is coupled out parallel to its resonant circuit capacitance. Since the leakage inductance Ls and the main inductance Lh of the transformer, which change with distance, form part of the oscillating circuit, the resonant frequency is shifted when the two transformer sides are disconnected or during operation with mutually offset transformer halves. In the worst case, the operating mode changes from over-resonant operation to the sub-resonant mode, which can lead to the destruction of the power semiconductors.
  • the connection of the primary and secondary side is detected by measuring the secondary load current or with the aid of micro-probes or optocouplers.
  • this is structurally complex and prone to failure.
  • Auxiliary windings in the primary-side transformer half also detect separate transformer halves, but due to their slow detection can not prevent destruction of the power semiconductors.
  • Another way to prevent destruction is the überresonante operation with a sufficiently large distance from the resonant frequency, but this has a poor utilization of the power components result. It is the object of the present invention to provide a possibility for the operation of a resonant circuit with semiconductor components, which protects the semiconductor components in the case of a subresonant operation with simultaneous good utilization.
  • the method is used to operate a resonant circuit with at least two electronic switches.
  • the resonant circuit is switched off, if substantially during the switching off and / or after switching off (in particular immediately after switching off) one of the switches, a current through this switch reaches or falls below a predetermined threshold value.
  • This method has the advantage that it switches very quickly and requires little or only easily implementable and also insensitive additional components. Thus, to detect the subresonance, it is not necessary to scan and evaluate several oscillations.
  • a current through the / the switch on a coil, in particular inductor, the resonant circuit is tapped.
  • the choke coil is preferably a choke coil common to a plurality of switches.
  • the use of the current in a resonant choke is particularly advantageous because it is already monitored in resonant circuits, in particular resonant converters, so that overcurrents due to very different load resistances can not occur. Therefore, no additional current transformer is needed.
  • the stream can also be sensed at a suitable other location, z. B. directly on the transistor. It is advantageous for energy transfer with high efficiency, if the resonant circuit is designed for resonant excitation, in particular as a resonant converter.
  • the resonant circuit may have any suitable number and arrangement of switches for exciting the resonant circuit, however, a half-bridge is preferred, in particular at not too high power required, for. As compared to a more expensive VoIl- bridge.
  • any suitable electronic switch for excitation of the resonant circuit can be used, for. B. a transistor in the form of an IGBT or a MOSFET.
  • a MOSFET since an IGBT has a comparatively high loss due to its current path, it is preferred if at least one of the electronic switches is a MOSFET, in particular all electronic switches are MOSFETs.
  • the predetermined threshold can be chosen arbitrarily suitable, z. B. such that it compensates for an inertia of the shutdown or provides a margin of safety.
  • the threshold may preferably be set to trip for approximately a period of time prior to reaching the zero crossing, which corresponds to a time delay of the shutdown.
  • the threshold value is essentially zero, that is to say a zero-crossing detection is carried out, preferably with sign recognition.
  • the resonant circuit equipped with at least two electronic switches, is set up to run the procedure as described above.
  • the resonant circuit preferably has at least: a current threshold detection circuit for detecting a reaching of a current threshold of a current through at least one of the switches; a disconnect detection circuit for detecting a turn-off of this at least one switch; an AND circuit connected downstream of the current threshold detection circuit and clock edge detection circuit, which outputs a signal for switching off the converter when detection by the current threshold detection circuit occurs in common and detection by the clock edge detection circuit.
  • the current threshold detection circuit comprises a zero-crossing detection circuit for detecting a zero crossing through at least one of the switches.
  • the circuit breaker detection circuit preferably comprises a clock edge detection circuit for detecting a clock edge of a clock signal which switches off the switch.
  • the clock signal is a gate voltage signal (eg, in a MOSFET or an IGBT).
  • the resonant circuit is designed as a resonant converter and comprises at least one side of a separable transformer for power transmission.
  • the household appliance is designed with such a resonant circuit.
  • FIG 1 shows a circuit diagram of a resonant circuit for power transmission (FIG IA) and its frequency response (FIG IB);
  • FIG IA shows a more detailed circuit diagram of the resonant circuit of FIG IA
  • FIG. 3 shows a frequency response of the resonant circuit from FIG. 2 in over-resonant operation (FIG. 3A) and in sub-resonant operation (FIG. 3B) for the case where a
  • Switching frequency is 100 KHz
  • FIG. 4 shows in each case three partial images a profile of a drain current, a drain-source voltage and a gate voltage in the over-resonant mode (FIG
  • FIG. 5 shows a diagram of a simulation of a drain current and a drain-source voltage in over-resonant operation (FIG. 5A) and in sub-resonant operation (FIG. 5B);
  • FIG. 6A shows a block diagram of a resonance detection circuit
  • FIG. 6B shows a possible implementation of the resonance detection circuit of FIG. 6A.
  • FIG. 1A shows a circuit diagram of a resonant circuit 1 of a resonant converter for power transmission between a power part 2 and a galvanically separated consumer part 3 by means of a transformer 4.
  • the transformer 4 is here as an equivalent circuit with a primary-side main inductance LhI, a secondary-side Haupinduktivi- act Lh2 and a leakage inductance Ls shown.
  • the primary-side main inductance LhI is connected in parallel with a resonant capacitor Cres, both of which are in series with a resonance coil (resonance choke) Lres are connected.
  • the inductances of the transformer 4, the resonance capacitor Cres and the resonance coil Lres substantially determine the resonance frequency or the resonance point of the resonant circuit 1.
  • the primary-side main inductance LhI is operated with an alternating voltage whose frequency sets the output voltage. You can z. B. are at the resonant frequency, be in the vicinity of the resonant frequency or be significantly larger, for example, depending on the desired output voltage.
  • the magnetic field thus generated by the primary-side main inductance LhI is inductively inducted by the secondary-side main inductance Lh2 in order to feed a load connected thereto, which is simplified here as load resistor RL.
  • the transformer 4 is here associated with its primary-side main inductance LhI to the power section 2 and drawn with its secondary-side main inductance Lh2 to consumer part 3 belonging.
  • Lh2 For spatial separation of power unit 2 and consumer part 3 of the transformer 4 between its main inductances LhI, Lh2 is separable.
  • the transformer halves are disconnected, the values of the main inductances LhI and Lh2 greatly decrease while the value of the leakage inductance Ls increases. This changes the resonant circuit parameters, and the resonant frequency of the resonant circuit increases. If the drive frequency remains constant, this can lead to under-resonant operation, as a result of which the current and voltage load of the switches changes considerably, as described in more detail below with reference to FIGS. 3A and 3B.
  • FIG. 1B shows the calculated frequency response of the resonant circuit from FIG. 1A plotted as the amplitude of the individual frequencies of the calculated frequency response in arbitrary units over the frequency f in KHz.
  • the normal operation of the resonant circuit is to the right of the resonant frequency, ie, superresonant.
  • Power unit 2 and consumer part 3 may for example be part of a household appliance system. Thus, one or more power parts 2 may be integrated into a work surface, for. B. for a kitchen, or in a hob. A consumer part 3 can then be placed on the work surface opposite one of the power parts 2, or slightly laterally offset, and operated.
  • a consumer part 3 can be designed, for example, as cooking utensils (with the load resistance RL in the form of resistance heating, eg as a pot, pan, etc.) or as a coffee machine (with the load resistance RL in the form of electronics and multiple resistance heaters).
  • FIG. 2 shows the resonant circuit 1 from FIG. 1A with a more detailed illustration of the power section 2.
  • the power section operates as a DC-AC converter 2, which supplies a DC voltage Ug applied to its input terminals 5 from here by way of example 380 V into an AC voltage for operating the primary-side main inductance LhI converts (resonant converter).
  • the resonant circuit 1 comprises for this purpose a half-bridge with two electronic switches in the form of normally-conducting MOSFETs 6.
  • the MOSFETs 6 are connected in series between the input terminals 5.
  • the MOSFETs 6 passively turn on at a current less than zero and actively turn off a current greater than zero.
  • Each of the MOSFETs 6 is connected in parallel to an associated diode 7, which are arranged blocking with respect to the input DC voltage of 380 V.
  • the diodes 7 correspond to the respective parasitic body diodes. For IGBTs these must be connected in parallel.
  • the MOSFETs 6 are switched on and off alternately via their respective gate voltage UG. As a result, a sinusoidal AC voltage with a frequency corresponding to the clock frequency of the MOSFETs 6 is generated.
  • FIG. 3A shows, in a representation analogous to FIG. 1B, a frequency response of the resonant circuit 1 from FIG. 2 with the consumer part attached as the frequency response of the resonant circuit 1 plotted as the amplitude of the individual frequencies of the calculated frequency response in arbitrary units over the frequency f in KHz.
  • the resonant circuit 1 is operated überresonant, d. h., At frequencies above the resonant frequency of the resonant circuit whose position is at about 90 kHz.
  • FIG. 3B shows, in a representation analogous to FIG. 3A, the frequency response in the case of separate transformer halves, ie, a heavily offset or removed consumer part.
  • the values of the main inductances LhI and Lh2 greatly decrease while the value of the leakage inductance Ls increases. Consequently, the resonant circuit parameters change, and the resonant frequency of the resonant circuit increases, the position of which is now indicated by dashed lines at approx. 120 KHz.
  • dashed lines At constant drive frequency of the power semiconductors from here 100 KHz it comes to the subresonant operation, causing the Current and voltage load on the MOSFETs 6 seriously changes.
  • FIG. 4A outlines for the over-resonant operation for one clock cycle in each case: (a) a profile of the transistor current (drain current) ID through one of the MOSFETs from FIG. 2 (upper partial image); (b) a profile of the drain-source voltage UDS at this MOSFET (middle field); and (c) a trace of the gate voltage UGS at this MOSFET (lower field) over an on / off cycle of the MOSFET.
  • 5A shows in a diagram a corresponding measured transistor current (drain current) ID and an associated, measured drain-source voltage UDS of a MOSFET over the relative time t for an on / off cycle in%.
  • the MOSFET When the MOSFET is switched on (gate voltage UGS switched on, see lower part of FIG. 4A), it conducts, so that the drain-source voltage UDS is substantially zero. In this conductive state, the drain current ID in the over-resonant state goes high from a negative initial value into the positive region.
  • FIG. 4B shows, in an analogous view to FIG. 4A, a profile in the sub-resonant mode
  • FIG. 5B shows, in an analogous view to FIG. 5A, an associated measured drain current ID and an associated measured drain-source voltage UDS.
  • the drain current ID now typically comes from a positive initial value first to a maximum high to then change to the range of negative polarity, while the MOSFET is still active.
  • the parasitic body diode of the transistor is flooded (inverse operation). If this MOSFET is subsequently switched off or the following MOSFET is switched on, the flooded (slow) body diode causes high currents and thus high losses, which can destroy the MOSFET.
  • the resonant circuit is turned off when a negative transistor current and turning off the transistor or turning on the opposite transistor come together.
  • this can be done by detecting a falling gate voltage edge in the event of a negative transistor current.
  • the transistor current can be evaluated directly on the transistor or the current in the resonant choke together with the associated gate signal of a power transistor. By evaluating the current in the resonant choke in conjunction with the gate voltage edge is immediate, d. h., With almost no delay, a separate transformer half recognizable.
  • FIG. 6A shows a block diagram of a resonance detection circuit 10 or blocking circuit for detecting undersampling operation of the resonant circuit from FIG. 2 or detection and subsequent blocking (switching off) of the resonant circuit.
  • the resonance detection circuit 10 comprises firstly a current threshold value detection circuit 11 for detecting a reaching of a current threshold value of a current through at least one of the switches (in particular MOSFETs) and a switch-off detection circuit 12 for detecting a deactivation of this at least one switch.
  • a current threshold value detection circuit 11 for detecting a reaching of a current threshold value of a current through at least one of the switches (in particular MOSFETs) and a switch-off detection circuit 12 for detecting a deactivation of this at least one switch.
  • These two detection circuits 11,12 an AND circuit 13 is connected downstream, which outputs a signal for switching off the resonant circuit at a common occurrence of detection by the Stromschwellwerterkennungsscrien and detection by the clock edge detection circuit.
  • the current threshold detection circuit 11 is configured as a threshold detection circuit for detecting a threshold value near the zero crossing into the region of negative polarity by the considered MOSFET. It is thus recognized whether the condition ID ⁇ ID_min exists, where ID min represents a drain current threshold.
  • the disconnect detection circuit 12 is configured as a clock edge detection circuit for detecting a clock edge of a clock signal which switches off the MOSFET.
  • the clock signal here corresponds to the gate voltage UGS, so that it is detected whether the condition d (UGS) / dt ⁇ 0 is present.
  • FIG. 6B shows a self-explanatory possible realization of the block diagram of FIG. 6A.
  • an IGBT can be used which is comparatively robust, but due to the tail current at shutdown causes a relatively high power loss (or any other suitable electronic switch, in particular transistor).
  • a full-bridge converter can be used, for. B. with four electronic switches.
  • the resonant circuit is generally suitable for the wireless transmission of energy through a transformer and is not limited to the household sector. Furthermore, not only need to be lifted to a zero crossing for detecting a negative-polarity transistor current; Rather, for example, reaching a predetermined, previously occurring threshold value can fulfill one of the conditions for switching off the resonant circuit.
  • the threshold may be set to trigger a period of time before the zero crossing that corresponds to a time delay of the shutdown.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un procédé de fonctionnement d'un circuit oscillant comportant au moins deux commutateurs électroniques, ledit procédé étant caractéristé en ce que le circuit oscillant est coupé lorsque, essentiellement pendant la coupure et/ou après la coupure de l'un des commutateurs, un courant traversant ce commutateur atteint une valeur de seuil prédéterminée ou tombe au-dessous.
EP09757587A 2008-06-06 2009-06-04 Procédé de fonctionnement d'un circuit oscillant comportant au moins deux commutateurs électroniques et circuit oscillant correspondant Withdrawn EP2289165A2 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102008027126A DE102008027126A1 (de) 2008-06-06 2008-06-06 Verfahren zum Betreiben eines Schwingkreises mit mindestens zwei elektronischen Schaltern und Schwingkreis
PCT/EP2009/056867 WO2009147206A2 (fr) 2008-06-06 2009-06-04 Procédé de fonctionnement d'un circuit oscillant comportant au moins deux commutateurs électroniques et circuit oscillant correspondant

Publications (1)

Publication Number Publication Date
EP2289165A2 true EP2289165A2 (fr) 2011-03-02

Family

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Family Applications (1)

Application Number Title Priority Date Filing Date
EP09757587A Withdrawn EP2289165A2 (fr) 2008-06-06 2009-06-04 Procédé de fonctionnement d'un circuit oscillant comportant au moins deux commutateurs électroniques et circuit oscillant correspondant

Country Status (3)

Country Link
EP (1) EP2289165A2 (fr)
DE (1) DE102008027126A1 (fr)
WO (1) WO2009147206A2 (fr)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2713470A1 (fr) * 2012-10-01 2014-04-02 Siemens Aktiengesellschaft Circuit doté d'un convertisseur de courant résonant et procédé de fonctionnement d'un convertisseur de courant résonant
DE102013207883A1 (de) 2013-04-30 2014-10-30 Siemens Aktiengesellschaft Schaltungsanordnung mit einem Resonanzwandler und Verfahren zum Betreiben eines Resonanzwandlers
DE102013219530A1 (de) * 2013-09-27 2015-04-16 Siemens Aktiengesellschaft Ermittlung eines Stromnulldurchgangs eines Wechselstroms
DE102013224586A1 (de) 2013-11-29 2015-06-03 Siemens Aktiengesellschaft Frequenzerzeugung für einen Resonanzwandler

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4337504B4 (de) * 1993-11-03 2005-04-28 Sms Elotherm Gmbh Verfahren und Vorrichtung zur Ansteuerung von abschaltbaren Leistungshalbleitern eines Resonanz-Umrichters mit angepaßter Schaltgeschwindigkeit
DE19961227A1 (de) * 1999-12-18 2001-06-28 Philips Corp Intellectual Pty Konverter mit Resonanzkreiselementen

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO2009147206A2 *

Also Published As

Publication number Publication date
DE102008027126A1 (de) 2009-12-10
WO2009147206A9 (fr) 2010-02-18
WO2009147206A2 (fr) 2009-12-10

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