EP2692018B1 - Antennenstrukturen mit einer kombination aus metamaterialien - Google Patents

Antennenstrukturen mit einer kombination aus metamaterialien Download PDF

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Publication number
EP2692018B1
EP2692018B1 EP12709129.6A EP12709129A EP2692018B1 EP 2692018 B1 EP2692018 B1 EP 2692018B1 EP 12709129 A EP12709129 A EP 12709129A EP 2692018 B1 EP2692018 B1 EP 2692018B1
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EP
European Patent Office
Prior art keywords
radome
antenna
metamaterial
split
support
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English (en)
French (fr)
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EP2692018A1 (de
Inventor
Mohamed LATRACH
Wafa ABDOUNI-ABDALLAH
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ECOLE SUPERIEURE ELECTRONIQUE DE L'OUEST
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ECOLE SUPERIEURE ELECTRONIQUE DE L'OUEST
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0086—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices having materials with a synthesized negative refractive index, e.g. metamaterials or left-handed materials
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0013—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective
    • H01Q15/0026—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective said selective devices having a stacked geometry or having multiple layers

Definitions

  • the field of the invention is that of electromagnetic waves, preferably in the range of Ultra High Frequencies (or “UHF” for “Ultra High Frequency” in English) (300 MHz to 3 GHz) and Microwave frequencies (3 GHz to 300 GHz ).
  • the invention relates to a metamaterial structure comprising elementary blocks of metamaterial, and an antenna system (also hereinafter referred to as an antenna structure) using such a metamaterial structure as an antenna radome.
  • the invention applies in particular, but not exclusively, to all antenna systems for which it is desired to increase the directivity and the antenna gain and to minimize rear and side radiation.
  • the invention applies to antennas of RFID base stations in the UHF band
  • metamaterials Recent years have seen a strong interest in metamaterials.
  • the concept of metamaterial is well known and is discussed for example in the document JB Pendry, AJ Holden, Robbins DJ, and WJ Stewart, "Magnetism from conductors and enhanced nonlinear phenomena," IEEE Trans. Microw. Theory Tech., Vol. 47, no. 11, pp. 2075-2084, 1999 .
  • metamaterials are by definition metallo-dielectric composite media. These are periodic structures, the constituent elements of which are metallic inclusions of very small dimensions in front of the wavelength ( ⁇ / 10).
  • Electrical metamaterials are metamaterials that have electrical behavior and are likely to have a negative permittivity ( ⁇ ) in a given frequency spectrum.
  • the most known electrical metamaterials are those formed by a network of metal rods.
  • Magnetic metamaterials are metamaterials that have a magnetic behavior and are likely to have a negative ( ⁇ ) permeability in a given frequency spectrum.
  • the most known magnetic metamaterials are those formed by a network of square or circular split ring resonators (or "SRR" for "Split Ring Resonator”).
  • the left-hand materials are metamaterials that are likely to have a permittivity ( ⁇ ) and permeability ( ⁇ ) simultaneously negative in a given frequency spectrum.
  • the best-known left-hand materials are those formed by the combination of a network of metal rods and a network of split-ring resonators. With such materials on the left hand, it is thus possible to obtain quite unusual propagation phenomena, such as opposite phase and group velocities, inverted doppler effects, a negative refractive index, etc.
  • the figure 1 illustrates an example of an antenna system comprising a left-hand material radome based on split-ring resonators and conducting ribbons. For the sake of clarity, only one half of the antenna system is represented on the figure 1 .
  • the radome 15 extends above the antenna 110.
  • the radome 15 is separated from the antenna 110 by a volume 16 consisting, for example, of air or dielectric material and / or magnetic.
  • the radome 15 includes a left hand material structure.
  • the left-hand material structure comprises a plurality of elementary blocks 17 arranged in rows and columns in a matrix.
  • Each elementary block 17 comprises a split ring resonator and a conductive strip.
  • the figure 2 illustrates a possible example of an elementary block of left-hand material based on a split-ring resonator and conducting ribbon.
  • the elementary block of left-hand material 20 comprises a first support 21 of dielectric material comprising an upper face 22 on which is disposed a split-ring resonator 24, and a lower face 23 on which a first linear metal ribbon 25 is arranged.
  • the elementary block 20 comprises a second support 26 of dielectric material comprising a lower face 27 on which is disposed a second linear metal strip 28.
  • the two supports 21 and 26 are separated by an air layer 29.
  • the split ring resonator 24 comprises an inner split square 241 and an outer split square 242.
  • the width of the slot of each square split is about 0.3mm.
  • the width of the different metal tracks is about 0.3 mm.
  • the spacing between the inner 241 and outer 242 split squares is about 0.3mm.
  • the volume of an elementary block 20 is approximately 3.3 x 3.3 x 4.5 mm 3 and the periodicity of the metamaterial structure is approximately 3.63 mm in the plane and 4.5 mm deep. .
  • the radome 15 acts as an electromagnetic wave diffraction device and makes it possible to increase the directivity and the gain of the antenna 101, while reducing the side lobe and rear radiation levels. This is particularly described in detail in the document Shah Nawaz Burokur, Mohamed Latrach, and Serge Toutain "Theoretical Investigation of a Circular Patch Antenna in the Presence of a Left-Handed Medium", IEEE Trans. Antennas and Wireless Propagation Letters, Vol 4, pp. 183-186, 2005 .
  • this left-hand material structure based on split ring resonators and conductive ribbons is that it only works with linear polarization antennas. In other words, this structure can not be used in circular polarization.
  • the left-hand material structure (forming the antenna radome) is simple to implement, and that it has the lowest possible cost.
  • the figure 3 illustrates an example of an elementary block of left-hand material based on S-shaped resonators (arranged on one side of a support made of dielectric material) and inverted S-shaped resonators (arranged on the other side of the support ).
  • the particularity of this type of resonator 30 is that it has a double resonance, magnetic and electrical, without requiring the implementation of small slots and an additional network of metal rods.
  • a left-hand material structure based on S-shaped resonators has a good simplicity of implementation.
  • it has the disadvantage of not working in the case where the polarization of the antenna is circular.
  • the invention in at least one embodiment, is intended in particular to overcome these various disadvantages of the state of the art.
  • an objective is to provide a metamaterial structure having a simplicity of realization in industrial form, while being compatible with many applications.
  • At least one particular embodiment of the invention aims to provide such a metamaterial structure that makes it possible to obtain an antenna radome.
  • Another objective of at least one embodiment of the invention is to provide such an antenna radome which makes it possible to improve the radiation characteristics of an antenna, while reducing (or at least without increasing) its dimensions.
  • Another objective of at least one embodiment of the invention is to provide such an antenna radome that is compatible with operation in linear and / or circular polarization.
  • Another objective of at least one embodiment of the invention is to provide such an antenna radome which is adapted to antennas of RFID base stations in the UHF band.
  • said first and second C-shaped conductive elements are identical.
  • the first connector has a rectilinear shape
  • each C-shaped conductive element is an arc whose center corresponds to the middle of the first connector.
  • the media of the first and second connectors are superimposed.
  • said first and second conductive units are superimposed with a 90 ° rotation of the first connector relative to the second connector.
  • said first and second conductive units are identical.
  • said first conductive unit comprises at least one active component.
  • said second conductive unit comprises at least one active component.
  • the metamaterial structure is such that it is adapted to operate in a frequency band from 860 MHz to 960 MHz.
  • each of the inner and outer split squares is formed by a metal track of width approximately 1 mm and comprises a slot width of about 2 mm, the slits of the inner and outer split squares being aligned with each other.
  • Each side of the inner split square measures about 17mm.
  • Each side of the outer split square measures approximately 20mm.
  • the spacing between the inner and outer split squares is about 0.5mm.
  • said at least one elementary block comprises a rectilinear metal strip about 22 mm long and about 2 mm wide, disposed on the underside of the support, the slots of the inner and outer split squares being superimposed above said metal ribbon.
  • the metamaterial structures according to the invention have negative permittivity and / or negative permeability in a given and relatively wide frequency spectrum. They can be used as an antenna radome to increase the directivity and gain of an antenna.
  • the metamaterial structures according to the invention can be used in the range of UHF and microwave frequencies and for any type of antenna, and its manufacture remains simple.
  • the figure 4 illustrates an example of an antenna system comprising a metamaterial radome according to a first embodiment of the invention.
  • the antenna system 40 is configured and sized to operate in the UHF-RFID band.
  • the UHF-RFID band extends from 860 MHz to 960 MHz.
  • the figure 5 shows an example of antenna 401 according to the invention. This figure 5 illustrates an exemplary embodiment of the carrier structure 41 and the radiating element 42.
  • the carrier structure 41 comprises a ground plane 51 printed on the underside of a first layer 52 of dielectric material.
  • the carrier structure 41 comprises a second layer 54 of dielectric material which is separated from the first layer 52 of dielectric material by an air layer 53.
  • the radiating element 42 is printed on the upper face of the second layer 54 of dielectric material.
  • the radiating element 42 and the ground plane 51 are sized to operate in the UHF-RFID band.
  • the radiating element 42 and the ground plane 51 are of square shape, the length (Lp) of the radiating element 42 being about 130 mm and the length (Lm) of the ground plane 51 being about 250mm.
  • the radiating element 42 is fed via a conventional connector 55 of the SMA type.
  • a conventional SMA connector includes a central blade with a length of about 15mm.
  • the excitation of the radiating element 42 may be carried out according to various techniques among which may be mentioned the coaxial probe, the microband line, the coupling by proximity or the coupling by a slot.
  • the first and second layers of dielectric material 52 and 54 each comprise a FR4-type epoxy layer.
  • each FR4 epoxy layer has a height of 1.6 mm. Which is advantageous in terms of cost.
  • the FR4 epoxy layers can be replaced by layers of air (this in particular makes it possible to reduce the production costs and to lighten the structure) or other types of substrates.
  • the height of the antenna must be less than 15mm (height of the SMA connector), the height of the air layer 53 is 11.2mm.
  • the total height of the antenna is 14.4mm.
  • the square radiating element 42 is capable of operating in both linear and circular polarization (depending on the location of the excitation device 55).
  • the HFSS (registered trademark) software was used to simulate the performance in terms of reflection coefficient (denoted S11) and gain of the antenna 401 (without radome) of the figure 5 in linear polarization ( Figures 7a and 7b ) and in circular polarization ( Figures 8a and 8b ).
  • the figure 7a presents the curve 71 of the reflection coefficient of the antenna of the figure 5 in linear polarization for the frequency band from 800 MHz to 1 GHz.
  • the figure 7b presents the curve 72 of gain of the antenna of the figure 5 in linear polarization for the frequency band from 800 MHz to 1 GHz.
  • the antenna 401 of the figure 5 in linear polarization has a resonance frequency at about 883 MHz and a maximum gain of about 10 dBi.
  • the figure 8a presents the curve 81 of the reflection coefficient of the antenna of the figure 5 in circular polarization for the frequency band from 800 MHz to 1 GHz.
  • the figure 8b presents the curve 82 of gain of the antenna 401 of the figure 5 in circular polarization for the frequency band from 800 MHz to 1 GHz.
  • the antenna of the figure 5 in circular polarization has a resonance frequency at about 881 MHz and a maximum gain of about 9.5 dBi.
  • the radome 43 comprises a metamaterial structure according to the invention.
  • This metamaterial structure comprises a plurality of elementary blocks according to the invention.
  • the elementary block of metamaterial 60 comprises a support 61 of dielectric material of square shape and side about 45mm.
  • the radome 43 is in the form of a 5x5 matrix, each cell of which comprises the elementary block of metamaterial 60.
  • the radome 43 may be in the form of a sphere cap, a cone or a cylinder.
  • the elementary blocks of metamaterial according to the invention can be inserted in or can constitute the substrate of the radiating element.
  • the support 61 has a height (hsub) of about 1.6mm.
  • the elementary metamaterial block 60 comprises an electrically conductive unit 62 printed on the upper face of the support 61.
  • the printing of the conductive unit 62 on the support 61 is easily obtained by the implementation of photolithography techniques. In this way, manufacturing costs are reduced. Of course, other printed circuit printing techniques can be implemented.
  • the first and second conductive members 621 and 622 are arranged with respect to each other such that the first and third ends E1 and E3 face each other and are separated by a gap (g), and the second and fourth ends E2 and E4 face each other and are separated by a space (g).
  • the connector 623 is configured to connect the first end E1 to the fourth end E4.
  • the connector 623 is a straight metal strip.
  • the connector 623 can take a curved or meandering shape.
  • the connector 623 may be configured to connect the second end E2 to the third end E3.
  • the width of each of the first and second conductive elements 621 and 622 and the connector 623 is approximately 1 mm.
  • first and second conductive elements 621 and 622 are identical. Each conductive element 621 and 622 is an arc whose center corresponds to the middle of the connector 623.
  • first and second conductive elements 621 and 622 may be different, that is to say they may have different dimensions and C-curves. For example, they may come from two circles of different centers.
  • the operating frequency may vary, which is a means of adjustment according to the desired working frequency.
  • first and second conductive members 621 and 622 are spaced approximately 20mm apart.
  • the spaces between the first and third ends E1 and E3, and the second and fourth ends E2 and E4 may be different.
  • first and third ends E1 and E3 may be spaced about 40mm and the second and fourth ends E2 and E4 of about 10mm.
  • the operating frequency may vary, which is a means of adjustment according to the desired working frequency. It is conceivable to place in these spaces (or gaps) varicaps diodes connecting the ends E2 to E4 and / or E1 to E3, and / or at the level of the connector ribbon 623. This makes it possible to make the antenna system agile in frequency.
  • HFSS software has been used to simulate the performances in terms of permittivity ( ⁇ ) and permeability ( ⁇ ) of a network made up of elementary blocks of metamaterial 60 according to the first embodiment of the invention ( described in relation to the figure 6 ).
  • the figure 9 presents the curves of the real parts of permittivity 91 and permeability 92 of a network constituted by elementary blocks of metamaterial of the figure 6 for the frequency band from 500 MHz to 1 GHz.
  • the network of elementary blocks of metamaterial of the figure 6 has a positive permeability in the 500 MHz band at 1 GHz and a negative permittivity for frequencies in the 690 MHz to 1 GHz band.
  • the permittivity of the metamaterial according to the first embodiment of the invention is negative. in a frequency band of about 0.5 GHz instead of 0.1 GHz.
  • the use of the metamaterial according to the first embodiment of the invention therefore implies a better system stability and consequently a flexibility in precision of realization.
  • the HFSS (registered trademark) software was used to simulate the performance in terms of reflection coefficient (denoted S11) and gain of the antenna system 40 of the figure 4 in linear polarization ( Figures 10a and 10b ) and in circular polarization ( Figures 11a and 11b ).
  • the radome 43 is placed at a distance of about 120 mm (that is to say approximately ⁇ 0/3 ) from the radiating element 42.
  • the figure 10a presents the curve 101 of the reflection coefficient of the antenna system 40 of the figure 4 in linear polarization for the frequency band from 800 MHz to 1 GHz.
  • the curve 71 of the reflection coefficient of the antenna 401 (without radome) of the figure 5 in linear polarization is improved.
  • the figure 10b presents the gain curve 102 of the antenna system 40 of the figure 4 in linear polarization for the frequency band from 800 MHz to 1 GHz.
  • the gain curve 72 of the antenna 401 (without radome) of the figure 5 in linear polarization we have shown on the figure 10b the gain curve 72 of the antenna 401 (without radome) of the figure 5 in linear polarization.
  • the antenna system 40 of the figure 4 in linear polarization has a resonance frequency at about 889 MHz and a maximum gain of about 12.5 dBi.
  • the radome 43 thus makes it possible to increase the overall gain of the antenna in linear polarization by approximately 2 dBi.
  • the figure 11a presents the curve 111 of the reflection coefficient of the antenna system 40 of the figure 4 in circular polarization for the frequency band from 800 MHz to 1 GHz.
  • the curve 81 of the reflection coefficient of the antenna 401 (without radome) of the figure 5 in circular polarization is improved.
  • the figure 11b presents the gain curve 112 of the antenna system 40 of the figure 4 in circular polarization for the frequency band from 800 MHz to 1 GHz.
  • the curve 82 of gain of the antenna 401 (without radome) of the figure 5 in circular polarization we have shown on the figure 11b the curve 82 of gain of the antenna 401 (without radome) of the figure 5 in circular polarization.
  • the antenna system 40 of the figure 4 in circular polarization has a resonance frequency at about 889 MHz and a maximum gain of about 10.3 dBi.
  • the radome 43 thus makes it possible to increase the overall gain of the antenna in circular polarization by approximately 1 dBi.
  • the radome 43 can be oriented with respect to the antenna 401 according to an orientation angle determined according to the desired increase in gain in the plane ⁇ and / or ⁇ .
  • the radome 43 is oriented at an angle of orientation of + 45 ° with respect to the antenna 401.
  • the gain increase is approximately 2 dBi according to ⁇ .
  • the radome 43 is oriented at an angle of orientation of -45 ° relative to the antenna 401.
  • the gain increase is about 2dBi according to ⁇ .
  • the conductive unit 62 may comprise one or more active components (semiconductor components) such as, for example, varicaps diodes.
  • the antenna system 40 may therefore comprise a device for dynamically controlling such active components.
  • a voltage control device for varicap diodes it will be possible to envisage a voltage control device for varicap diodes.
  • the figure 12 illustrates an example of an antenna system comprising a metamaterial radome according to a second embodiment of the invention.
  • the carrier structure 122 and the radiating element 123 are respectively identical to the supporting structure 41 and the radiating element 42 described above in relation to the figures 4 and 5 . These elements are therefore not described again below.
  • the radome 121 comprises a metamaterial structure.
  • This metamaterial structure comprises a plurality of elementary blocks according to the invention.
  • the elementary block of metamaterial 130 comprises a support 131 made of dielectric material of square shape and side of about 45mm.
  • the radome 121 is in the form of a 5x5 matrix, each cell of which comprises the elementary block of metamaterial 130.
  • this example is not limiting.
  • the radome 121 may be in the form of a sphere cap, a cone or a cylinder.
  • the support 131 has a height (h sub ) of about 1.6mm. Note that this height is one of the parameters on which it is possible to intervene to change the frequency of operation of the system if necessary.
  • the elementary block of metamaterial 130 comprises a first electrically conductive unit 132 printed on the upper face of the support 131, and a second electrically conductive unit 133 printed on the underside of the support 131.
  • the printing of the conductive units 132 and 133 on the support 131 is obtained by the implementation of photolithography techniques. In this way, manufacturing costs are reduced. Of course, other printed circuit printing techniques can be implemented.
  • the first and second conductive members 1321 and 1322 are arranged relative to each other so that the first and third ends E11 and E13 face each other and are separated by a gap, and the second and fourth ends E12 and E14 face each other and are separated by a space (g).
  • the connector 1323 is configured to connect the first end E11 to the fourth end E14.
  • the connector 1323 has a rectilinear shape.
  • the connector can take a shape curved or meandering.
  • the connector 1323 may be configured to connect the second end E12 to the third end E13.
  • the third and fourth conductive members 1331 and 1332 are arranged relative to each other so that the fifth and seventh ends E15 and E17 face each other and are separated by a gap (g), and the sixth and fourth ends eighth ends E16 and E18 face each other and are separated by a space (g).
  • the connector 1333 is configured to connect the fifth end E15 to the eighth end E18.
  • the connector 1333 has a rectilinear shape.
  • the connectors 1323 and 1333 are arranged relative to each other so that they are superimposed in their middle A. In other words, the media of the connectors 1323 and 1333 are superimposed.
  • the connector 1323 forms an angle ⁇ with the connector 1333.
  • the first and second conductive units 132 and 133 are superimposed with a 90 ° rotation of the first connector relative to the second connector.
  • the angle ⁇ can take a value between 10 ° and 170 °.
  • the width of each of the conductive elements and connectors is about 1 mm. Note that this width is one of the parameters on which it is possible to intervene to change the operating frequency of the system if necessary.
  • first and second conductive units 132 and 133 are identical. As can be seen, the conductive elements 1321 and 1322 of the first conductive unit 132 and the conductive elements 1331 and 1332 of the second conductive unit 133 overlap at certain locations B, C, D and E. These overlaps have the effect of decreasing the operating frequency of the system.
  • the first and second conductive units 132 and 133 may have different dimensions such that, for example, the second conductive unit 133 extends inside the first conductive unit 132.
  • Another alternative embodiment may consist of placing or printing on the same face of the support (substrate) dielectric or magnetic two concentric conductive units or of different dimensions.
  • the ends of the first and second conductive members 1321 and 1322 are spaced a distance (g) of about 20mm, and the ends of the third and fourth conductive members 1331 and 1332 are spaced a distance (g) of about 20mm.
  • the operating frequency may vary, which is a means of adjustment according to the desired working frequency.
  • the radome 121 is placed at a distance of approximately 80 mm (that is to say approximately ⁇ 0/4 ) from the radiating element 123.
  • the figure 14a presents the curve 141 of the reflection coefficient of the antenna system 120 of the figure 12 in circular polarization for the frequency band from 840 MHz to 1 GHz.
  • the curve 81 of the reflection coefficient of the antenna 401 (without radome) of the figure 5 in circular polarization is improved.
  • the figure 14b presents the gain curve 142 of the antenna system 120 of the figure 12 in circular polarization for the frequency band from 840 MHz to 1 GHz.
  • the curve 82 of gain of the antenna 401 (without radome) of the figure 5 in circular polarization we have shown on the figure 14b the curve 82 of gain of the antenna 401 (without radome) of the figure 5 in circular polarization.
  • the antenna system 120 of the figure 12 in circular polarization has a resonance frequency at about 907 MHz and a maximum gain of about 10.7 dBi.
  • the radome 121 thus makes it possible to increase the overall gain of the antenna in circular polarization by approximately 1 dBi.
  • the radome 121 (comprising a single conductive unit on the upper face of the support) makes it possible to make the circular polarization of the perfect antenna.
  • Radomes are already known in left hand material capable of operating in the X band or the UHF high band (that is to say for frequencies greater than 2GHz). However, to date, there are no solutions for the low UHF band (that is for frequencies below 2GHz).
  • the figure 15 illustrates an example of an antenna system comprising a left-hand material radome optimized for the UHF-RFID band. For the sake of clarity, only one half of the antenna system is represented on the figure 15 .
  • the carrier structure 162 and the radiating element 163 are respectively identical to the carrier structure 41 and the radiating element 42 described above in relation to the examples of the figures 4 and 5 . These elements are therefore not described again below.
  • the radome 161 includes a left-hand material structure optimized for the UHF-RFID band.
  • This left-hand material structure comprises a plurality of elementary blocks 170 arranged in rows and columns in a matrix.
  • the figure 16 illustrates an elementary block of left-hand material optimized for the UHF-RFID band.
  • the elementary block of left-hand material 170 comprises a support 171 made of dielectric material comprising an upper face 172 on which is disposed a split-ring resonator 174, and a lower face 173 on which a linear metal strip 175 is arranged.
  • the support 171 is of square shape. Of course, it may be of another form (rectangular, circular, ..., following the shape of the split ring resonator). Each side of the square measures approximately 22mm.
  • the support 171 has a height (hsub) of about 1.6 mm but can be of different size.
  • the split ring resonator 174 comprises an inner split square 1741 and an outer split square 1742.
  • the inner split square 1741 is formed by a metal track with a width of about 1 mm. Each side of the inner split square 1741 measures about 17mm.
  • the inner split square 1741 includes a slot whose width is about 2mm.
  • the spacing between the inner 1741 and outer 1742 split squares is about 0.5mm.
  • the outer split square 1742 is formed by a metal track of approximately 1mm width. Each side of the outer split square 1742 measures about 20mm.
  • the outer split square 1742 comprises a slot whose width is substantially equal to that of the slot of the inner split square 1741, that is to say about 2mm.
  • the slits of the inner 1741 and outer 1742 split squares are aligned with each other.
  • the straight metal strip 175 has a length substantially equal to that of the support 171, that is to say about 22 mm, and a width substantially equal to that of the slots, that is to say about 2 mm.
  • the HFSS (registered trademark) software was used to extract the permittivity ( ⁇ ) and permeability ( ⁇ ) parameters of a network made up of elementary blocks of left-hand material 170.
  • the figure 17 presents the curves of the real parts of permittivity 181, of permeability 182 and of the refractive index of a network made up of elementary blocks 170 of the figure 16 for the frequency band from 500 MHz to 1 GHz.
  • the network consists of elementary blocks of material left hand of the figure 16 simultaneously exhibits negative permeability and permittivity for frequencies in the 790 MHz to 920 MHz band.
  • the radome 161 is placed at a distance of approximately 80 mm (that is to say approximately ⁇ 0/4 ) from the radiating element 163.
  • the figure 18a presents the curve 191 of the reflection coefficient of the antenna system 160 of the figure 15 in linear polarization for the frequency band from 840 MHz to 1 GHz.
  • the curve 81 of the reflection coefficient of the antenna 401 (without radome) of the figure 5 in linear polarization we have shown on the figure 18a the curve 81 of the reflection coefficient of the antenna 401 (without radome) of the figure 5 in linear polarization.
  • the figure 18b presents the gain curve 192 of the antenna system 160 of the figure 15 in linear polarization for the frequency band from 840 MHz to 1 GHz.
  • the curve 82 of gain of the antenna 401 (without radome) of the figure 5 in linear polarization we have shown on the figure 18b the curve 82 of gain of the antenna 401 (without radome) of the figure 5 in linear polarization.
  • the antenna system 160 of the figure 15 in linear polarization has a resonance frequency at about 918 MHz and a maximum gain about 13.2 dBi.
  • the radome 161 thus makes it possible to increase the overall gain of the antenna in linear polarization by approximately 3 dBi.
  • the figure 19 illustrates an example of an antenna system comprising a metamaterial radome based on split resonator optimized for the UHF-RFID band. For the sake of clarity, only one half of the antenna system is represented on the figure 19 .
  • the radiating element 2003 and the ground plane 2004 are sized to operate in the UHF-RFID band.
  • the length of the radiating element 2003 is about 75mm and the length of the ground plane 2004 is about 225mm.
  • the figure 20 presents the 2100 gain curve of the antenna of the figure 19 , in the absence of a radome, in linear polarization for the frequency band from 800 MHz to 1 GHz.
  • the 2001 radome includes a split resonator network optimized for the UHF-RFID band.
  • the figure 21 illustrates an elementary block comprising a split resonator optimized for the UHF-RFID band
  • the elementary block 2200 comprises a support 2201 of dielectric material comprising an upper face 2202 on which is disposed a split ring resonator 2204.
  • the support 2201 is of square shape. Of course, it may be of another form (rectangular, circular, ..., following the shape of the split ring resonator). Each side of the square measures approximately 22mm.
  • the support 2201 has a height (hsub) of about 1.6mm.
  • the split ring resonator 2204 comprises an inner split square 22041 and an outer split square 22042.
  • the inner split square 22041 is formed by a metal track with a width of about 1 mm. Each side of the split square inside 22041 measures about 17mm.
  • the inner split square 22041 includes a slot whose width is about 2mm.
  • the spacing between the split inner 22041 and outer 22042 split is about 0.5mm.
  • the outer split square 22042 is formed by a metal track of approximately 1mm width. Each side of the outer split square 22042 measures about 20mm.
  • the outer split square 22042 comprises a slot whose width is substantially equal to that of the slot of the inner split square 22041, that is to say about 2mm.
  • the slits of the inner split and the outer split 22041 are aligned with each other.
  • the HFSS (registered trademark) software was used to extract the permittivity ( ⁇ ) and permeability ( ⁇ ) parameters of a network made up of elementary blocks of left-hand material 170.
  • the figure 22 presents the curves of the real portions of permittivity 2301 and permeability 2302 of a network constituted by elementary blocks 2200 of the figure 21 for the frequency band from 500 MHz to 1 GHz.
  • the network of elementary blocks of the figure 21 has a negative permeability for frequencies in the 820 MHz to 900 MHz band.
  • the radome 2001 is placed at a distance of about 40 mm (that is to say approximately ⁇ 0/8 ) from the radiating element 2003.
  • the figure 23 presents the gain curve 2402 of the antenna system 2000 of the figure 19 in linear polarization for the frequency band from 840 MHz to 1 GHz. For ease of comparison, we have shown on the figure 23 the antenna gain curve 2100 2005 (without radome) in linear polarization.
  • the antenna system 2000 of the figure 19 in linear polarization has a resonance frequency at about 940 MHz and a maximum gain of about 8.2 dBi.
  • the radome 2001 thus makes it possible to increase the overall gain of the antenna in linear polarization by approximately 2.4 dBi.
  • the antennal structure (also referred to above antenna system) may consist of a radiating element, a ground plane and a metamaterial radome of parallelepiped shape or spherical plain or hollow cap.
  • a radome is transparent to electromagnetic waves.
  • the radiating element may be in planar structure, wire or volume, and any geometric shape.
  • the radiating element may be separated from the ground plane by a volume which may consist of air, dielectric and / or magnetic materials.
  • the antenna structure may not have a ground plane.
  • a second metamaterial radome according to the invention.
  • This second radome extends below the element radiating and is placed at the same distance from the radiating element as the first radome (extending above the radiating element).
  • the metamaterial radome may be in the form of a cylinder (the radiating element extending inside the cylinder). This radome is therefore well suited to the case of a wired half-wave antenna or a helix antenna.
  • the metamaterial radome according to the invention can be positioned vertically or perpendicularly to the plane of the radiating element.
  • the metamaterial radome according to the invention is positioned vertically in the plane of the radiating element ( figure 24 )
  • the circular polarization is perfect.

Landscapes

  • Details Of Aerials (AREA)
  • Waveguide Aerials (AREA)

Claims (8)

  1. Metamaterialstruktur (43), die mindestens einen Elementarblock (60) umfasst, der einen Träger (61) aus dielektrischem Material umfasst, wobei der Träger eine Oberseite und eine Unterseite umfasst,
    dadurch gekennzeichnet, dass der mindestens eine Elementarblock eine erste elektrisch leitfähige Einheit (62) umfasst, die auf der Oberseite des Trägers (61) angeordnet ist und Folgendes umfasst:
    - ein erstes leitfähiges Element mit der Form eines C (621), das ein erstes und ein zweites Ende (E1, E2) umfasst;
    - ein zweites leitfähiges Element mit der Form eines C (622), das ein drittes und ein viertes Ende (E3, E4) umfasst, wobei das erste und das zweite leitfähige Element derart in Bezug zueinander eingerichtet sind, dass das erste (E1) und dritte (E3) Ende sich gegenüberstehen und durch einen ersten Raum getrennt sind, und das zweite (E2) und das vierte (E4) Ende sich gegenüberstehen und durch einen zweiten Raum getrennt sind;
    - einen ersten Verbinder (623, 1323), der ausgestaltet ist, um das erste Ende (E1) mit dem vierten Ende (E4) zu verbinden.
  2. Metamaterialstruktur nach Anspruch 1, dadurch gekennzeichnet, dass das erste und das zweite leitfähige Element mit der Form eines C identisch sind.
  3. Metamaterialstruktur nach einem der Ansprüche 1 und 2, dadurch gekennzeichnet, dass der erste Verbinder eine geradlinige Form aufweist.
  4. Metamaterialstruktur nach einem der Ansprüche 1 bis 3, dadurch gekennzeichnet, dass der mindestens eine Elementarblock eine zweite elektrisch leitfähige Einheit (133) umfasst, die auf der Unterseite des Trägers (131) angeordnet ist und Folgendes umfasst:
    - ein drittes leitfähiges Element mit der Form eines C (1331), das ein fünftes und ein sechstes Ende (E15, E16) umfasst;
    - ein viertes leitfähiges Element mit der Form eines C (1332), das ein siebtes und ein achtes Ende (E17, E18) umfasst, wobei das dritte und das vierte leitfähige Element derart in Bezug zueinander eingerichtet sind, dass das fünfte (E15) und das siebte (E17) Ende sich gegenüberstehen und durch einen dritten Raum voneinander getrennt sind, und das sechste (E16) und das achte (E18) Ende einander gegenüberstehen und durch einen vierten Raum getrennt sind;
    - einen zweiten Verbinder (1333), der ausgestaltet ist, um das fünfte Ende (E15) mit dem achten Ende (E18) zu verbinden,
    und dadurch, dass die Mitten des ersten (1323) und des zweiten (1333) Verbinders übereinander liegen.
  5. Metamaterialstruktur nach Anspruch 4, dadurch gekennzeichnet, dass die erste und die zweite leitfähige Einheit mit einer Drehung von 90° des ersten Verbinders in Bezug zum zweiten Verbinder übereinander liegen.
  6. Metamaterialstruktur nach einem der Ansprüche 4 und 5, dadurch gekennzeichnet, dass die erste und die zweite leitfähige Einheit identisch sind.
  7. Metamaterialstruktur nach einem der Ansprüche 1 bis 6, dadurch gekennzeichnet, dass die erste leitfähige Einheit mindestens ein aktives Bauelement umfasst.
  8. Metamaterialstruktur nach einem der Ansprüche 4 bis 7, dadurch gekennzeichnet, dass die zweite leitfähige Einheit mindestens ein aktives Bauelement umfasst.
EP12709129.6A 2011-03-31 2012-03-19 Antennenstrukturen mit einer kombination aus metamaterialien Not-in-force EP2692018B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR1152692A FR2973585B1 (fr) 2011-03-31 2011-03-31 Structures antennaires associant des metamateriaux.
PCT/EP2012/054841 WO2012130661A1 (fr) 2011-03-31 2012-03-19 Structures antennaires associant des métamatériaux

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EP2692018A1 EP2692018A1 (de) 2014-02-05
EP2692018B1 true EP2692018B1 (de) 2015-06-10

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EP2692018A1 (de) 2014-02-05
US9293834B2 (en) 2016-03-22
FR2973585A1 (fr) 2012-10-05
FR2973585B1 (fr) 2013-04-26
US20140111400A1 (en) 2014-04-24
WO2012130661A1 (fr) 2012-10-04
FR2973586B1 (fr) 2013-10-11
FR2973586A1 (fr) 2012-10-05

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