EP3280226A1 - Verfahren und anordnung zur bereitstellung von flackerfreiem licht mit zwei ausgangskanälen - Google Patents

Verfahren und anordnung zur bereitstellung von flackerfreiem licht mit zwei ausgangskanälen Download PDF

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Publication number
EP3280226A1
EP3280226A1 EP16182738.1A EP16182738A EP3280226A1 EP 3280226 A1 EP3280226 A1 EP 3280226A1 EP 16182738 A EP16182738 A EP 16182738A EP 3280226 A1 EP3280226 A1 EP 3280226A1
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EP
European Patent Office
Prior art keywords
current
output
colour
channel
emitting means
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP16182738.1A
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English (en)
French (fr)
Inventor
Jouni VANHANEN
Lauri Syväranta
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Helvar Oy AB
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Helvar Oy AB
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Publication date
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Priority to EP16182738.1A priority Critical patent/EP3280226A1/de
Publication of EP3280226A1 publication Critical patent/EP3280226A1/de
Withdrawn legal-status Critical Current

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/20—Controlling the colour of the light
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/50—Circuit arrangements for operating light-emitting diodes [LED] responsive to malfunctions or undesirable behaviour of LEDs; responsive to LED life; Protective circuits
    • H05B45/59—Circuit arrangements for operating light-emitting diodes [LED] responsive to malfunctions or undesirable behaviour of LEDs; responsive to LED life; Protective circuits for reducing or suppressing flicker or glow effects
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/395—Linear regulators

Definitions

  • the invention relates to using semiconductor light sources to provide lighting that is controllable with respect to at least intensity and possibly also colour and/or colour temperature.
  • the invention relates to avoiding visible flickering of the lights.
  • PWM dimming where the acronym PWM comes from pulse width modulation. Basically it means switching the semiconductor light source on and off rapidly enough so that the human eye does not recognize the changes but only perceives the mean intensity of lighting that depends on the on/off duty cycle.
  • PFM pulse frequency modulation
  • PDM pulse density modulation
  • PWM dimming is used as a general designation of all dimming schemes that utilize rapid on/off switching to achieve a perceived mean intensity.
  • Methods for reducing the output current of a driver device to implement PWM dimming can be generally designated as pulse-based current reduction.
  • the number and relative weights of higher frequency components needed to accurately model the PWM pulse train depend on how steep and sharp the flanks of the PWM pulses are.
  • the sum of two PWM dimmed light streams is the sum of two such sums and thus contains a complicated matrix of oscillations at a large number of frequencies.
  • the interference between two light sources has prominent significance in the generation of so-called tunable white light.
  • White LEDs of two different colour temperatures can be driven at different relative intensities, so that the resultant light appears to have a colour temperature that is the weighted sum of the original colour temperatures of the different light sources.
  • Using exactly the same PWM frequency for both of them might help to mitigate some interference problems, but the synchronization must be very good, because already a difference of 1 Hz creates a beat frequency with one constructive-interference peak and one destructive-interference valley per second, which is easily perceivable to a human observer.
  • the objects of the invention are achieved with a hybrid dimming strategy in which constant current reduction is used in each channel between the maximum intensity and a threshold, and PWM dimming is used between the threshold and a minimum intensity, so that it becomes unlikely that both channels would be in the PWM dimming range simultaneously.
  • a driver device for semiconductor light-emitting means comprising:
  • a luminaire comprising a driver device of the kind described above and semiconductor light-emitting means coupled to receive the controllable output current from said first output channel and said second output channel.
  • a method for generating controllable output current simultaneously for first semiconductor light-emitting means of first colour and second semiconductor light-emitting means of second colour comprising:
  • Fig. 1 illustrates schematically a driver device 101 for semiconductor light-emitting means 102 and 103.
  • the driver device comprises a first output channel 104 and a second output channel 105.
  • the output channels 104 and 105 are essentially controllable current sources.
  • the first output channel 104 is configured to provide a controllable output current lout1 for light-emitting means 102 of first colour.
  • said first colour is so-called cool white, i.e. white light the spectrum of which resembles the visible part of blackbody radiation from an object the surface temperature of which is relatively high, such as 6500K.
  • the second output channel 105 is configured to provide a controllable output current lout2 for light-emitting means 103 of second colour.
  • said second colour is so-called warm white, i.e. white light the spectrum of which resembles the visible part of blackbody radiation from an object the surface temperature of which is significantly lower, such as 2700K.
  • These colours and colour temperatures are used for the sake of example, and any other colours or colour temperatures could be used instead.
  • the first and second colours may even be the same colour unless it is explicitly said that they are different colours.
  • the driver device 101 comprises a control unit 106 that is configured to receive colour setting commands, and a power conversion unit 107 that receives mains power and distributes it in appropriate form to the first 104 and second 105 output channels.
  • the power conversion unit 107 may comprise e.g. an input section with EMI filter(s) and rectifier(s), and a PFC (power factor correction) section that comprises one or more switched-mode power supplies for synchronizing the current drawn from the mains power with the voltage waveform of the mains power.
  • colour setting command is used as a general designation of all kinds of machine-readable or machine-executable instructions that indicate to the control unit 106 the characteristics of a combined emission spectrum that should be produced by using the semiconductor light-emitting means that the control unit 106 has at its disposal.
  • the semiconductor light-emitting means are white LEDs of two different colour temperatures
  • a colour setting command may be a command to produce white light at a characteristic colour temperature that is at or between the extremes set by the characteristic colour temperatures of the component light sources 102 and 103.
  • the effective electric current through each light-emitting means defines the emission intensity at the respective colour, and the combined emission spectrum is the weighted sum of the component spectra, where the weights are the relative magnitudes of the effective electric currents.
  • the control unit 106 is configured to set the simultaneous output currents lout1 and lout2 of the first 104 and second 105 output channels to match a received colour setting command.
  • the control unit 106 may comprise e.g. one or more processors programmed to carry out the necessary functions.
  • a control interface 108 is provided so that the control unit 106 may receive the colour setting commands from a remote device.
  • the control interface 108 may conform to a standard of a building automation system, so that the colour setting commands can be created and distributed with a central controlling device that follows that standard.
  • the standard may be part 209 of the standard IEC 62386, so that the colour setting commands may be so-called DALI Type 8 commands.
  • the control interface 108 may alternatively or additionally comprise a wireless interface, so that the control unit 106 may receive colour setting commands conforming to e.g. the Bluetooth, Bluetooth Low Energy, ZigBee, WLAN, IrDA, or NFC standards or to some other commonly used communications standards.
  • the driver device 101 comprises an outer cover, so that circuitry of the first output channel 104, the second output channel 105, and the control unit 106 are all inside the outer cover.
  • Electric connectors 109 and 110 are provided that are accessible from outside the outer cover for making connections to the light-emitting means 102 and 103 of first and second colour.
  • the semiconductor light-emitting means 102 and 103 may be provided in one or more so-called LED modules, which are essentially circuit boards the surface of which serves both as an attachment surface of the LEDs and as a carrier of conductive tracks through which the electric currents flow to and from the LEDs.
  • an integrated driver and LED module is built, having a common circuit board so that at least part of the circuitry of the first output channel 104, second output channel 105, and control unit 106 is located on the same circuit board on which at least a part of the light-emitting means 102 and 103 are also located.
  • Each of the first 104 and second 105 output channels is capable of both constant current reduction and pulse-based current reduction.
  • Constant current reduction means that the amperage of a steadily flowing output current is reduced
  • pulse-based current reduction means producing rapidly repeated pulses of output current and reducing the portion of time when output current flows in relation to the portion of time when output current doesn't flow.
  • pulse-based current reduction may take the form of e.g. pulse width modulation, pulse frequency modulation, or pulse density modulation.
  • Circuits that are capable of reducing current are naturally also capable of increasing current by performing an opposite operation; for example pulse-based current increasing means producing rapidly repeated pulses of output current and increasing the portion of time when output current flows in relation to the portion of time when output current doesn't flow.
  • the driver device is configured to apply so-called hybrid dimming in both the first 104 and the second 105 output channel.
  • Hybrid dimming means that constant current reduction is used for at least one range of desired output intensities and pulse-based current reduction is used for at least another range of desired output intensities. Said ranges may be adjacent and non-overlapping on the intensity axis, but they may also overlap partly or wholly.
  • Fig. 2 illustrates a non-overlapping hybrid dimming scheme in which an output current of a channel is set through constant current reduction between a maximum (100% output intensity) and a threshold value (here: 20% output intensity), and through pulse-based current reduction (here: PWM) between said threshold value and a minimum (0% intensity).
  • the solid curve in fig. 2 shows how the peak current (which is synonymous to the amperage of the steadily flowing output current when duty cycle is 100%) decreases from its maximum value Imax to a smaller value Imin linearly when the output intensity of the corresponding channel decreases from 100% to 20%, and remains constant at said value Imin in the output intensity range between 20% and 0%.
  • the dotted curve in fig. 2 shows how the duty cycle remains at 100% when the output intensity of the corresponding channel decreases from 100% to 20%, and decreases linearly from 100% to 0% when the output intensity decreases from 20% to 0%.
  • a first output channel has been set to 10% output intensity and the second channel has been set to 90% output intensity, as shown by the vertical lines 201 and 202 respectively.
  • the output current produced by the first output channel comes at peak value Imin and duty cycle 50%, while the output current produced by the second output channel comes at a peak value only slightly below the maximum output current Imax and duty cycle 100%. Since only one of the channels is applying pulse-based current reduction (the other having 100% duty cycle), there can be no interference between PWM frequencies, and flicker is thus avoided.
  • the control unit 106 of the driver device 101 is configured to implement changes in set colour at least through reciprocal changes in the output currents of the first 104 and second channels 105.
  • An example of such reciprocal changes is illustrated by the single-ended horizontal arrows in fig. 2 : the intensity of the first output channel is increased and the intensity of the second output channel is decreased.
  • Fig. 3 shows how, as a result of said reciprocal change, the first output channel has been set to 30% intensity and the second output channel has been set to 70% intensity, as shown by the vertical lines 301 and 302 respectively. None of the channels is applying pulse-based current reduction, so there can be no interference between PWM frequencies and flicker is again avoided.
  • the sum of the channel-specific intensities is 100% in each of figs. 2 and 3 , meaning that the combined light output is not dimmed, only its colour (or colour temperature) is changed.
  • the first channel in the examples above is the 6500K channel and the second channel is the 2700K channel of fig. 1
  • the combined output spectrum corresponds to white light at 3080K in fig. 2 (calculated as 0.1*6500K + 0.9*2700K) and white light at 3840K in fig. 3 (calculated as 0.3*6500K + 0.7*2700K), at full overall intensity.
  • Dimming the combined light output may result in a situation in which the channel-specific intensity of each channel is below 20%, so both channels may be in the pulse-based current reduction range. In that case there is the possibility of interference-based flicker. However, since the overall intensity of the combined output spectrum is relatively low in such a case, the possible flicker may be more difficult to perceive and it may have less somatic effects than if flicker occurred at full or nearly full overall intensity.
  • the exemplary threshold value 20% has been used above, but it may be larger or smaller, for example 10%.
  • a threshold value can be selected for example on the basis of energy consumption and colour consistency: if the efficiency of the output channels can be kept at good level and if the low current does not cause much distortion in the spectrum of emitted light, the threshold value can be relatively small. Correspondingly if the efficiency of the output channels suffers significantly and/or the emitted colour suffers from heavy distortion at lower peak current levels, it is advisable to select a larger threshold value.
  • the control unit receives the colour setting commands (and possibly intensity setting commands) that define the desired values of T(and E ). It may then calculate the channel-specific intensities E i using equations (1) and (2). If there are more than 2 channels, there may be several possible values for the E i that lead to the desired characteristic colour temperature T and relative intensity E of the combined output spectrum. In that case the control unit may utilize a suitable optimization algorithm, for example so that it aims at keeping each selected E i value as small as possible to reduce the generation of heat in each channel. It is also possible that the selection of available colour temperatures T of the combined output spectrum is limited, for example because the available set of command words for colour temperature is limited.
  • the optimal E i values for each desired characteristic colour temperature T at 100% output intensity may have been calculated beforehand and stored in a table in the memory of the control unit.
  • the E i values to be used are then obtained by scaling the stored values with the desired overall relative output intensity E .
  • Fig. 4 illustrates a driver device for semiconductor light-emittting means according to an embodiment.
  • the first block on the main power line is the input section 401, which comprises rectifier and filter functionalities and produces a DC (or rectified AC) voltage between the lines VDC and GND.
  • the next block is the PFC (power factor correction) block 402, which may comprise a suitably controlled switched-mode power supply or some other kind of PFC functionality.
  • the DC/DC converter block 403 produces the so-called bus voltage between the lines VBUS and 0V, to which the parallel output channels or output stages 404 and 405 are coupled. Additionally the DC/DC converter block 403 produces an auxiliary voltage level on line VCC, which is also coupled to the output channels or output stages 404 and 405.
  • a monitor circuit and soft start functionality 406 may control the operation of the PFC 402 and DC/DC converter block 403.
  • a microcontroller 407 and an output current setting block 408 represent schematically one or more processors and associated circuits that constitute the control unit of the driver device in fig. 4 .
  • Some examples of associated circuits are explicitly shown, like a sensor functionality (NTC; negative temperature coefficient; meaning a temperature sensor) 409 and a control bus interface 410.
  • NTC negative temperature coefficient
  • a control bus interface 410 Included in the schematically shown microcontroller 407 but not explicitly illustrated in fig. 4 is a program memory for storing one or more sets of machine-readable instructions that constitute the program to be executed by said one or more processors. Executing said machine-readable instructions cause the implementation of the method(s) according to embodiment(s) of the invention.
  • the output current setting block 408 may comprise for example an amplifier based coupling that includes an external connection, to which an external current setting resistor can be connected for setting the maximum output current to be produced by any of the two output channels.
  • Such couplings are well known in the art of LED drivers and do not need to be described here in more detail. If the auxiliary voltage VCC is not needed in the output channels, it may be just for providing an operating voltage to some active circuit(s) in the output current setting block 408.
  • Control connections from the blocks 407 and 408 that constitute the control unit to the output channels 404 and 405 comprise the ISET and CTRL lines in fig. 4 .
  • One exemplary ways of using such control lines is such where the commands to set the actual output currents of the output channels come through the CTRL1 and CTRL2 lines respectively, while the ISET lines serve to set the maximum output current (also known as Imax in the description earlier).
  • Fig. 5 illustrates a simplified example of a circuit that can be used for example as one of the output channels 404 and 405 in the driver device of fig. 4 .
  • the circuit of fig. 5 is essentially a switched-mode power supply for generating the output current of the respective output channel. It comprises a current switch, which here is a MOSFET 501, as well as a switch driver circuit 502 configured to provide switching pulses to the current switch at a switching frequency.
  • the switch driver circuit 502 is most advantageously an integrated circuit.
  • Other typical components of the switched-mode power supply are an inductor 503, a freewheeling diode 504, a current sensing resistor 505 and a number of capacitors 506, 507, and 508.
  • a special feature of the circuit of fig. 5 is that the output current it produces can be set through constant current reduction and through pulse-based current reduction using a single control input 509 of the switch driver circuit 502.
  • a switch driver circuit is for example the MP24894 circuit available from Monolithic Power Systems, San Jose, California.
  • the value of the first threshold is 0.3 V
  • the value of the second threshold is 2.7 V.
  • a voltage smaller than 0.3 V between the driver circuit's input pin marked EN and the ground potential pin GND keeps the MP24894 from giving any switching pulses at all, while a voltage larger than 0.3 V but smaller than 2.7 V enables it to give switching pulses but simultaneously limits the peak current between a minimum value and a maximum value so that the closer the voltage is to 2.7 V the closer the peak current can be to the maximum value.
  • control unit should contain a control pulse formatter coupled to the control input 509 and configured to provide said control input with control pulses of variable amplitude exceeding or meeting said first threshold at a pulse width modulation frequency that is smaller than the switching frequency mentioned above.
  • a control pulse formatter may be implemented e.g. as a programmed executable process within the microcontroller block 407 in fig. 4 , or as a separate circuit element consisting analogue and/or digital components.
  • the output channel implements pulse-based current reduction at the PWM frequency and the minimum peak current value. Setting the output current through constant current reduction necessitates maintaining the control input 509 at the appropriate voltage between 0.3 V and 2.7 V (where maintaining is conceptually the same as PWM with 100% duty cycle).
  • Fig. 6 illustrates conceptually a slightly different approach in which there are two control signals to the output channel 601: one for setting the output current through constant current reduction (CCR) and another for setting the output current through pulse-based current reduction (PWM).
  • the two control signals could come directly from two different outputs of a processor, but in fig. 6 it is assumed that there is a command formatter 602 that produces the control signals from one control command received from a command processing unit 603.
  • the circuit is essentially a switched-mode power supply for generating the output current of the respective output channel. It comprises a current switch 701 and a switch driver circuit 702 configured to provide switching pulses to said current switch at a switching frequency.
  • the switch driver circuit 702 has an enabling control input labelled EN in fig. 7 , and is configured to respond to voltages exceeding an enabling threshold at said control input (to be more accurate, between the control input EN and the ground potential pin GND) by enabling the generation of switching pulses.
  • the circuit comprises also a current feedback circuit 703 for the switch driver circuit 702.
  • the switch driver circuit 702 is configured to respond to signals provided by said current feedback circuit 703 by controlling at least one of the length, the frequency, or the duty cycle of the switching pulses.
  • the command formatter is coupled to the enabling control input through line 704 and configured to provide the control input with control pulses at a pulse width modulation frequency that is smaller than the switching frequency mentioned above. Effectively the control pulses repetitively enable and disable the operation of the output channel, thus implementing pulse-based current reduction.
  • the command formatter is also configured to provide the current feedback circuit 703 with a gain control signal through line 705.
  • the gain control signal is effective to change a feedback gain of the current feedback circuit 703. In the implementation of fig. 7 the gain control signal changes the conductivity of a bipolar transistor, which in turn controls the flow of currents through the branches of the resistor network from which the current feedback signal is taken to the appropriate input pin of the switch driver circuit 702.
  • a luminaire comprises a driver device according to one of the embodiments described so far, as well as semiconductor light-emitting means coupled to receive the controllable output current from the first output channel and the second output channel.
  • the aim of the method is to generate controllable output current simultaneously for first semiconductor light-emitting means of first colour and second semiconductor light-emitting means of second colour.
  • the method comprises receiving a colour setting command and resolving how the currents through the first and second light-emitting means are to be set to match said colour setting command.
  • Said resolving may be accomplished for example by calculating or by using the received colour setting command as a key to a look-up table from which the appropriate commands and/or parameters are read for setting the currents through the first and second light-emitting means.
  • the method comprises setting one of the currents through the first and second light-emitting means through constant current reduction and the other through pulse-based current reduction.
  • the current to be set through constant current reduction is the one for channel-specific intensity between a maximum and threshold value and the current to be set through pulse-based current reduction is the one for channel-specific intensity between said threshold value and a minimum.
  • the threshold value of relative intensity defines a sharp division between a PWM domain (lower intensities) and a CCR domain (higher intensities), but there can be a range of intermediate relative intensities within which both constant current reduction and pulse-based current reduction are applied.
  • the arrangement can be equipped with optical feedback that measures the actual emitted intensity and/or colour and/or colour temperature of light, either for each channel separately or for the combined output spectrum, so that the result of the measurement may fine tune the channel-specific relative intensities to achieve the desired combined output spectrum as accurately as possible.
  • the mapping between colour commands and channel-specific peak currents and/or duty cycles may comprise time-dependent factors that compensate for effects caused by the ageing of the LEDs.
  • a flicker detector may be employed that detects interference-based flicker and e.g. changes the threshold value at which pulse-based current reduction changes to constant current reduction, so that the threshold may dynamically take into account the actual occurrence of flicker.

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  • Circuit Arrangement For Electric Light Sources In General (AREA)
EP16182738.1A 2016-08-04 2016-08-04 Verfahren und anordnung zur bereitstellung von flackerfreiem licht mit zwei ausgangskanälen Withdrawn EP3280226A1 (de)

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EP16182738.1A EP3280226A1 (de) 2016-08-04 2016-08-04 Verfahren und anordnung zur bereitstellung von flackerfreiem licht mit zwei ausgangskanälen

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EP16182738.1A EP3280226A1 (de) 2016-08-04 2016-08-04 Verfahren und anordnung zur bereitstellung von flackerfreiem licht mit zwei ausgangskanälen

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070045524A1 (en) * 2003-06-23 2007-03-01 Advanced Optical Technologies, Llc Intelligent solid state lighting
EP2364064A2 (de) * 2010-03-03 2011-09-07 Panasonic Electric Works Co., Ltd. LED-Beleuchtungsvorrichtung
US20130293134A1 (en) * 2010-11-12 2013-11-07 Toshiba Lighting & Technology Corporation Led lighting device and led luminaire
US20160073473A1 (en) * 2014-09-04 2016-03-10 Liang Fang Led driver
EP3043625A1 (de) * 2015-01-09 2016-07-13 Helvar Oy Ab Dimmbarer LED-Treiber und Verfahren zur Herstellung eines Dimmsignals

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070045524A1 (en) * 2003-06-23 2007-03-01 Advanced Optical Technologies, Llc Intelligent solid state lighting
EP2364064A2 (de) * 2010-03-03 2011-09-07 Panasonic Electric Works Co., Ltd. LED-Beleuchtungsvorrichtung
US20130293134A1 (en) * 2010-11-12 2013-11-07 Toshiba Lighting & Technology Corporation Led lighting device and led luminaire
US20160073473A1 (en) * 2014-09-04 2016-03-10 Liang Fang Led driver
EP3043625A1 (de) * 2015-01-09 2016-07-13 Helvar Oy Ab Dimmbarer LED-Treiber und Verfahren zur Herstellung eines Dimmsignals

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