JPH0429310B2 - - Google Patents
Info
- Publication number
- JPH0429310B2 JPH0429310B2 JP58006182A JP618283A JPH0429310B2 JP H0429310 B2 JPH0429310 B2 JP H0429310B2 JP 58006182 A JP58006182 A JP 58006182A JP 618283 A JP618283 A JP 618283A JP H0429310 B2 JPH0429310 B2 JP H0429310B2
- Authority
- JP
- Japan
- Prior art keywords
- voltage
- circuit
- oscillation
- resistor
- output
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
- 230000010355 oscillation Effects 0.000 claims description 55
- 239000003990 capacitor Substances 0.000 claims description 16
- 238000004804 winding Methods 0.000 claims description 9
- 230000008929 regeneration Effects 0.000 claims description 6
- 238000011069 regeneration method Methods 0.000 claims description 6
- 230000000087 stabilizing effect Effects 0.000 claims description 3
- 230000006641 stabilisation Effects 0.000 claims 1
- 238000011105 stabilization Methods 0.000 claims 1
- 230000007423 decrease Effects 0.000 description 7
- 230000000630 rising effect Effects 0.000 description 6
- 238000001514 detection method Methods 0.000 description 5
- 238000010586 diagram Methods 0.000 description 3
- 230000002238 attenuated effect Effects 0.000 description 2
- 230000001681 protective effect Effects 0.000 description 2
- 238000000034 method Methods 0.000 description 1
- 230000002265 prevention Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Power Conversion In General (AREA)
- Inverter Devices (AREA)
Description
【発明の詳細な説明】
本発明は、コレクタ同調発振回路を備え、発振
回路を構成する発振トランジスタのベース電流を
制御することにより安定した高圧出力を得る安定
化高圧電源に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a stabilized high-voltage power supply that includes a collector-tuned oscillation circuit and obtains a stable high-voltage output by controlling the base current of an oscillation transistor constituting the oscillation circuit.
従来の安定化高圧電源を第１図に示す。第１図
において、高圧電源１は、制御回路２と、発振用
トランジスタTr4を有するコレクタ同調発振回路
３と、抵抗値が高い第１抵抗回路部４１および発
振用トランジスタTr4にベース電流を供給する第
２抵抗回路部４２を有する抵抗回路４と、保護用
トランジスタTr3よりなる保護回路５と、コンデ
ンサC1、抵抗R1、基準電圧E1、出力Ａと基準電
圧E1とを比較増幅して制御回路２を制御する比
較増幅器AMPを備えた負帰還制御回路６と、出
力回路７とを備える。 Figure 1 shows a conventional stabilized high-voltage power supply. In FIG. 1, a high-voltage power supply 1 supplies base current to a control circuit 2, a collector-tuned oscillation circuit 3 having an oscillation transistor Tr 4 , a first resistor circuit section 41 having a high resistance value, and an oscillation transistor Tr 4 . A resistor circuit 4 having a second resistor circuit section 42, a protection circuit 5 including a protection transistor Tr3 , a capacitor C1 , a resistor R1 , a reference voltage E1 , and an output A and a reference voltage E1 are compared and amplified. The negative feedback control circuit 6 includes a comparison amplifier AMP that controls the control circuit 2 by controlling the control circuit 2, and an output circuit 7.
この電源回路１では、制御回路２の出力点P1
の電圧Vaが、ツエナーダイオードZDのツエナー
電圧Vzよりも高いときにツエナーダイオードZD
を導通させることによりベース電流を発振用トラ
ンジスタTr4に供給するようになつている。そし
て、発振が開始されると、正帰還巻線L3と再生
用コンデンサC2により接続点P3の電圧Vcは負電
位となり、接続点P2の電圧Vbを引込む働きをす
る。 In this power supply circuit 1, the output point P 1 of the control circuit 2
When the voltage V a of the Zener diode ZD is higher than the Zener voltage V z of the Zener diode ZD
By making conductive, base current is supplied to the oscillation transistor Tr4 . Then, when oscillation starts, the voltage V c at the connection point P 3 becomes a negative potential due to the positive feedback winding L 3 and the regeneration capacitor C 2 , which acts to pull in the voltage V b at the connection point P 2 .
この為保護用トランジスタTr3は導通すること
なく、回路は正常動作する。このような高圧電源
１において、負荷RL側で出力短絡が生じたとき
には、正帰還巻線L3の誘起電圧は垂下特性によ
り減衰する。これにより接続点P3の電圧Vcは正
電位となり、接続点P2の電圧Vbは上昇すること
になる。この結果、保護用トランジスタTr3が導
通状態となり、制御回路２の出力点P1の電圧Va
が低下する。このため、第２抵抗回路部４２内の
ツエナーダイオードZDが不導通になる。これに
より、発振用トランジスタTr4のベースにはベー
ス電流が供給されなくなる。このため、発振回路
３は発振しなくなる。こうして、高圧出力の短絡
からこの電源１は保護される。 Therefore, the protection transistor Tr 3 does not become conductive, and the circuit operates normally. In such a high voltage power supply 1, when an output short circuit occurs on the load R L side, the induced voltage in the positive feedback winding L 3 is attenuated due to drooping characteristics. As a result, the voltage V c at the connection point P 3 becomes a positive potential, and the voltage V b at the connection point P 2 increases. As a result, the protection transistor Tr 3 becomes conductive, and the voltage V a at the output point P 1 of the control circuit 2
decreases. Therefore, the Zener diode ZD in the second resistance circuit section 42 becomes non-conductive. As a result, no base current is supplied to the base of the oscillation transistor Tr4 . Therefore, the oscillation circuit 3 no longer oscillates. This power supply 1 is thus protected against short circuits of the high voltage output.
次に、出力短絡状態が解除されて発振回路３を
起動させる場合に、出力点P1の電圧Vaをツエナ
ーダイオードZDのツエナー電圧Vzよりも高くさ
せる必要がある。そして、この起動を確実にする
ために、第１図に示すように、起動用抵抗として
抵抗体R6をツエナーダイオードZDに対して設け
ることが考えられるが、無負荷時には余分なベー
ス電流を供給することになつて間欠発振を生じ、
好ましくない。 Next, when the output short-circuit state is canceled and the oscillation circuit 3 is activated, it is necessary to make the voltage V a of the output point P 1 higher than the Zener voltage V z of the Zener diode ZD. In order to ensure this startup, as shown in Figure 1, it is conceivable to provide a resistor R 6 as a startup resistor to the Zener diode ZD, but when there is no load, extra base current is supplied. This causes intermittent oscillation,
Undesirable.
本発明は、発振回路を単に通常の起動時のみな
らず、高圧出力短絡状態の解除後の起動時にもこ
の起動を確実に行え、しかも無負荷時に間欠発振
が生じないようにすることを目的とする。 The object of the present invention is to ensure that the oscillation circuit is started not only during normal startup, but also after the high voltage output short-circuit condition has been released, and to prevent intermittent oscillation from occurring during no-load conditions. do.
本発明の安定化高圧電源は、このような目的の
ために、第１抵抗回路部の抵抗体の分圧出力がベ
ースに接続された保護用トランジスタのベースと
接地電位点の間にコンデンサを接続し、制御回路
の出力電圧の立上り速度よりも第１抵抗回路部の
抵抗体の接続点における電圧の立上り速度を遅く
させるようにしてなるものである。 For this purpose, the stabilized high-voltage power supply of the present invention connects a capacitor between the base of the protection transistor, the base of which is connected to the divided voltage output of the resistor in the first resistor circuit, and the ground potential point. However, the rising speed of the voltage at the connection point of the resistor of the first resistor circuit section is made slower than the rising speed of the output voltage of the control circuit.
以下、本発明安定化高圧電源の一実施例を第２
図に基づいて詳細に説明する。第２図は本発明安
定化高圧電源の電気回路図であり、第１図と対応
する部分には同一の符号が付される。第２図にお
いては、高圧電源１０は、制御回路２と、再生用
コンデンサC2および発振トランジスタTr4等を含
むコレクタ同調・エミツタ接地型発振回路３とを
備える。このうち、制御回路２は発振回路３の発
振用トランジスタTr4のベース電流を制御するも
のである。高圧電源１０はまた、制御回路２の出
力に応答して発振用トランジスタTr4にベース電
流を供給する抵抗回路４と、抵抗回路４の出力の
一部を受けて、負荷RL側において出力短絡が生
じた時に制御回路２の出力を遮断動作する保護用
トランジスタTr3を有する保護回路５とを備え
る。このうち、抵抗回路４は、制御回路２の出力
点P1と発振用トランジスタTr4との間に並列に接
続されてなる、抵抗値が高い第１抵抗回路部４１
と、ツエナーダイオードZDを含む第２抵抗回路
部４２とを含む。第１抵抗回路部４１は複数の抵
抗体R3，R4を直列に接続させてなるとともにこ
の複数の抵抗体R3，R4の接続点P2は保護回路５
の保護用トランジスタTr3のベースに接続されて
いる。６は負帰還制御回路であり、この負帰還制
御回路６は符号Ａ，Ａで示すように高圧出力側に
接続された検出用抵抗R9からの出力を負帰還し
て制御回路２の動作を制御する。７は発振回路３
の出力に応答した高圧出力を負荷RLに与える出
力回路である。Vioは直流電源の入力端子であり、
Vputは出力端子である。RLはこの出力端子に接続
された負荷である。 Hereinafter, a second embodiment of the stabilized high voltage power supply of the present invention will be described.
This will be explained in detail based on the figures. FIG. 2 is an electrical circuit diagram of the stabilized high-voltage power supply of the present invention, and parts corresponding to those in FIG. 1 are given the same reference numerals. In FIG. 2, the high-voltage power supply 10 includes a control circuit 2, and a collector-tuned/grounded-emitter type oscillation circuit 3 including a regeneration capacitor C2 , an oscillation transistor Tr4 , and the like. Of these, the control circuit 2 controls the base current of the oscillation transistor Tr 4 of the oscillation circuit 3. The high-voltage power supply 10 also includes a resistor circuit 4 that supplies a base current to the oscillation transistor Tr 4 in response to the output of the control circuit 2, and a resistor circuit 4 that receives a portion of the output of the resistor circuit 4 and shorts the output on the load R L side. The protection circuit 5 includes a protection transistor Tr 3 that operates to cut off the output of the control circuit 2 when a problem occurs. Of these, the resistance circuit 4 includes a first resistance circuit section 41 having a high resistance value and connected in parallel between the output point P 1 of the control circuit 2 and the oscillation transistor Tr 4 .
and a second resistance circuit section 42 including a Zener diode ZD. The first resistance circuit section 41 is formed by connecting a plurality of resistors R 3 and R 4 in series, and the connection point P 2 between the plurality of resistors R 3 and R 4 is connected to the protection circuit 5.
is connected to the base of the protection transistor Tr3 . 6 is a negative feedback control circuit, and this negative feedback control circuit 6 negatively feeds back the output from the detection resistor R 9 connected to the high voltage output side as shown by symbols A and A to control the operation of the control circuit 2. Control. 7 is oscillation circuit 3
This is an output circuit that provides a high voltage output to the load RL in response to the output of the RL. V io is the input terminal of the DC power supply,
Vput is an output terminal. R L is the load connected to this output terminal.
発振回路３は更に発振安定化抵抗R7と、正帰
還巻線L3と、同調コンデンサC3と、高圧トラン
スＴの１次側（低圧側）巻線L1とを含む。抵抗
回路４内の第１抵抗回路部４１は、発振用トラン
ジスタTr4にベース電流を流すことが主目的では
なく高圧出力の短絡の有無を検出するための短絡
検出回路を構成するものである。このため、抵抗
体R3は高い抵抗値に設定されている。抵抗回路
４内の第２抵抗回路４２は、上記ベース電流を主
に流す主ベース電流回路を構成するものであり、
抵抗体R3は低い抵抗値に設定される。負帰還制
御回路６は、比較増幅器AMPを備える。この比
較増幅器AMPは、その逆相側入力端子−に検出
用抵抗R9からの出力が矢符Ａ，Ａで示すように
入力されるとともに、その正相側入力端子＋に基
準電源E1の出力が入力されるようになつている。
出力回路７は、高圧トランスＴの２次側（高圧
側）巻線L2と整流用ダイオードD1と火花放電防
止用抵抗R8とを含む。 The oscillation circuit 3 further includes an oscillation stabilizing resistor R 7 , a positive feedback winding L 3 , a tuning capacitor C 3 , and a primary side (low voltage side) winding L 1 of the high voltage transformer T. The first resistor circuit section 41 in the resistor circuit 4 constitutes a short circuit detection circuit whose main purpose is not to flow a base current to the oscillation transistor Tr 4 but to detect the presence or absence of a short circuit in the high voltage output. For this reason, the resistor R3 is set to a high resistance value. The second resistance circuit 42 in the resistance circuit 4 constitutes a main base current circuit through which the base current mainly flows,
Resistor R3 is set to a low resistance value. Negative feedback control circuit 6 includes a comparison amplifier AMP. This comparator amplifier AMP has the output from the detection resistor R 9 inputted to its negative phase side input terminal - as shown by arrows A and A, and the reference power supply E 1 to its positive phase side input terminal +. Output is now input.
The output circuit 7 includes a secondary side (high voltage side) winding L2 of a high voltage transformer T, a rectifying diode D1 , and a spark discharge prevention resistor R8 .
このような構成において、本発明の特徴とする
構成は、第１抵抗回路部４１を形成する抵抗R3，
R4の接続点P2と接地電位点P4との間、つまり、
保護用トランジスタTr3のベースと接地電位点P4
との間にコンデンサC5を接続するようにしたこ
とである。このコンデンサC5により、制御回路
２の出力電圧Vaの立上り速度よりもこの接続点
P2における保護用トランジスタTr3の動作電圧Vb
の立上り速度を遅くさせることができる。 In such a configuration, the feature of the present invention is that the resistors R 3 ,
Between the connection point P 2 of R 4 and the ground potential point P 4 , that is,
Base of protection transistor Tr 3 and ground potential point P 4
The reason is that a capacitor C5 is connected between the Due to this capacitor C 5 , the rising speed of the output voltage V a of control circuit 2 is faster than this connection point.
Operating voltage V b of the protection transistor Tr 3 at P 2
The rising speed of can be slowed down.
次に、動作を説明する。電源回路が起動すると
きは、負帰還制御回路６の比較増幅器AMPの逆
相側入力端子−への入力レベルが低くなつてい
る。このため、負帰還制御回路６の出力はＨレベ
ルの方向に立上つてくるので、制御回路２の出力
点P1の出力電圧Vaが大きくなる。第１抵抗回路
部４１を形成する抵抗R3，R4の接続点P2の電位
Vbは、制御回路２の出力点P1の電圧Vaの上昇と
ともに抵抗R3より流れるコンデンサＣ５への充
電電流によつて決まる。このときの時定数は比較
的大きなC5×R3となる。（ここでR3は比較的大き
な値が選定される。）したがつて、制御回路２の
出力電圧Vaの立上り速度に比べ接続点P2の動作
電圧Vbの立上り速度は遅い。 Next, the operation will be explained. When the power supply circuit starts up, the input level to the negative phase side input terminal - of the comparator amplifier AMP of the negative feedback control circuit 6 is low. Therefore, the output of the negative feedback control circuit 6 rises toward the H level, and the output voltage V a at the output point P 1 of the control circuit 2 increases. Potential at the connection point P 2 of the resistors R 3 and R 4 forming the first resistance circuit section 41
V b is determined by the charging current flowing from the resistor R 3 to the capacitor C5 as the voltage V a at the output point P 1 of the control circuit 2 rises. The time constant at this time is relatively large C 5 ×R 3 . (Here, a relatively large value is selected for R 3. ) Therefore, the rise speed of the operating voltage V b at the connection point P 2 is slow compared to the rise speed of the output voltage V a of the control circuit 2.
これは、接続点P2と接地電位点P4との間にコ
ンデンサC5が設けられているためである。この
ため、この接続点P2の動作電圧Vbが大きくなつ
て保護用トランジスタTr3が導通させられるより
も早く、出力電圧VaがツエナーダイオードZDを
導通させる値にまで上昇する。この結果、発振用
トランジスタTr4のベースにはベース電流が供給
されることになり、発振回路３が正常な発振状態
にはいる。こうして、発振回路３が正常な発振状
態にはいつたときは、制御回路２の出力点P1の
出力電圧Vaは、ツエナーダイオードZDのツエナ
ー電圧よりも高くなるように設定されているので
発振用トランジスタTr4には継続してベース電流
が供給される。また同時に、接続点P2の動作電
圧Vbは保護用トランジスタTr3の導通電圧よりも
低くなるように設定されている（R3≫R4）ので、
保護用トランジスタTr3が動作することがない。 This is because the capacitor C5 is provided between the connection point P2 and the ground potential point P4 . Therefore, the output voltage V a rises to a value that makes the Zener diode ZD conductive earlier than the operating voltage V b at the connection point P 2 increases and the protective transistor Tr 3 becomes conductive. As a result, the base current is supplied to the base of the oscillation transistor Tr 4 , and the oscillation circuit 3 enters a normal oscillation state. In this way, when the oscillation circuit 3 reaches the normal oscillation state, the output voltage V a at the output point P 1 of the control circuit 2 is set to be higher than the Zener voltage of the Zener diode ZD, so the oscillation starts. The base current is continuously supplied to the transistor Tr4 . At the same time, since the operating voltage V b of the connection point P 2 is set to be lower than the conduction voltage of the protection transistor Tr 3 (R 3 ≫ R 4 ),
Protection transistor Tr 3 does not operate.
ところが、高圧出力が短絡されたときには、発
振が減衰することにより再生用コンデンC2の電
圧Vcが上昇し、これにより接続点P2の動作電圧
Vbも上昇する。この際、前述のように、接続点
P2の電圧Vbは、接続点P1とP3を抵抗R3及びR4で
分圧しているので、、接続点P3の電圧Vcが上昇す
るとP2の電圧も上昇する。この結果、P2の電圧
Vbが保護用トランジスタTr3の導通電位に達して
保護用トランジスタTr3が導通し、制御回路２の
トランジスタTr2のベース電位を引き下げること
により制御回路２の出力電圧Vaを減少させる。
この減少後の出力電圧Vaはツエナーダイオード
ZDのツエナー電圧Vzよりも低くなるように設定
されている。このため、ツエナーダイオードZD
が不導通になつて、発振用トランジスタTr4には
抵抗R3，R4を経て流れる微少なベース電流しか
供給されなくなり、発振回路３の発振は極めて微
少な状態となる。こうして、高圧出力の短絡から
電源１０は保護される。 However, when the high voltage output is short-circuited, the oscillation is attenuated and the voltage V c of the regeneration capacitor C 2 increases, which causes the operating voltage of the connection point P 2 to increase.
V b also increases. In this case, as mentioned above, the connection point
Since the voltage V b at P 2 is divided by the resistors R 3 and R 4 between the connection points P 1 and P 3 , when the voltage V c at the connection point P 3 increases, the voltage at P 2 also increases. As a result, the voltage of P 2
When V b reaches the conduction potential of the protection transistor Tr 3 , the protection transistor Tr 3 becomes conductive, lowering the base potential of the transistor Tr 2 of the control circuit 2 and thereby reducing the output voltage V a of the control circuit 2 .
The output voltage V a after this reduction is the Zener diode
It is set to be lower than the Zener voltage V z of ZD. For this reason, the Zener diode ZD
becomes non-conductive, and only a small base current flowing through the resistors R 3 and R 4 is supplied to the oscillation transistor Tr 4 , and the oscillation of the oscillation circuit 3 becomes extremely small. In this way, the power supply 10 is protected from short circuits in the high voltage output.
そして、高圧出力の短絡が解除されたときに
は、発振回路３の負荷が軽くなり、接続点P3か
らの発振トランジスタTr4側をみたときのインピ
ーダンスは小さくなる。この結果、第１抵抗回路
部４１へ流れる微少なベース電流により発振回路
３は微少発振が成長し始める。それによつて再生
用コンデンサC2の電圧（接続点P3の電圧）Vcが
低下しはじめ、接続点P2の電圧Vbは低下してい
く。このときの時点数はC5×R4（R3≫R4）であ
り、比較的小さな値に選んであるため、P3の電
圧Vcの低下は直ちにP2の電圧Vbの低下を引き起
こす。この結果、保護用トランジスタTr3は非導
通の方向へ向いはじめ、
Vaの上昇→発振トランジスタTr4のベース電流
の増加→発振の成長→Vcの低下→Vbの低下
の繰り返しにより急速に発振は成長を始める。そ
して、ついに電圧Vaがある値以上に達したとき、
ツエナーダイオードZDが導通するに至る。すな
わち、電圧Vbは比較的遅く上昇し、比較的速く
低下するよう構成されている。この結果、発振用
トランジスタTr4にはベース電流が供給されるこ
とになつて発振回路３が円滑に発振動作を再開す
る。 Then, when the short circuit of the high voltage output is released, the load on the oscillation circuit 3 becomes lighter, and the impedance when looking at the oscillation transistor Tr 4 side from the connection point P 3 becomes smaller. As a result, the oscillation circuit 3 begins to generate minute oscillations due to the minute base current flowing to the first resistor circuit section 41 . As a result, the voltage of the regeneration capacitor C 2 (the voltage at the connection point P 3 ) V c begins to decrease, and the voltage V b at the connection point P 2 begins to decrease. The number of time points at this time is C 5 × R 4 (R 3 ≫ R 4 ), which is selected to be a relatively small value, so a decrease in the voltage V c of P 3 immediately causes a decrease in the voltage V b of P 2 . cause. As a result, the protection transistor Tr 3 begins to turn non-conductive, and the cycle of increase in V a → increase in the base current of oscillation transistor Tr 4 → growth of oscillation → decrease in V c → decrease in V b is rapidly caused. The oscillation begins to grow. Then, when the voltage V a finally reaches a certain value or higher,
Zener diode ZD becomes conductive. That is, the voltage V b is configured to rise relatively slowly and fall relatively quickly. As a result, the base current is supplied to the oscillation transistor Tr 4 , and the oscillation circuit 3 smoothly restarts its oscillation operation.
なお、上記実施例の検出用抵抗R9にかえて検
出コイルを用い、磁気フイードバツク方式の負帰
還制御回路とすることや、定電圧電源にかえて定
電流電源とすること等は全く任意になし得る。 Note that it is completely optional to use a detection coil instead of the detection resistor R9 in the above embodiment to create a negative feedback control circuit using a magnetic feedback method, or to use a constant current power supply instead of the constant voltage power supply. obtain.
以上のように、本発明によれば、第１抵抗回路
部を形成する複数の抵抗体の接続点の接地電位点
との間、つまり、保護用トランジスタのベースと
接地電位点との間にコンデンサを接続することに
より、制御回路の出力電圧の立上り速度よりもこ
の接続点における電圧の立上り速度を遅くさせて
なり、発振回路の起動が常に確実に行われ、無負
荷時に間欠発振を生じさせることもなく、負荷の
短絡時の保護動作を確実に行わせることができ
る。 As described above, according to the present invention, a capacitor is connected between the connection point of the plurality of resistors forming the first resistance circuit section and the ground potential point, that is, between the base of the protection transistor and the ground potential point. By connecting this, the rising speed of the voltage at this connection point is made slower than the rising speed of the output voltage of the control circuit, so that the oscillation circuit is always started reliably, and intermittent oscillation occurs when there is no load. Therefore, it is possible to reliably perform the protective operation when the load is short-circuited.
第１図は従来の安定化高圧電源の電気回路図、
第２図は本発明の一実施例における安定化高圧電
源の電気回路図である。
１０……高圧電源、２……制御回路、３……コ
レクタ同調発振回路、４……抵抗回路、５……保
護回路、６……負帰還制御回路、７……出力回
路、Tr3……保護用トランジスタ、Tr4……発振
トランジスタ、C5……コンデンサ。
Figure 1 is an electrical circuit diagram of a conventional stabilized high-voltage power supply.
FIG. 2 is an electrical circuit diagram of a stabilized high voltage power supply in one embodiment of the present invention. 10... High voltage power supply, 2... Control circuit, 3... Collector tuned oscillation circuit, 4... Resistance circuit, 5... Protection circuit, 6... Negative feedback control circuit, 7... Output circuit, Tr 3 ... Protection transistor, Tr 4 ...Oscillation transistor, C5 ...Capacitor.
Claims (1)
調発振回路を形成する発振トランジスタのコレク
タに接続し、他端を電圧安定化用の制御回路の電
源入力端に接続し、前記発振トランジスタのベー
ス・エミツタ間に正帰還巻線、発振安定化抵抗、
再生用コンデンサを直列に接続し、該発振安定化
抵抗と再生用コンデンサの接続点と前記制御回路
の出力端間に複数個のベース抵抗からなる第１抵
抗回路部を接続し、該第１抵抗回路部に並列にシ
エナーダイオードと抵抗体が直列接続されてなる
第２抵抗回路部を接続し、前記制御回路の制御入
力端と前記発振トランジスタのエミツタ間に接続
された保護用トランジスタのベースに前記第１抵
抗回路部の抵抗体の分圧出力を接続するととも
に、前記保護用トランジスタのベースと前記発振
トランジスタのエミツタの間にコンデンサを接続
し、前記高圧巻線の出力巻線から高圧出力を得る
ことを特徴とする安定化高圧電源。1. One end of the input winding of the high-voltage transformer is connected to the collector of an oscillation transistor forming a collector-tuned oscillation circuit, the other end is connected to the power input terminal of a control circuit for voltage stabilization, and the base and emitter of the oscillation transistor are connected. A positive feedback winding, an oscillation stabilizing resistor,
Regeneration capacitors are connected in series, and a first resistor circuit section consisting of a plurality of base resistors is connected between the connection point of the oscillation stabilizing resistor and the regeneration capacitor and the output terminal of the control circuit, and the first resistor A second resistor circuit section in which a Sienar diode and a resistor are connected in series is connected to the circuit section in parallel to the base of a protection transistor connected between the control input terminal of the control circuit and the emitter of the oscillation transistor. The divided voltage output of the resistor of the first resistor circuit section is connected, and a capacitor is connected between the base of the protection transistor and the emitter of the oscillation transistor, and a high voltage output is output from the output winding of the high voltage winding. A stabilized high-voltage power supply characterized by:
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58006182A JPS59132776A (en) | 1983-01-17 | 1983-01-17 | Stabilized high voltage power source |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58006182A JPS59132776A (en) | 1983-01-17 | 1983-01-17 | Stabilized high voltage power source |
Related Child Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP8039489A Division JPH0246167A (en) | 1989-03-30 | 1989-03-30 | Stabilized high-voltage power supply |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS59132776A JPS59132776A (en) | 1984-07-30 |
| JPH0429310B2 true JPH0429310B2 (en) | 1992-05-18 |
Family
ID=11631404
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP58006182A Granted JPS59132776A (en) | 1983-01-17 | 1983-01-17 | Stabilized high voltage power source |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS59132776A (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS61218368A (en) * | 1985-03-20 | 1986-09-27 | Murata Mfg Co Ltd | Stabilized high voltage power source |
| JPS62233066A (en) * | 1986-03-31 | 1987-10-13 | Murata Mfg Co Ltd | Stabilized high-tension power circuit |
-
1983
- 1983-01-17 JP JP58006182A patent/JPS59132776A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS59132776A (en) | 1984-07-30 |
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