JPH0477436B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION [Object of the Invention] The present invention relates to a lighting control device, and particularly to a power-saving lighting control device for incandescent lamps or discharge lamps such as high-pressure sodium lamps, metal halide lamps, mercury lamps, and fluorescent lamps.

[Prior art]

In conventional lighting control devices, a method has been proposed in which lighting is controlled by directly controlling the phase of an alternating current voltage using a semiconductor switch such as a thyristor, thereby changing the voltage. In this method, the load current flowing through the illuminator contains many harmonic components, and this harmonic current causes problems such as abnormal noise, vibration, overheating, damage, and shortened life of the illuminator. Furthermore, the harmonic current causes distortion in the received power supply voltage waveform, causing a great deal of trouble to peripheral information devices such as computers, measurement control devices, and the like. The thyristor is fired in synchronization with the voltage in each cycle, but since the synchronization signal for firing the thyristor is derived from the power supply voltage, the synchronization signal may fluctuate due to this waveform distortion. Ta. As a result, control of the lighting becomes unstable or uncontrollable in some cases, resulting in safety and reliability problems. To solve this problem, it has been proposed to install a harmonic filter, but this device requires a large number of large-capacity capacitors and reactors, which inevitably increases the size of the lighting control device and increases manufacturing costs. It was getting extremely high.

Furthermore, with conventional lighting control devices, once the illuminance is manually set, power is supplied to the illuminator to maintain the set illuminance even when no one is in the lighting zone, which wastes energy. . Also, station platforms, factories, schools,
In hospitals, airports, etc., even if a lighting zone is brightly illuminated by sunlight and there is no harm in lowering the illuminance of the illuminator in that lighting zone, the illuminance of the illuminator is maintained at a high level. Energy consumption was high.

[Purpose of the invention]

SUMMARY OF THE INVENTION An object of the present invention is to provide a lighting control device that is small and lightweight and has a high power saving effect.

Another object of the present invention is to provide a power-saving lighting control device that does not generate noise or distortion to a sinusoidal AC waveform.

Another object of the present invention is to provide a power-saving lighting control device that allows precise control of lighting.

Another object of the present invention is to provide a power-saving lighting control device that is inexpensive, stable, and reliable.

[Structure of the invention]

The power-saving lighting control device of the present invention is arranged between an input end connected to an AC power source and an output end connected to a lighting load, and includes an output winding that supplies an output voltage to the lighting load, and an output winding that supplies an output voltage to the lighting load. a magnetically controlled voltage regulator including a control winding that adjusts the output voltage by controlling magnetic flux interlinking with a wire; a DC excitation power source that supplies a DC excitation current to the control winding; and the control winding. and a semiconductor switch circuit connected between the DC excitation power source and the DC excitation current supplied to the control winding; and a semiconductor switch circuit that controls the conduction rate of the semiconductor switch circuit to adjust the DC excitation current. and a control circuit that controls the illuminance of the lighting load.

〔Example〕

Hereinafter, the present invention will be explained in detail with reference to the drawings.

In FIG. 1, a power saving lighting control device 10 according to a preferred embodiment of the present invention has input terminals 14, 16 connected to an AC power source 12, and an output terminal 20 connected to a lighting load 18 such as an incandescent lamp or a discharge lamp. ,22
and a magnetically controlled voltage regulator 2 comprising a control winding 26 that adjusts the output voltage supplied to the lighting load 18.
4, a DC excitation power supply 28 that supplies a DC excitation current to the control winding 26, and a DC excitation power supply 28 that is connected between the control winding 26 and the DC excitation power supply 28 to vary the DC excitation current supplied to the control winding 26. Semiconductor switch circuit 3
0, and a control circuit 34 that controls the illuminance of the lighting load 18 by controlling the conduction rate of the semiconductor switch circuit 30 and adjusting the output voltage.

In Figs. 1 to 5, a magnetically controlled voltage regulator 2
4 is a first saturable iron core 4 constituting the main magnetic flux loop path
2 and a magnetic shunt core 44 for bypassing a part of the main magnetic flux loop path, and the first saturable core 42 is made of a wound core. The first saturable core 42 includes an output winding consisting of a first series winding 46 , a shunt winding 48 , and a second series winding 50 . Shunt winding 48
The turns ratio of the first series winding 46 is selected such that the output voltage increases preferably by 1 to 2% with respect to the input voltage, and the winding ratio of the second series winding 50 is set such that the output voltage increases by 1 to 2% relative to the input voltage. determined accordingly. That is,
When it is desired to control the output voltage within a range of 100 to 50%, for example, the number of turns N of the second series winding is determined as follows: total number of turns of the first series winding and shunt winding x 50%. The first series winding 46 is connected between the high voltage terminal connected to the output end 20 and the medium voltage terminal connected to the input end 14, and the shunt winding 48 is connected to the first series winding 46.
connected in series with the same polarity. The lower end of the shunt winding 48 is connected to a neutral point connected to the input end 16. The second series winding 50 is connected between the lower end of the shunt winding 48 and the output end 22 with opposite polarity to the first series winding 46 . By changing the magnetic saturation state of at least a portion of the main magnetic flux loop path, the magnetic shunt core 44
The second
Saturable core 52 is controlled by control winding 26 as described below.

In FIGS. 2 and 3, the first saturable core 42 includes a center leg 54 and outer legs 56, 58 that constitute a main magnetic flux loop path. The center leg 54 includes a first core portion 54a and a second core portion 54b separated by the magnetic shunt core 44. Furthermore, center legs 54 are outer
An extension portion extending outward from the legs 56, 58, that is, a third core portion 54c is provided. The center leg 54 is disposed above the first saturable core 42, and
They are fixed to each other and integrated with fixtures 60 and 62. As is clear from FIGS. 2, 3, and 5, the magnetic shunt core 44 is composed of a C-shaped cross-section core made by laminating a large number of silicon steel plates. Groove 4 of magnetic shunt core 44
4a is arranged to be magnetically coupled to the center leg 54. End 4 of magnetic shunt core 44
4b and 44c are interlayers having a required thickness corresponding to a constant air gap between the first coil block of the first series winding 46 and the shunt winding 48 and the second coil block of the second series winding 50. The outer legs 56 of the first saturable iron core 42 sandwich the legs 64 and 66,
58 and secured to the outer legs 56, 58 by fixtures 68, 70, each core is integrated. A magnetic shunt core 64 shunts a portion of the magnetic flux in the main flux loop path through a high reluctance gap (formed by inserts 64 and 66) to outer legs 56 and 58 to provide an output voltage. It also functions to attenuate harmonics and reduce waveform distortion of the output voltage.
The second saturable core 52 is located below the magnetic shunt core 54, i.e. between the first coil block of the first series winding 46 and the shunt winding 48 and the second series winding 5.
0 and the upper part of the second core part 54b of the center leg 54 and the third core part 5.
4c, the fixtures 72,7
4, each core is integrated and magnetically coupled. In this way, the second saturable core 52 is arranged so as to overlap the lower half of the first saturable core 42, and magnetically saturates a portion of the first saturable core to increase the magnetic flux of the second series winding 50. is the first series winding 46
The first series winding 46 and the shunt winding 48 have no effect on the magnetic flux of the shunt winding 48, and the magnetic flux of the first series winding 46 and the shunt winding 48 is shifted to the magnetic shunt core 44. A first series winding 46 and a shunt winding 48, a second
The series winding 50 and the control winding 26 are connected to the first to third core portions 54a of the center leg 54, respectively.
It is wound on 54b and 54c and arranged in substantially the same plane. Furthermore, the top and bottom surfaces of each winding are
They are arranged so as to be aligned with the upper surface of the saturable iron core 52 and the lower surface of the first saturable iron core 42, respectively. That is, a coil block consisting of the first series winding 46 and the shunt winding 48, a second coil block consisting of the second series winding 50, and a third coil block of the control winding 26.
The block is located approximately within the thickness of the center leg 54 and the first and second saturable cores 42,52.
The third core portion 54c of the center leg 54 is
Extending outside the saturable core 42, the control winding 2
6 is wound onto the lower end 54c of the center leg 54. A second saturable core 52 surrounds the second coil block of the second series winding 50 and the third coil block of the control winding 26. In FIGS. 2 and 3, the upper and lower parts of the second saturable core 52 are connected to the center leg 54 by fixing devices 72 and 74, respectively.
together with the control winding 2 to form an auxiliary magnetic flux loop path.
When a DC excitation current is supplied to control winding 2
It functions as a path for the magnetic flux of 6. That is, the magnetic flux of the control winding 26 partially magnetically saturates the second core portion 54b of the center leg 54, and
The magnetic flux of series winding 46 and shunt winding 48 is shifted from the main flux loop through magnetic branch core 44 to outer legs 56,58.

The first series winding 46 and the shunt winding 48 are connected to the center
The leg 54 is wound on the first core part 54a to form an autotransformer, and the second series winding 50 is wound on the second core part 54b with the opposite polarity to the first series winding 46, So-called differential coupling.

In the above configuration, when the input ends 14 and 16 are connected to the AC power supply 12 and the output ends 20 and 22 are connected to the lighting load 18, the first and second series windings 4
A large current flows through the shunt windings 6 and 50, and a difference current between the input current and the output current flows through the shunt winding 48.

In FIGS. 1 and 2, when no DC excitation current is supplied to the control winding 26, the first series winding 46, the shunt winding 48, and the second series winding differentially coupled to the shunt winding 48 The magnetic flux generated by the wire 50 is transferred from the center leg 54 to the outer legs 56,5.
8 and circulates to the center leg 54. At this time, the first series winding 46 and the shunt winding 48
Since the magnetic flux generated by the second series winding 50 and the magnetic flux generated by the second series winding 50 are in opposite directions, the mutual magnetic flux as a whole acts as a difference. Therefore, the output voltage at this time is the minimum.

Next, when a DC excitation current is supplied to the control winding 26, the second saturable iron core 52 is magnetically saturated together with the second and third core portions 54b and 54c of the center leg 54, so that the first series winding The magnetic flux produced by wire 46 and shunt winding 48 is shifted to magnetic shunt core 44. At this time, the magnetic flux is transmitted to the first core portion 54a, the outer legs 56, 58, and the magnetic shunt core 4.
4, and the output voltage at the output terminals 20, 22 becomes maximum. When the DC excitation current supplied to the control winding 26 is reduced, the output voltage at the output end of the output winding is reduced accordingly. In this way, the second and third core portions 54b and 54 of the center leg 54
By variably controlling the magnetic saturation state of the magnetic shunt core 44, the differential coupling state of the second series winding 50 to the output winding consisting of the first series winding 46 and the shunt winding 48 is changed. By controlling the magnetic fluxes of the first series winding 46 and the shunt winding 48, which are shifted to , the output voltage at the output terminal can be variably controlled.

Returning to FIG. 1, the DC excitation power supply 28 is connected to a transformer 80 connected to the input side of the magnetically controlled voltage regulator 24 and to the output side of the transformer 80 to convert AC current into DC output current. Equipped with a rectifier 82,
This DC output current is smoothed by a capacitor 84 and used as a DC excitation current I for the control winding 26.

The semiconductor switch circuit 30 is a semiconductor switch 88
and a drive transistor 89, and this semiconductor switch 88 is connected between the DC output terminals of the rectifier 82 to control the DC excitation current I.
As the semiconductor switch 88, a transistor or a thyristor can be used.

In FIG. 1, semiconductor switch 88 includes first and second switches forming an inverted Darlington circuit.
control transistors 88a and 88b.
Here, what is an inverted Darlington circuit?
A circuit in which a PNP type transistor and an NPN type transistor are connected in a complementary manner. That is, in order to control the base current of the first control transistor 88a, the second control transistor 88b is connected in an inverted Darlington manner to form an inverted Darlington circuit. The collector of the drive transistor 89 is connected to the collector side of the first transistor 88a via resistors R1 and R2. The base of the second transistor 88b is connected to the junction of resistors R1 and R2. The emitter of the transistor 89 is connected to zero potential via the resistor R3, and the base of the transistor 89 is connected to the control circuit 34.
Driven by. A current absorption circuit 90 is connected in parallel to the control winding 26 to which the DC excitation current I is supplied. A capacitor is used as the current absorption circuit 90. This current absorption circuit 90 functions to absorb the difference current between the DC output current of the rectifier 82 and the DC excitation current when the semiconductor switch 88 is off. Voltage limiting element 92 in parallel with current absorption circuit 88
is connected. This voltage control element 92 becomes conductive when the excitation voltage reaches the voltage limited by the voltage limiting element 92, and is provided to prevent overvoltage from being applied to the semiconductor switch 88 and the current absorption circuit 90. An embodiment in which a constant voltage diode is used as the voltage control element 92 is shown in FIG. In FIG. 1, a backflow prevention diode 94 is inserted between a capacitor serving as a current absorption circuit 90 and a semiconductor switch 88. The diode 94 allows the discharge current from the capacitor 90 to flow through the semiconductor switch 88 when the semiconductor switch 88 is turned on.
to prevent it from flowing through. This prevents the risk of destruction of elements such as the illustrated transistor used as the semiconductor switch 88.

In FIG. 6, the control circuit 34 includes a keyboard switch 10 for inputting a plurality of dimming patterns.
0, a programming device 102 for storing the dimming pattern input by the keyboard switch 100, and an F/V converting the output of the programming device 102 into frequency/voltage to obtain a first illuminance setting signal.
a first illuminance setting device 106 consisting of a converter 104;
and a second illuminance setting device 108 that is manually adjusted and supplies a second illuminance setting signal. In this embodiment, the level of the illuminance setting signal of the second illuminance setting device 108 is adjusted to be set to a lower illuminance than the illuminance according to the dimming pattern input from the first illuminance setting device 106. The first and second illuminance setting devices 106 and 108 are connected to the first and second terminals 110a and 11 of the illuminance changeover switch 110, respectively.
0b, and the illuminance selector switch 110
A third terminal 110c of the comparator 112 is connected to the positive input terminal of the comparator 112. The illuminance changeover switch 110 is controlled by a human body sensor 114 placed in the lighting zone of the lighting load 18. The human body sensor may be a known infrared sensor or ultrasonic sensor. That is, when there is a person in the lighting zone, the illuminance changeover switch 110 is held at the position where the first and third terminals 110a and 110c are connected by the contact 110d, but when there is no person in the lighting zone, the human body sensor 114 is held. The contact 110d is operated to switch from the first terminal 110a to the second terminal 110b. Comparator 1
The negative input terminal of 12 is connected to the reference power source REF, and the first or second illuminance setting device 106,1
The illuminance setting signal from 08 is compared with the reference power supply,
The comparison signal C1 corresponding to the difference signal is sent to the comparator 11.
Supplied to the negative input terminal of 4. The comparator 114 compares the comparison signal C1 with the triangular wave signal S1 supplied from the triangular wave generator 116 at its positive input terminal, and drives an output signal P1 with a pulse width proportional to the difference through the output terminal 128. transistor 8
Supply to the base of 9.

The control circuit 34 further includes a light intensity sensor 118 that is disposed in the lighting zone and generates a voltage signal according to the external light in this lighting zone, and a reference illuminance setting device 12 that sets a reference voltage level corresponding to the reference illuminance.
0, and a comparator 122 that outputs a difference signal C2 between the output signal of the light intensity sensor 118 and the reference voltage of the reference illuminance setting device 120. The difference signal C2 is sent to the comparator 12
On the other hand, the triangular wave signal S2 of the triangular wave generator 126 is connected to the positive input terminal of the comparator 124. The comparator 124 compares the difference signal C2 and the triangular wave signal S2, generates an output signal P2 with a pulse width proportional to the difference, and supplies it from an output terminal 128 to the base of the drive transistor 89.

In FIG. 7, the program device 102 includes a power supply section 130, a reference signal generation circuit 132, and a CPU 13 operated by a keyboard switch 100.
4. The keyboard switch 100 can set and delete a time schedule, or recall a stored time schedule. When a dimming pattern as shown in FIG. 8 is set according to the day of the week or time using the keyboard switch 100, the dimming pattern is stored in the dimming pattern memory 138 via the program memory 136. On the other hand, the built-in clock function advances the time, and searches the dimming pattern memory 138 every minute to see if any action is set at that time according to a predetermined program.
At the set time, a signal corresponding to the operation is outputted through the interface circuit 146.
The output is converted from a frequency signal to a voltage signal by an F/V conversion circuit 104, and is then sent to a comparator 11 as described above.
4, an output signal P1 is generated, and the illuminance pattern shown in FIG. 8 is obtained depending on the time. The display drive unit 142 drives the display unit 144 and
normally displays the time, but is configured to display each status when setting is made using the keyboard switch 100. A battery backup 140 backs up the dimming pattern memory 138 during a power outage.

Next, the operation of the power-saving lighting control device of FIG. 1 will be explained with reference to the voltage and current waveform diagram of FIG. 9.

The circuit constants are selected such that the DC output current I of the rectifier 84 is in any case greater than the required value of the excitation current I' of the control winding 26. When the semiconductor switch 88 is on, the DC output current I of the rectifier 84 is shunted by the semiconductor switch 88, and the exciting current I' decreases. Next, when the semiconductor switch 88 is turned off, the rectifier output current I flows into the control winding 26 in an increasing manner. Due to the inductance of the control winding 26, the excitation current
Since I' can only increase gradually, the difference current I-
I' flows into current absorbing capacitor 90. In this way, the excitation current I' is instantaneously controlled by the base signal of the semiconductor switch 88 so as to be maintained at the target value.

The conduction rate α of the semiconductor switch 88 at a certain moment can be expressed as α=Ton/T, where Ton is the on time and T is the period, and the average value I′av of the exciting current I′ is:
If the average value Iav of the rectifier output I is taken, the relationship is I'av=α·Iav. That is, when viewed as an average value, of the rectifier output current I, only αIav flows for excitation, and the remaining (1-α) flows to the semiconductor switch 88.
You can see that Iav is branching off. In this way, the semiconductor switch 88 is connected to the output terminal 12 of the control circuit 34.
The drive transistor 89 is turned on and off in response to an output signal appearing at 8 to control the DC excitation current I' supplied to the control winding 26. At this time, as the pulse width of the output signal from the output terminal 128 becomes narrower, the conduction rate of the semiconductor switch 88 becomes smaller and the diversion ratio of the excitation current becomes smaller. Therefore, the control current I' supplied to the control winding 26 increases, and the center current I' of the magnetically controlled voltage regulator 24 increases.
The degree of magnetic saturation of the second core portion 54b of the leg 54 increases. At this time, the amount of magnetic flux of the first series winding 46 and shunt winding 48 in FIG. As a result, the illuminance of the lighting load 18 increases. Next, as the pulse width of the output signal from the output terminal 128 increases, the conduction rate of the semiconductor switch 88 increases, the excitation current I' decreases, and the degree of magnetic saturation of the center leg 54b decreases. At this time, the amount of action of the magnetic flux of opposite polarity by the second series winding 50 on the magnetic flux of the first series winding 46 and the shunt winding 48 increases, and the output voltage of the voltage regulator 24 decreases, resulting in a decrease in illuminance. do. In this way, the control circuit 34 controls the semiconductor switch 88 via the output signal of the output terminal 128.
The excitation current I' is controlled by controlling the conduction rate of , and the output voltage supplied from the voltage regulator 24 to the lighting load 18 is varied to automatically control the illuminance of the lighting load 18.

As shown in FIG. 8, the program device 102 of the control circuit 34 sets the illuminance to 50% from 8 a.m. to 10 a.m., 95% from 10 a.m. to 12 noon, and 100% illuminance from 12 to 15 p.m.
A dimming pattern that obtains an illuminance pattern A consisting of 95% illumination from 15:00 to 19:00 and 50% illuminance from 19:00 to 20:00 is stored.On the other hand, the manual second illuminance setting device 108 adjusts the illuminance. A dial (not shown) is set so that illuminance pattern B having lower illuminance than pattern A in the high range can be obtained. In this state, when there is a person in the lighting zone, the contact 110d of the changeover switch 110 is held at the position connecting the first and third terminals 110a and 110c, as shown in FIG. At this time,
A first illuminance setting signal corresponding to the dimming pattern stored in the programming device 102 is transmitted to the F/V converter 104.
Output via . This output is compared with the reference voltage REF in the comparator 112, and the difference signal C1 is compared with the triangular wave signal S1 in the comparator 114, and the output signal P1 in FIG.
to the base of drive transistor 89. At this time, transistor 89 is turned on, and transistors 88a and 88b are turned on. As shown in FIG. 9, when the voltage level of the comparison signal C1 is high, the pulse width of the output signal P1 at the output terminal 128 of the control circuit 34 is small. The DC excitation current I' increases, the output voltage of the voltage regulator 24 increases, and the illuminance of the lighting load 18 increases. Next, in FIG. 9, the comparison signal C1' is changed to the comparison signal C1
As the voltage becomes lower, the pulse width of the output signal increases as shown in waveform P1', and the shunt ratio of the semiconductor switch 88 increases. At this time, the DC excitation current I' of the control winding 26 becomes smaller, the output voltage of the voltage regulator 24 drops, and the illuminance of the lighting load 18 decreases. In this way, the illuminance is adjusted according to the illuminance pattern A in FIG.
is obtained.

Now, when a person leaves the lighting zone, the contact 110d of the changeover switch 110 shown in FIG.
The second illuminance setting device 10 is switched to the terminal 110b.
8 is connected to comparator 112. The second illuminance setting device 108 supplies the comparator 112 with a second illuminance setting signal to obtain the illuminance pattern B having a lower illuminance than the high-frequency level of the illuminance pattern A, as described above. Therefore, since the output signal of the control circuit 34 has a wide pulse width as shown in waveform P1', the output signal of the semiconductor switch 8
8 increases, the output voltage of the lighting load 18 decreases, and the illuminance is adjusted to 80% as shown in FIG. The level of this illuminance pattern B depends on the user's required environment, for example,
You can adjust the brightness up to 50%.

Next, when the reference illuminance setter 120 is set to the maximum illuminance level of the illuminance pattern A in FIG. 8, when the external light incident on the illumination zone approaches the maximum illuminance level, the comparator in FIG. 122
Since the voltage level of the comparison signal C2 becomes smaller and the pulse width of the output signal P2 of the comparator 124 becomes larger, the voltage level of the comparison signal C2 of the semiconductor switch 88 of FIG.
As the diversion ratio increases, the input voltage of the lighting load 18 decreases, and the illuminance automatically decreases. In this way, regardless of the setting levels set by the first and second illuminance setting devices 106 and 108, if the luminous intensity due to natural light in the lighting zone increases, the voltage will automatically drop, thereby reducing wasted energy consumption. can be prevented and significant savings can be achieved.

In the above explanation, the DC excitation power source is transformer 8
Although it was explained as consisting of 0, transformer 80
may be connected to the secondary side of the voltage regulator 24. Alternatively, instead of a transformer, a current transformer and an AC reactor may be connected to the input or output side of the voltage regulator 24 to convert the load voltage component and load current component to the rectifier 82.
The vector combination may be used as the DC excitation current.

〔Effect of the invention〕

As is clear from the above, the power-saving lighting control device according to the present invention provides the following effects.

(1) The lighting control device of the present invention is capable of setting the first stage illuminance and the second stage illuminance, and automatically switches the illuminance depending on whether there are people in the lighting zone or not. Therefore, the energy saving effect is high. Moreover, when the luminous intensity of the lighting zone becomes brighter due to natural light, the voltage of the illuminator is automatically lowered to lower the illuminance, thereby preventing wasteful energy consumption. Therefore,
If this device is installed in factories, schools, hospitals, stations, airports, etc., significant energy savings can be achieved.

(2) Moreover, by adopting a voltage regulator having an autotransformer structure, the entire device can be significantly reduced in size, weight, and cost.

(3) Since the output voltage can be adjusted using an autotransformer with a small self-capacity to control the illuminance of a large load capacity, it is possible to control the illuminance with a low voltage and low power excitation current, and the configuration of the control circuit is extremely simple. This makes it possible to significantly reduce the price and size.

(4) Since the excitation current of the control winding of the voltage regulator is controlled by a low-voltage, small-capacity semiconductor switch, stable illuminance control can be achieved using safe, highly reliable, and extremely inexpensive electronic components. Therefore, it has a great practical effect.

(5) Since the lighting control device of the present invention does not use an AC voltage phase control method, it does not cause distortion in the voltage waveform or generate noise, so it does not cause any disturbance to surrounding computer equipment or measurement control devices.

(6) By making it possible to use a voltage regulator with a small self-capacity and a control circuit with low power consumption for a large load capacity, energy loss is minimized, making it possible to significantly improve the efficiency and save energy of lighting control equipment.

[Brief explanation of drawings]

FIG. 1 is a wiring diagram of a preferred embodiment of the power-saving lighting control device of the present invention, FIG. 2 is a plan view showing an example of the magnetically controlled voltage regulator shown in FIG. 1, and FIG. Figure 4 is a side view of the voltage regulator, Figure 4 is a bottom view of the voltage regulator in Figure 2, Figure 5 is a sectional view taken along the line V-V in Figure 2, and Figure 6 is a specific example of the control circuit in Figure 1. For example, Fig. 7 is a block diagram of the programming device shown in Fig. 6, Fig. 8 is a graph showing the illuminance pattern of the lighting control device shown in Fig. 1, and Fig. 9 is the voltage of various signals of the lighting control device shown in Fig. 1. The current waveform diagrams are shown respectively. 24... Voltage regulator, 28... DC excitation power supply,
34...Semiconductor switch circuit, 88...Control circuit, 106...First illuminance setting device, 108...Second
Illuminance setting device, 114... Human body sensor, 118...
Light intensity sensor, 120...Reference illuminance setting device.

Claims (1)

[Claims] 1 (a) An output winding disposed between an input end connected to an AC power source and an output end connected to a lighting load, and supplying an output voltage to the lighting load, (b) a magnetically controlled voltage regulator including a control winding that adjusts the output voltage by controlling magnetic flux interlinking with the winding; (b) a DC excitation power source that supplies a DC excitation current to the control winding; (c) a semiconductor switch circuit connected between the control winding and the DC excitation power source and controlling the DC excitation current supplied to the control winding; (d) conduction rate of the semiconductor switch circuit; A power-saving lighting control device comprising: a control circuit that controls the DC excitation current to control the illuminance of the lighting load; 2. The power-saving lighting control device according to claim 1, wherein the DC excitation power source includes a transformer connected to the input end and a rectifier connected to the transformer. 3. Claim 1 or 2, characterized in that the semiconductor switch circuit is connected to a DC output terminal of the DC excitation power supply, and a part of the DC excitation current is shunted to the semiconductor switch circuit.
The power-saving lighting control device described in Section 1. 4. The power-saving lighting control device according to claim 3, characterized in that a current absorption circuit is connected in parallel to the semiconductor switch circuit. 5. The power-saving lighting control device according to claim 4, wherein a voltage limiting element is connected in parallel to the semiconductor switch circuit. 6. The power-saving lighting control device according to claim 1 or 2, wherein the semiconductor switch circuit includes a drive transistor. 7. An illuminance setting device in which the control circuit generates an illuminance setting signal for setting the illuminance of the lighting load;
3. The power-saving lighting control device according to claim 1, further comprising an output signal generation circuit that generates an output signal having a pulse width responsive to the illuminance setting signal. 8. The power-saving lighting control device according to claim 7, wherein the illuminance setting device is a manual illuminance setting device. 9 A first illuminance setting device for the control circuit to set the first illuminance, a second illuminance setting device for setting the second illuminance, and illuminance settings from the first and second illuminance setting devices. an output signal generation circuit that generates an output signal with a pulse width in response to a signal; and an output signal generation circuit that is connected between the first and second illuminance setting devices and the output signal generation circuit to control the first and second illuminance setting devices. 3. The power-saving lighting control device according to claim 1, further comprising an illuminance changeover switch for switching the illuminance. 10 The first illuminance setting device is connected to a keyboard switch, a programming device that stores the dimming pattern input by the keyboard switch, and an output side of the programming device and an input side of the illuminance changeover switch. 10. The power-saving lighting control device according to claim 9, further comprising an output conversion device. 11. Claim 9 or 10, characterized in that the control circuit includes a human body sensor disposed in a lighting zone of the lighting load, and the illuminance changeover switch is switched and controlled by the output of the human body sensor. The power-saving lighting control device described in Section 1. 12 a light intensity sensor, the control circuit being disposed in a lighting zone of the lighting load to detect external light in the lighting zone and generate an output proportional to the external light;
a reference illuminance setting device that sets a reference voltage level corresponding to a reference illuminance; and a comparison signal generation circuit that compares outputs of the light intensity sensor and the reference illuminance setting device and generates a comparison signal corresponding to a difference signal. 3. The power-saving lighting control device according to claim 1, further comprising: an output signal generation circuit that generates an output signal having a pulse width proportional to the comparison signal.