JPH0846533A - Interference compensation method - Google Patents

Abstract

(57) [Abstract] [Purpose] It is an object of the present invention to provide an interference compensation method that can reduce interference in the same channel caused by the influence of fading and the like, and can obtain high transmission quality and high frequency utilization efficiency. [Configuration] Two or more signals to which different training signals are added are simultaneously transmitted and received. On the receiving side, a tap coefficient indicating the degree of interference is calculated from the interference signal mixed in the received training signal, and the interference signal is removed from the received data signal based on this tap coefficient.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an interference compensation method suitable for use in communications requiring high transmission quality and high frequency utilization efficiency even in a fading environment.

[0002]

2. Description of the Related Art As one of communication methods that are not easily affected by interference and interference and can obtain high transmission quality, a method of simultaneously using two radio waves whose polarization planes are orthogonal (hereinafter referred to as orthogonal polarization communication Method). This orthogonal polarization communication method is as follows. There is no correlation between two radio signals whose polarization planes are orthogonal to each other. Therefore,
Two antennas having polarizations orthogonal to each other are combined, and the same signal is transmitted by each of the antennas. On the other hand, the reception side uses an antenna having a polarization plane corresponding to that of the transmission side antenna, and the signals transmitted by both polarizations are combined to cancel interference and interference. By the way, a radio wave having a single plane of polarization is inclined in its plane of polarization due to reflection or refraction. For this reason, even if the radio wave is transmitted by orthogonal polarization, the planes of polarization will not be orthogonal at the receiving point. Therefore, when the orthogonal polarization communication method as described above is used in a communication path in which selective fading is present due to the influence of reflection or refraction, the reception side causes interference with each other in the signals of the respective polarization planes, and A compensation method is needed.

FIG. 11 is a block diagram showing the structure of a receiving apparatus using a conventional interference compensation method. On the other hand, in FIG.
FIG. 12 is a block diagram showing a configuration of a compensation circuit 3 in FIG. 11.
In these figures, as an example, UHF (Ultra High Frequency)
An apparatus for handling digital data communication such as TDMA (Time Division Multiple Access) packet communication in the band or the microwave band will be shown and described. In addition, in the receiving devices shown in these figures, it is assumed that there is no influence of delayed waves propagating in space. One unit of data handled by the above-described receiving device is configured as shown in FIG. 13 as an example, but the first half (left side in the figure) of one unit is a training signal assigned to each communication line. , The latter half (right side in the figure) is a data signal. In the orthogonal polarization communication method, the data signal is the same for each of the two carriers whose polarization planes are orthogonal, but the training signal is composed of data having different data frequencies and data codes, for example.

The receiving apparatus shown in FIG. 11 is provided with one antenna 1d for receiving a desired wave and one antenna 1u for receiving an interference wave. These antennas 1d and 1u are antennas each having a single polarization plane, and it is assumed that simultaneous transmission / reception is currently performed using both vertical polarization and horizontal polarization. Further, the antenna 1d is an antenna for vertical polarization reception, and the antenna 1u is an antenna for horizontal polarization reception. Detector 2
The radio waves received by the antennas 1d and 1u are input to d and 2u, respectively, and are detected based on a modulation method suitable for the received radio waves such as FSK (frequency shift keying) and PSK (phase shift keying). The reception signal R ₁ which is a desired wave signal and the reception signal R ₂ which is an interference wave signal output from the detectors 2 d and 2 u are simultaneously input to the compensation circuit 3.

The compensating circuit 3 is a circuit for removing the interference wave signal component from the desired wave signal as follows (see FIG. 12). Received signal R _1, when the switch 6a is T side allocated to the subtracter 7a side, when the D side distributes the received signals R ₁ to the subtracter 7b. The output P of the subtractor 7a
₁ is input to the subtractor 7c and the control circuit 10. The training signal generator 8 produces D _T 'which is the same signal as the training signal to be put on the desired wave, and outputs the signal processing circuit 9a.
To the subtractor 7a via. The received signal R ₂ passes through the signal processing circuit 9b, and when the switch 6b is on the T side, the subtractor 7
c, and when it is on the D side, it is distributed to the subtractor 7b. The output E ₀ of the subtractor 7c is input to the control circuit 10. Here, the signal processing circuits 9a and 9b, as an example, quantize and code the input signal, store the signal in an internal storage unit, and re-signal it under the control of the control circuit 10 and output it. That is, the signal processing circuits 9a and 9b change the amplitude and phase of the input signal under the control of the control circuit 10 and output the signal. In the compensation circuit 3, the control information output from the control circuit 10 to the signal processing circuits 9a and 9b is represented by h _d and h, respectively.

In the compensation circuit 3, the received signals R ₁ and R ₂ are in the training signal section (hereinafter referred to as the T side time, see FIG. 13).
If so, both switches 6a and 6b are set to the T side. At this time, the received signal R ₁ and the training signal D _T ′ are input to the subtractor 7a via the signal processing circuit 9a. The received signal R ₁ is a mixture of the desired training signal D _T and the interference training signal u _T. on the other hand,
The output signal P ₁ of the subtracter 7a _{is, P 1 = R 1 -h d} · D T becomes a _{'= D T + u T -h} d · D T', the control circuit 10, D = h _d · D _T Then, h _d is obtained by the method of least squares so that In this way, assuming that the influence of noise can be ignored, the interference training signal component u _T is obtained for the signal P ₁ .

The output signal P ₁ of the subtractor 7a and the received signal R ₂ are input to the subtractor 7c via the signal processing circuit 9b. The received signal R ₂ is the interference training signal U _T
And the desired training signal d _T are mixed. On the other hand, the output signal E ₀ of the subtractor. _{7c, E 0 = P 1 -h ·} R 2 = u T -h · (U T + d T) and becomes the control circuit 10, u _T = h · U _T Then, h is calculated by the method of least squares so that

As described above, at the T side (see FIG. 13), h
After convergence, switches 6a and 6b are both set to the D side,
As a result, the reception signal R ₁ and the reception signal R ₂ are input to the subtractor 7b via the signal control circuit 9b. The reception signal R ₁ is a mixture of the desired data signal D and the interference data signal u, and the reception signal R ₂ is a mixture of the interference data signal U and the desired data signal d. The output signal C ₀ of the subtractor 7b is as follows. C ₀ = R ₁ −R ₂ = D + u−h (U + d) By the way, since u _T = h · U _T as described above,
Since u = h · U, C ₀ = D + u−h (U + d) = D + u−u−h · d = D−
h · d. Since D >> d and h << 1, h · d becomes a negligible value and C ₀ ≈D, and the interference signal can be removed from the received signal. The control circuit 10 obtains h and h _d by iterative calculation using a least squares method such as an RLS (recursive least squares mean) algorithm. C ₀ obtained in this way is
The discriminator 4 and the demodulator 5 convert the continuous digital data, an analog signal obtained by demodulating the continuous digital data, and the like to output.

[0009]

The method of canceling interference and interference by combining received signals of vertically polarized waves and horizontally polarized waves, as in the above-mentioned prior art, is very useful in a static channel environment. It is valid. However, the compensation effect is reduced in a transmission line in which a dynamic instantaneous change exists, such as an urban propagation line. This is because the plane of polarization rotates when the radio wave is reflected by a structure or the like. Therefore, the single polarization receiving antenna cannot suppress the different polarization very much. Therefore, the vertically polarized waves and the horizontally polarized waves interfere with each other and the transmission quality deteriorates. Further, in the urban propagation path, the average period D / U (desired wave to interference wave protection ratio) fluctuates greatly because fading in a short cycle is large, and it becomes difficult to secure stable quality. Further, in the conventional interference compensation method, only one desired signal can be compensated for one device. Therefore, in the communication method in which two signals are required to be compensated, the number of devices corresponding to the number of compensation signals is required and the configuration becomes complicated. The present invention has been made under such a background, and provides an interference compensation method capable of reducing the interference in the same channel caused by the influence of fading or the like, and obtaining high transmission quality and high frequency utilization efficiency. It is an object.

[0010]

In order to solve the above-mentioned problems, in the invention described in claim 1, a training signal part which is a unique sequence predetermined in each transmitting device and transmission A desired signal 1 and a desired signal 2 which are time-divisionally configured by a data signal part to be received, and a reception signal 1 in which an interference signal 1 that interferes with the desired signal 1 to be received is mixed; In the receiving device which inputs the reception signal 2 in which the interference signal 2 which gives interference to the desired signal 2 is mixed, the desired signal 1 and the desired signal 2 being received are the training signal portions, respectively. In this case, a training signal generating means 1 for generating a training signal corresponding to the desired signal 1 and a training signal corresponding to the desired signal 2 are generated. To training signal generating means 2
, Control means 1 and control means 2 for controlling the amplitude and phase of the output of the training signal generating means 1, and control means 3 and control means 4 for controlling the amplitude and phase of the output of the training signal generating means 2. And subtraction means 1 for subtracting the output of the control means 1 from the received signal 1.
A subtraction means 2 for subtracting the output of the control means 3 from the output of the subtraction means 1, a subtraction means 3 for subtracting the output of the control means 2 from the received signal 2, and a control means from the output of the subtraction means 3. And the subtraction means 4 for reducing the output of 4 and the control value in the control means 1 is a 1-row, 1-column component, the control value in the control means 2 is a 2-row, 1-column component, and the control value in the control means 3 is 1-row. Inverse matrix calculation means for calculating a matrix h which is an inverse matrix of a matrix H of a 2-row 2-column matrix having 2-row components and control values in the control means 4 being 2-row 2-column components. , The respective control means 1 to 4 are controlled so that the square values of the outputs of the subtraction means 2 and the subtraction means 4 are minimized to obtain the matrix h, and the desired signal being received. 1 and the desired signal 2 In the case of each data signal part, the product of the 1st row and 1st column component of the matrix h and the received signal 1 and the product of the 1st row and 2nd column component of the matrix h and the received signal 2 are added. The addition means 1 and the addition means 2 for adding the product of the 2 × 1 column component of the matrix h and the received signal 1 and the product of the 2 × 2 column component of the matrix h and the received signal 2 It is characterized in that the desired signal 1 and the desired signal 2 are outputted by the combining means.

Further, in the invention according to claim 2,
A receiver of a wireless communication line composed of a single or a plurality of transmitters and a receiver for receiving the signal of the transmitter, wherein a desired signal and an interference signal to be transmitted and received are predetermined for each transmitter. And a desired signal to be received and N- which gives interference to the desired signal, which is composed of a training signal part, which is a unique sequence, and a data signal part to be partially transmitted in a time division manner.
In a receiving apparatus for inputting an integer N number of received signals 1 to received signal N, in which one type of the interference signal is mixed, the desired signal and the interference signal being received are each the training signal portion. In addition, the training signals corresponding to the desired signal or the interference signal are generated, and the M training signal generating units 1 to M, which are the same number as the N, and the received signals 1 to For each of the received signals up to N,
Phase control means 1 to phase control means M for controlling the amplitude and phase of outputs from the training signal generation means 1 to training signal generation means M, and the received signal N.
To subtracting means 1 to subtracting means M for respectively reducing the outputs to the training signal generating means 1 to training signal generating means M via the phase controlling means 1 to phase controlling means M, and the received signals 1 to The inverse matrix M of the matrix H in which the control amounts of the control means 1 to the control means M for the reception signals N are N rows and M columns.
In a coefficient calculation means having an inverse matrix calculation means for calculating a matrix h of N rows and N, the square value of the output of the subtraction means M is minimized for each of the received signals 1 to N. When each of the control means 1 to the control means M is controlled to obtain the matrix h, and the desired signal and the interference signal being received are data signal portions, respectively,
Reception signal control means 1-reception signal control means M that configures M rows and N columns and controls the amplitude and phase of the reception signals N for each of the reception signals 1-N and outputs them respectively.
And an adding means 1 to an adding means M for obtaining an integer M number of compensation outputs by adding outputs of all the received signal control means of the corresponding M rows, each element of the matrix h. Each of the corresponding reception signal control means is controlled by.

[0012]

According to the present invention, two or more signals to which different training signals are added are simultaneously transmitted and received. On the receiving side, a tap coefficient indicating the degree of interference is calculated from the interference signal mixed in the received training signal, and the interference signal is removed from the received data signal based on this tap coefficient.

[0013]

An embodiment of the present invention will be described below with reference to the drawings. FIG. 1 shows an example of the configuration of a communication line to which the present invention is applied. In the communication line in FIG. 1, the transmission device 59 has a vertically polarized antenna 61d and a horizontally polarized antenna 61u. On the other hand, the receiving device 60 has a vertically polarized antenna 1d and a horizontally polarized antenna 1u. In this communication line, two orthogonal polarization signals have different data signals (see FIG. 13).
However, when receiving the desired signal D of vertically polarized waves due to the effect of fading in an urban area or the like, the interference signal u is mixed in the electric signal received by the vertically polarized antenna 1d,
When the horizontally polarized wave desired signal U is received, the interference signal d is mixed with the signal received by the horizontally polarized antenna 1u.

FIG. 2 is a block diagram showing an example of the configuration of a receiving apparatus using the present invention. The communication handled by the receiving apparatus shown in FIG. 2 is also digital data communication such as TDMA packet communication in the UHF band or the microwave band as an example, and one unit of data to be handled is shown in FIG.
It is configured as shown in FIG. In addition, in FIG.
The parts corresponding to the parts in FIG. 11 are designated by the same reference numerals, and the description thereof will be omitted. In the receiving apparatus shown in FIG. 2, the compensation circuit 30 inputs the reception signal R ₁ and the reception signal R ₂ at the same time, and outputs the signals C ₁ and C ₂ .

FIG. 3 and FIG. 4 are diagrams showing an example of the configuration of the compensation circuit 30. First, when the switches 36a and 36b are on the T side, the following is performed. The received signal R ₁ is the subtractor 3
7a and the output of the subtractor 37a is the subtractor 3a.
7b is input. The output E ₁ of the subtractor 37b is
It is input to the control circuit 40. Received signal R ₂ is subtracted by subtractor 37
c, and the output of the subtractor 37c is the subtractor 37c.
It is input to d. The output E ₂ of the subtractor 37d is input to the control circuit 40. Training signal generator 38
a produces D _T 'which is the same signal as the training signal to be placed on the desired wave, and inputs it to the subtractor 37a via the signal processing circuit 39a and also inputs to the subtractor 37c via the signal processing circuit 39c. Training signal generator 38b
Creates U _T 'which is the same signal as the training signal to be placed on the interference wave, and the subtractor 3 is generated via the signal processing circuit 39b.
7b, and also to the subtractor 37d via the signal processing circuit 39d.

On the other hand, the above-mentioned switches 36a and 36b are set to D
If it is on the side, then: The received signal R ₁ is input to the signal processing circuit 31a and the signal processing circuit 31c, and the received signal R ₂ is input to the signal processing circuit 31b and the signal processing circuit 31d. The output of the signal processing circuit 31a and the output of the signal processing circuit 31b are input to the adder 34a, and the output of the signal processing circuit 31c and the output of the signal processing circuit 31d are input to the adder 34b. These adders 34
The output C _{1 of a} is input to the discriminator 4a (see FIG. 2), and the output C ₂ of the adder 34b is input to the discriminator 4b (see FIG. 2).

The signal processing circuits 31a to 31d and 39a to 39d, for example, quantize and encode the input signals, store them in an internal storage unit, and re-convert them into signals under the control of the control circuit 40 for output. Is. That is, the signal processing circuits 31a to 31d and 39a to 39d change the amplitude and phase of the input signal and output the signal under the control of the control circuit 40. In the compensation circuit 30, the control circuit 40 controls the signal processing circuits 31a, 31b, 31.
The control information to be output to c and 31d is H ₁₁ , H ₁₂ , and
The control circuit 40 indicates the signal processing circuit 39 by H ₂₁ and H _22.
It represents a, 39b, 39c, (later h _nn, referred to as tap coefficients) each _{h 11, h 12, h 21} , h 22 of the control information to be output to 39d and.

Next, a method of determining the control information H ₁₁ , H ₁₂ , H ₂₁ , and H ₂₂ output by the control circuit 40 will be described. 2 to 4, the radio waves received by the antennas 1d and 1u are detected by the detector 2d and the detector 2d, respectively.
Detected by 2u and become received signals R ₁ and R ₂ , respectively,
It is input to the compensation circuit 30. First, when the reception signals R ₁ and R ₂ are on the T side (see FIG. 13), the switch 36
Both a and 36b are on the T side. Here, the received signal R ₁ is
The desired training signal D _T and the interference training signal u _T are mixed, and the received signal R ₂ is the interference data signal U.
And the desired data signal d are mixed. At this time,
Output signal E ₁ of the subtractor 37b _{is, E 1 = R 1 -h 11} · D T '-h 12 · U T' = D T + u T -h 11 · D T '-h 12 · U T' Also, output E ₂ of the subtracter 37d is a _{E 2 = R 2 -h 21 ·} D T '-h 22 · U T' = d T + U T -h 21 · D T '-h 22 · U T' The control circuit 40 obtains each tap coefficient by the least square method such as the RLS algorithm so that E ₁ and E ₂ become 0.

After the end of the training signal section of the received signal, the control circuit 40 calculates H ₁₁ , H ₁₂ , H ₂₁ , and H ₂₂ , which are inverse matrices of the tap coefficient matrix composed of the tap coefficients,
The control information is for the synthesizing circuit 33 shown in FIGS. Therefore, the outputs C ₁ and C ₂ of the synthesis circuit 33 are as follows. C ₁ = H ₁₁ · R ₁ + H ₁₂ · R ₂ and C ₂ = H ₂₁ · R ₁ + H ₂₂ · R _{2 The} outputs C ₁ and C ₂ thus obtained are the discriminators 4a and 4b and the demodulator 5a, respectively. 5b, the continuous digital data, an analog signal obtained by demodulating the continuous digital data, and the like are output.

As an example of the evaluation of this example, the results shown in FIG. 5 were obtained. In FIG. 5, f _d (maximum Doppler frequency that causes fading) is 15 Hz, XPD
(Cross-chain polarization discrimination degree) is 5 dB, E _b / N ₀ (average signal energy E _b within 1 bit and noise power N ₀ per 1 Hz)
Ratio) is set to 40 dB, and BER (bit error ratio) with respect to D / U is evaluated. Here, 50 and 51 are evaluation examples when interference compensation is not performed, and
Is an evaluation example of an interference signal, and 51 is an evaluation example of a desired signal.
Reference numerals 52 and 53 are evaluation examples when the interference compensation method of the present invention is used, 52 is an evaluation example of an interference signal, and 53.
Is an example of evaluation of a desired signal. According to the evaluation example shown in this figure, the desired signal and the interference signal have characteristics such that they are folded back around 0 dB, but according to the present invention that simultaneously transmits and receives orthogonal polarized waves and compensates for interference, It turns out that BER can be improved considerably.

Furthermore, the BE of this embodiment and the prior art
A diagram comparing the R features is shown in FIG. F _d in this figure
Evaluation conditions such as are the same as the evaluation conditions of FIG. In FIG. 6, reference numeral 55 is an evaluation example when interference compensation is not applied,
Reference numeral 56 is an evaluation example by the conventional interference compensation method, and 57 is an evaluation example by the interference compensation method of the present invention. Comparing the evaluation examples of the conventional interference compensation method and the interference compensation method of the present invention, D / U
In the range of −5 to 10 dB, the interference compensation method of the present invention can reduce the BER as compared with the conventional technique.

The interference compensation method of the present invention can be applied to the following communication lines. A. Application Example 1 In the communication line shown in FIG. 7, D, which is a vertically polarized wave of frequency f, is assigned to the transmitting device 59 and the receiving device 60, and horizontally polarized wave of frequency f is assigned to the transmitting device 12 and the receiving device 14. By allocating a certain U, frequency and orthogonal polarization are spatially reused. Not only the desired signal D but also the interference signal u from the transmitter 12 is mixed in the vertically polarized antenna 1d provided in the receiver 60 now.
Receive interference. (In addition, in the horizontally polarized antenna 1u provided in the receiver 60, not only u, which is an interference signal,
The desired signal d from the transmitter 59 is also mixed. ) As described above, in a fading environment, because the polarization plane rotation caused by the reflection of a structure or the like does not suppress the different polarization even if the polarization receiving antenna is used, the XPD of the antenna decreases in the receiving device 60. As a result, the transmission quality deteriorates. However, when the receiving device 60 can receive not only the desired signal from the transmitting device 59 but also the interference signal u from the transmitting device 12, the quality of D, which is the desired signal, can be improved by the interference compensation method of the present invention. It is possible to compensate for the deterioration.

B. Application Example 2 In the communication line shown in FIG. 8, the transmitter 59 is provided with the vertically polarized antenna 61d, and the transmitter 12 is provided with the horizontally polarized antenna 13u. The receiving device 60 is provided with a vertically polarized antenna 1d and a horizontally polarized antenna 1u.
d and 1u receive the radio waves from the antennas 61d and 13u, respectively. The reception quality of the signals received by the antennas 1d and 1u of the receiving device 60 is deteriorated for the same reason as in Application Example 1. However, even in this case, the interference compensation method of the present invention can compensate for the quality deterioration of both the desired signals D and U.

C. Application Example 3 The communication line illustrated in FIG. 9 includes a transmitter 22 having a directional antenna 23d, a transmitter 24 having a directional antenna 25u, and a receiver 20 having directional antennas 21d and 21u. In these configurations, the antennas 21d, 21u, 23d, and 25u are all vertically polarized antennas having the frequency f and have directivity. Also, the antennas 21d and 23d, and the antenna 2
1u and 25u have directivities facing each other. Even in the communication line of this figure, the interference wave signal u is mixed in the desired wave signal D received by the antenna 21d,
The interference wave signal d is mixed in the desired wave signal U received by u. As a result, the transmission quality deteriorates for the same reason as in Application Example 1 or Application Example 2. But even in this case,
According to the interference compensation method of the present invention, it is possible to compensate the quality deterioration of both D and U which are desired signals.

By the way, according to the interference compensation method of the present invention, orthogonal polarizations that interfere with each other can be compensated by using the signals of each other in a fading environment. The efficiency can be greatly improved. Furthermore, if a directional antenna is used, 2
Simultaneous compensation of not only waves but also three waves and four waves can be dealt with by expanding the coefficient determination unit and the compensation circuit. Part 1
As an example, FIG. 10 shows a coefficient calculation unit 32a for simultaneously compensating for interference of three waves. The coefficient calculation unit 32a
This is an expansion of the coefficient calculation unit 32 in FIG.

In this embodiment, the interference compensating method of the present invention is used for the receiving device in the UHF (ultra high frequency) band or the microwave band frequency. However, in addition to this, an antenna having a single polarization plane or a fixed directivity is used. The present invention is applicable to any frequency that can be used by the antenna having the property. Further, in the present embodiment, an example of application to communication handling digital data communication such as TDMA packet communication is shown, but the applicable range of the present invention is not limited to this communication method. Further, in the control circuit 40 of the present embodiment, the tap coefficient is obtained using the RLS algorithm, but the algorithm for converging the tap coefficient is not limited to this.

[0027]

As described above, according to the present invention, it is possible to realize an interference compensation method capable of reducing interference in the same channel caused by the influence of fading or the like and obtaining high transmission quality and high frequency utilization efficiency.

[Brief description of drawings]

FIG. 1 is a diagram showing an example of a configuration of a communication system to which an interference compensation method of the present invention is applied.

FIG. 2 is a block diagram showing an example of a configuration of a receiving apparatus to which the interference compensation method of the present invention is applied.

FIG. 3 is a block diagram showing an example of a configuration of a compensation circuit 30 of this embodiment.

FIG. 4 is a schematic configuration diagram showing a configuration of a compensation circuit 30 of the present embodiment and an example of a flow of signals and control information.

FIG. 5 is a diagram showing an example of evaluation of BER characteristics with respect to each D / U of a desired signal and an interference signal by the interference compensation method of the present embodiment.

FIG. 6 is a diagram showing evaluation examples of BER characteristics with respect to D / U by the conventional interference compensation method and the interference compensation method of the present embodiment.

FIG. 7 is a diagram showing an example of a configuration of a communication line to which the interference compensation method of the present invention is applied.

FIG. 8 is a diagram showing an example of a configuration of a communication line to which the interference compensation method of the present invention is applied.

FIG. 9 is a diagram showing an example of a configuration of a communication line to which the interference compensation method of the present invention is applied.

FIG. 10 shows a case of simultaneously compensating for interference of three waves,
It is a figure which shows an example of a structure of a coefficient calculation part.

FIG. 11 is a block diagram showing a configuration example of a receiving device to which a conventional interference compensation method is applied.

FIG. 12 is a schematic configuration diagram showing a configuration example of a compensation circuit 3 according to a conventional interference compensation method and a flow of signals and control information.

FIG. 13 is a diagram showing a configuration example of one unit of a signal handled in a communication line to which the conventional interference compensation method and the interference compensation method of the present invention are applied.

[Explanation of symbols]

 20 receiver 30 compensation circuit 31a-31d signal processing circuit 32, 32a coefficient calculator 33 combining circuit 34a, 34b adder 37a-37d subtractor 38a, 38b training signal generator 39a-39d signal processing circuit 40 control circuit 60 receiver

Claims (2)

[Claims] 1. A desired signal 1 and a desired signal 2 which are time-divisionally configured by a training signal portion, which is a unique sequence predetermined for each transmitting device, and a data signal portion to be transmitted. A reception signal 1 in which an interference signal 1 which gives interference to the desired signal 1 to be received is mixed, and a reception signal 2 in which an interference signal 2 which gives interference to the desired signal 2 to be received are mixed In the device, the desired signal 1 and the desired signal 2 being received are
In the case of each of the training signal portions, training signal generating means 1 for generating a training signal corresponding to the desired signal 1, training signal generating means 2 for generating a training signal corresponding to the desired signal 2, Control means 1 and control means 2 for controlling the amplitude and phase of the output of the training signal generation means 1, respectively control means 3 and control means 4 for controlling the amplitude and phase of the output of the training signal generation means 2, and Subtracting means 1 for subtracting the output of the control means 1 from the received signal 1, subtracting means 2 for subtracting the output of the control means 3 from the output of the subtracting means 1, and subtracting the output of the control means 2 from the received signal 2. Subtraction means 3, subtraction means 4 for subtracting the output of the control means 4 from the output of the subtraction means 3, and the control means The control value in the control means 2 is the 2 row 1 column component, the control value in the control means 3 is the 1 row 2 column component, and the control value in the control means 4 is 2 Row 2 and column 2
An inverse matrix calculating means for calculating a matrix h which is an inverse matrix of the matrix H of the row and two columns matrix, and a square value of the output of each of the subtracting means 2 and the subtracting means 4 is minimized. So that the control means 1 to 4
Of the desired signal 1 and the desired signal 2 being received,
When each is a data signal portion, the product of the 1st row and 1st column component of the matrix h and the received signal 1 and the product of the 1st row and 2nd column component of the matrix h and the received signal 2 are added. Adder means 1 and adder means 2 for adding the product of the 2 × 1 column component of the matrix h and the received signal 1 and the product of the 2 × 2 column component of the matrix h and the received signal 2. An interference compensation method, characterized in that the desired signal 1 and the desired signal 2 are output by the combining means. 2. A receiver of a wireless communication line comprising a single or a plurality of transmitters and a receiver for receiving signals of the transmitters, wherein desired signals and interference signals to be transmitted and received are respectively The transmitter includes a training signal part, which is a predetermined unique sequence, and a data signal part to be partially transmitted in a time division manner, and interferes with the desired signal to be received and the desired signal. An integer N in which N-1 types of the interference signals are mixed
In a receiving device for inputting each of the received signal 1 to the received signal N, when the desired signal and the interference signal being received are the training signal portions, respectively, the desired signal or the interference signal For each of M training signal generating means 1 to training signal generating means M, which is the same number as N, for generating a corresponding training signal, and each of the received signal 1 to received signal N, the training signal Phase control means 1 to phase control means M for controlling the amplitude and phase of outputs from the generation means 1 to training signal generation means M, and the received signal N to the phase control means 1 to phase control means M. Through the training signal generating means 1
~ Subtracting means 1 to subtracting means M for reducing the output to the training signal generating means M, and N control lines for the controlling means 1 to controlling means M for each of the receiving signals 1 to N In a coefficient calculating means for calculating a matrix h of M rows and N columns, which is an inverse matrix of the matrix H which is the matrix H of M columns, in each of the reception signal 1 to the reception signal N, , The matrix h is obtained by controlling each of the control means 1 to control means M so that the square value of the output of the subtraction means M is minimized, and the desired signal and the interference signal received are: In the case of each data signal portion, reception signal control for forming M rows and N columns and controlling the amplitude and phase of the reception signal N with respect to each of the reception signals 1 to N and outputting them respectively Means 1 to received signal control means M
And an adder 1 to an adder M for obtaining an integer M number of compensation outputs by adding outputs of all the reception signal control units of the corresponding M rows, each of the elements of the matrix h. An interference compensation method, characterized in that each of the corresponding received signal control means is controlled by the following.