JPH09322585A - Power generator and vacuum cleaner using it - Google Patents

Abstract

(57) Abstract: A brushless motor having a conventional configuration uses three-phase windings, and an inverter circuit also uses six transistors, which makes the configuration complicated. A control circuit 65 receives a signal from a position detection means 66 and adjusts a ratio of ON times of a first switching element 71/74 and a second switching element 72/73,
The inverter circuit 64 includes the single-phase winding 67 of the first object 60.
The power generation device is capable of effectively using the switching element that constitutes the circuit by controlling the current supplied to the circuit so that the magnitudes in the positive direction and the negative direction are equal.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power generation device such as a motor or a linear motor used for home or industrial use,
The present invention relates to a vacuum cleaner using the power generation device.

[0002]

2. Description of the Related Art A conventional power generator is a brushless motor as shown in FIG. This brushless motor includes a stator that constitutes a first object 1, a rotor that constitutes a second object 2 that is rotatably provided inside the first object 1, and a position detection that detects the position of a magnetic pole. Means 33, a control circuit 30 for controlling the rotation of the second object 2 by the signal of the position detection means 33, and an inverter circuit 50 for rotating the second object 2 by the signal of the control circuit 30.

[0003] The second object 2 includes a magnetic body 5, a permanent magnet 3 and a permanent magnet 4 provided on the surface of the magnetic body 5, and an output shaft 6.
have. The permanent magnet 3 is bonded to the surface of the magnetic body 5 such that the N pole is on the outside, and the permanent magnet 4 is bonded to the surface of the magnetic body 5 so that the S pole is on the outside. The first object 1 includes an iron core 7 formed by laminating silicon steel plates and the like, and windings 8a and 9 provided in a slot formed by the iron core 7.
It has a, 10a, 8b, 9b and 10b. Winding 8
The a.8b, the windings 9a and 9b, and the windings 10a and 10b are connected in series, respectively, and are arranged at positions separated by 60.degree. so as to form a three-phase winding.

Each of the windings is driven by an inverter circuit 50 and a control circuit 30 which controls the inverter circuit 50. The inverter circuit 50 is a commercial AC power supply 1
1 and a full-wave rectifier circuit 12 for rectifying the commercial AC power supply 11
And a filter circuit 40 that shapes the waveform of this output, and an output circuit 17 that operates according to the output of the filter circuit 40. The rectifier circuit 12 is composed of diodes 13 ・ 14 ・ 1.
It is configured by connecting 5 and 16 in a bridge. The filter circuit 40 is composed of an electrolytic smoothing capacitor 41 and a choke coil 42, and waveform-shapes the output of the rectifier circuit 12 into a nearly complete direct current with little ripple. The output circuit 17 has a configuration in which six transistors 18 to 23 and six diodes 24 to 29 are connected to a three-phase inverter. The control circuit 30 has a drive circuit 31 and a logic circuit 32, and the base terminals of the respective transistors are all connected to the drive circuit 31.

The position detecting means 33 includes a first object 1 and a second object 1.
Hall ICs 34 and 35 provided in the gap between the object 2
36, and detects the positions of the permanent magnets 3 and 4 when the second object 2 rotates.

In the above configuration, the control circuit 30 receives the signal of the position detecting means 33, sequentially drives the six transistors 18 to 23, and rotates the second object 2. That is, the Hall IC 33.3 which constitutes the position detecting means 33.
By logically operating the three signals of 4.35, 3
Six transistors 18 to 23 forming a phase inverter
It is what creates the high and low signals that drive the. The drive circuit 31 supplies a base current to the transistor to turn it on when this signal is a high signal, and applies a reverse bias to the base to turn it off when the signal is a low signal.

As a result, the windings 8a, 9a, 10a, 8b, 9b, arranged in the three phases provided on the first object 1 are arranged.
The current flows sequentially through 10b. This current magnetizes the iron core 7, and the magnetic flux generated from the iron core 7
The permanent magnet 3 or the permanent magnet 4 constituting the object 2 acts to generate torque. This torque can be supplied to an external load using the output shaft 6.

[0008]

The brushless motor having the above-mentioned conventional structure uses three-phase windings, and the inverter circuit also uses six transistors. Therefore, the structure is complicated. The problem is that

[0009]

SUMMARY OF THE INVENTION The present invention solves the problems of the conventional structure as described above, and it is possible to solve the problems of the first object having a single-phase winding and the first object. A second object having a relatively movably provided permanent magnet is provided, and the power generation device is configured to control the current supplied to the winding by the control circuit to an equal amount of positive and negative.

[0010]

According to a first aspect of the present invention, a control circuit receives a signal from a position detecting means to adjust a ratio of ON times of a first switching element and a second switching element, and an inverter circuit A power generator capable of controlling the current supplied to the single-phase winding of the first object so that the magnitudes in the positive direction and the negative direction are equal to each other and effectively using the switching elements forming the circuit. I am trying.

According to a second aspect of the present invention, an ON period ratio control circuit constituting the control circuit is a power generator for controlling the DC component of the winding current detected by the DC component detection circuit to be zero. .

According to a third aspect of the present invention, an unbalance amount detecting circuit detects an on period ratio of the first switching element and the second switching element by the unbalance detecting circuit. The power generator is used to control the balance to zero.

According to a fourth aspect of the invention, the control circuit comprises:
By controlling the turn-on timings of the first switching element and the second switching element, control is performed so that the moment when the polarities of the electromagnetic forces generated between the first object and the second object are reversed does not occur. As a result, the reverse direction torque is not generated, the performance is high, and the size, cost, weight and efficiency are improved.

According to a fifth aspect of the present invention, a vacuum cleaner that drives a fan with the output of the power generator is a compact, lightweight, low-priced, highly efficient vacuum cleaner.

[0015]

【Example】

(Embodiment 1) Hereinafter, a first embodiment of the present invention will be described. FIG. 1 is an explanatory diagram illustrating the configuration of the power generation device according to the present embodiment. The first object 60 includes a single-phase winding 67 and an iron core 68.
It is configured to be wound around. The second object 61 is provided so as to be movable relative to the first object 60.
9 and 70 and the output shaft 59. Reference numeral 64 denotes an inverter circuit, which includes a first switching element (hereinafter simply referred to as a first switching element) composed of a pair of switching elements 71 and 74, and a pair of switching elements 7 similarly.
And a second switching element (hereinafter, simply referred to as a second switching element) composed of 2 · 73.
Supplying current to 7. Further, reference numeral 65 is a control circuit for controlling the inverter circuit 64 by receiving a signal from the position detecting means 66 constituted by a Hall IC.

The position detecting means 66 detects the positions of the magnetic poles of the permanent magnets 69 and 70 of the second object 61, and detects the high signal when detecting the N pole and the S pole. Generates a low signal.

The inverter circuit 64 includes a first switching element, a second switching element, and a silicon type diode 75.7 connected in anti-parallel to each switching element.
It has 6.77.78 and DC power supply 63.

The control circuit 65 receives the signal from the position detecting means 66 and outputs drive signals a, b, c and d for driving the first switching element and the second switching element. When each switching element receives a high signal from the control circuit 65, it is turned on and turned on,
When it receives a low, it turns off and turns off.

Thus, the first switching element and the second switching element supply current to the winding 67. As a result, the second object 61 rotates clockwise with respect to the first object 60. That is, a clockwise torque is generated.

The operation of the embodiment will be described below. FIG. 2 is a waveform diagram showing the operation of the power generator of this embodiment. 2A shows the waveforms of the drive signals a and d for the control circuit 65 to drive the first switching element, and FIG.
The waveforms of the drive signals b and c for driving the second switching element are shown, and (c) shows the waveform of the current i _M flowing through the winding 67.

In general, the switching element executes a turn-off after a delay from the turn-off signal when the turn-off signal is sent from the control circuit. In the present embodiment, as shown in FIG. 2C, the turn-off delay time of the first switching element is t _d1 and the turn-off delay time of the second switching element is t _d2 .
This turn-off delay time depends on the variation of the element.
The relationship is t _d1 > t _d2 .

The control circuit 65 controls the ON time T ₁ of the first switching element and the ON time T ₂ of the second switching element.
And are controlled so that T ₁ <T ₂ .
Those of properly controlling the ratio T ₁ / T ₂ T ₁ and T ₂ in other words. Therefore, the current i _M flowing through the winding 67
2 has the same magnitude in the positive and negative directions, as shown in FIG. As a result, the first
The currents flowing through the switching element and the second switching element become equal to each other, and one of them does not become excessive.

In other words, according to this embodiment, the ratings of the two switching elements, that is, the first switching element and the second switching element, can be used fully, and the current flowing through one switching element becomes large, resulting in loss. It is possible to increase the reliability of the device without increasing or destroying it. Further, the loss generated in the winding 67 and the generated torque ripple can be reduced.

As an example of the case where the control is not appropriate, t
A case where control is performed with T ₁ = T ₂ = 0.5 ms under the condition of _d1 > t _d2 will be described. In this case, since T ₁ = T ₂ is set, the winding 67 is equal to t _d1 > t _d2.
The application time of the positive and negative voltages with respect to is different. As a result, the current flowing through the winding 67 is large on the positive side and small on the negative side as shown in FIG. That is, the direct current component i _DC is generated.

When the device is operated with such a current waveform, the collector current of the first switching element is
It is much larger than the collector current flowing through the switching element. Therefore, the loss of the first switching element increases, which may lead to destruction. However, since only a small current flows through the second switching element, there is a large margin with respect to the rating, so that the second switching element cannot be effectively utilized. Also, winding current i _M
Since the current in the positive direction and the current in the negative direction are different, the torque ripple as the power generation device becomes large, and the effective value of the current flowing in the winding becomes large, so that the heat generation also becomes large.

In the example given here, the first switching element and the second switching element are explained as having a difference in delay time. However, even if the delay times are equal, saturation of the collector and the emitter is caused. The same phenomenon occurs when there is a difference in voltage or when there is variation in the delay time in the drive circuit of the switching element.

In particular, for a power generator that requires high efficiency.
In this case, the loss (copper loss) of the winding 67 should be minimized.
The DC resistance component of the winding 67 as much as possible for the purpose of
Design is often done. In this case, as above
Due to variations in characteristics between various switching elements,
Even if a slight DC component is generated in the winding 67, i _DC
The value of will be very large and will greatly affect the operation of the device.
May cause disability.

In this embodiment, the signals a, b, c, d generated by the control circuit 65 are controlled so that the actual ON periods of the respective switching elements are the same.
It is not always necessary that the actual ON periods are equal. That is, the positive and negative values of the winding current may be different due to the various causes as described above, and in some cases, the ON periods of the first switching element and the second switching element are different from each other. In some cases, the positive and negative magnitudes of the winding current may become equal for the first time.

In this embodiment, the size of the gap 79 between the iron core 68 and the second object 61 forming the first object 60 is not constant but is inclined. Therefore, when a so-called reluctance torque is generated and the inverter 64 is stopped, the second object 61 stops in a slightly tilted state as shown in FIG. That is, it stops at the position where the gap 79 between the iron core 68 and the second object 61 is the minimum, that is, the position where the magnetic resistance is the smallest. In this way, since the second object 61 stops in a slightly tilted state, it is possible to avoid the state where the starting torque becomes 0, and the structure having the single-phase winding 67 facilitates starting. Has become.

Although the second object 61 has two poles in this embodiment, it may have four poles, six poles, eight poles, or the like.
Further, although a Hall IC or a Hall element is used as the position detecting means 66, one that optically detects a rotation angle, one that uses ultrasonic waves, or the first object 60 is not provided with a separate element, The rotation angle of the second object 61 may be detected by using the voltage induced in each winding. As for the switching element, a bipolar transistor is used in this embodiment, but M
You may use OSFET, IGBT, etc.

Further, in the present embodiment, the power generating device transmits the rotary motion to the load, but the power generator is not necessarily limited to the rotary motion. For example, a linear motor such as a linear motor that performs a linear motion, and two-dimensionally It may be one that generates power.

In the present embodiment, the power is taken out by fixing the first object 60 and rotating the second object 61, but conversely, fixing the second object 61 and fixing the first object 60. You may make it take out power from. Further, in the present embodiment, all the components such as the inverter circuit 64 and the control circuit 65 are fixed in the same manner as the first object 61. However, for example, some or all of these components are arranged in the second object. It may be provided on 61, and the electric wire may be unwound and finally connected to the winding provided on the first object 60. In this case, if necessary, the current can be supplied by using a brush and a slip ring.

(Second Embodiment) Next, a second embodiment of the present invention will be described. As shown in FIG. 4, in the present embodiment, the control circuit 150 includes a DC component detection circuit 151 that detects a DC component of the current flowing through the winding 67, and an amplifier 156 that is connected to the output of the DC component detection circuit 151. And an ON period ratio control circuit 157, and a drive circuit 158 for producing signals a, b, c, d for driving the first switching element and the second switching element by the signal of the ON period ratio control circuit 157. There is. The DC component detection circuit 151 has 2
Winding current detection circuit 15 composed of 0 mΩ resistor
2 and a low pass filter 153. In the low-pass filter 153, the resistors 154 and the capacitors 155 are set to have a time constant that can almost completely cut the fundamental wave component of the winding current.

With the above configuration, the DC component detection circuit 151 detects the DC component corresponding to i _DC shown in FIG. The information of the DC component detection circuit 151 is fed back to the ON period ratio control circuit 157, and the ON period ratio control circuit 157 outputs the signal p for adjusting t _d1 or t _d2 in the direction in which the DC component i _DC approaches zero. It is being made.
The drive circuit 158 receives this signal p and outputs drive signals a, b, c, d to the first switching element and the second switching element which form the inverter circuit 64. That is, the current i _M flowing through the winding 67 by the inverter circuit 64 is monitored by the DC component detection circuit 151, and the information of the DC component i _DC of this i _M is fed back to the ON period ratio control circuit 157 to calculate the ON period ratio. Control circuit 1
The drive circuit 158 outputs drive signals a, b, c, d according to the signal p output from 57.

In this embodiment, the amplifier 156 is provided at the output of the low-pass filter 153, and the feedback control is performed so that the gain is 60 dB (1000 times) or more for direct current. The DC value of the winding current can be suppressed to a very small value. Further, in the present embodiment, the direct current component of the current flowing through the winding 67 is always detected, and the feedback control is performed so that the direct current component becomes zero. Therefore, during the operation of the device, a load fluctuation occurs or a switching element is generated. Even if the temperature rises, stable control can always be performed.

(Third Embodiment) Next, a third embodiment of the present invention will be described with reference to FIG. In the present embodiment, the control circuit 160 has an input current imbalance detection circuit 161 that detects an imbalance of the input current and an ON period ratio control circuit 162 that controls the ON period ratio.
The ON period ratio control circuit controls the ratio of the ON periods of the first switching element and the second switching element so that the output of the input current imbalance detection circuit becomes zero. That is, the input current imbalance detection circuit 161 and the ON period ratio control circuit 162 constitute a feedback circuit that feedback-controls the drive signals a, b, c, and d output by the drive circuit 158. The control input current unbalanced component detection circuit 161 includes the inverter circuit 6
Current sensor 1 composed of the current transformer provided in 4
63 and the current detected by the current sensor 163, the difference between the current flowing in the first switching element and the current flowing in the second switching element is detected, and this signal is output to the ON period ratio control circuit 162. It has means 164.

The operation of this embodiment will be described below. FIG. 6A shows the input current i _IN flowing through the inverter circuit 64.
Input current unbalance detection circuit 161
Is the value I ₁ of i _{IN at} the timing of turning off the first switching element and turning on the second switching element from the on state of the first switching element, and turning off the second switching element to the first The value I ₂ of i _{IN at} the timing of turning on the switching element is recognized, the current difference detection means 164 calculates (I ₁ −I ₂ ) and outputs this signal to the ON period ratio control circuit 162. The on period ratio control circuit 162 receives this information and creates a signal p indicating the ratio (T ₁ / T ₂ ) of the on times of the first switching element and the second switching element, and the drive circuit 15
It outputs to 8. The drive circuit 158 includes the input current imbalance detection circuit 161 and the ON period ratio control circuit 16
The feedback control by 2 controls the drive signals a, b, c and d so that the unbalanced amount detected by the input current unbalanced amount detection circuit 161 becomes zero.
FIG. 6A shows a state where the unbalance amount becomes zero by this feedback control, that is, a state where (I ₁ −I ₂ = 0).

Here, FIG. 6A shows the waveform of the input current i _IN flowing through the inverter circuit 64 when the control by the normal open loop is performed. In this case, I
There is a large imbalance between ₁ and I ₂ . Therefore, the current flowing through the winding 67 also has a difference in positive and negative components.

As described above, according to this embodiment, the second embodiment
The direct current detection circuit 151 having a complicated configuration used in the above is not used, and a current transformer having a simple configuration is used as the current sensor 163 to detect the input current flowing in the inverter circuit 64 and execute feedback control. It is a thing. In addition, when current detection is performed using the resistance element used in the second embodiment, power loss occurs in the resistance element. However, according to the present embodiment, no power loss occurs and the efficiency is improved. Achieving a high price.

(Embodiment 4) Next, a fourth embodiment of the present invention will be described. FIG. 7 is a circuit diagram showing the configuration of the power generator of this embodiment. In this embodiment, the control circuit 165
Is an electromagnetic force generated between the first object 60 and the second object 61 (rotational motion in the present embodiment) by adjusting the turn-on timing of the first switching element and the second switching element. Therefore, the current supplied to the winding 67 is controlled so that the moment when the polarity of the torque becomes opposite) does not occur.

That is, the control circuit 165 has an electric signal processing circuit 166 which detects the current i _M flowing through the winding 67 and performs signal processing. The electric signal processing circuit 166 has two
Winding current detection circuit 152 composed of 0 mΩ resistance
And the direct current component detection circuit 151 and the code determination unit 82 described with reference to FIG. That is, the code determiner 82
A high signal is output when the voltage ε across the winding current detection circuit 152 is positive (ie, i _M > 0), and a low signal is output when ε is negative (ie, i _M <0). To do.

Further, the position detecting means 88 for detecting the positions of the permanent magnets 69 and 70 is an electric neutral point of the first object 60,
That is, the magnetic sensor 79 constituted by the Hall element provided at the position where the magnetomotive force of the winding 67 is just zero.
And a sign determiner 80 that outputs high and low signals according to the sign of the output of the magnetic sensor 79.
That is, when the N pole faces the magnetic sensor 79, the sign determiner 80 outputs a high signal, and when the S pole faces the magnetic sensor 79, the sign determiner 80 outputs a low signal. is there.

Further, the control circuit 165 receives the signal of the position detecting means 88 and the signal of the electric signal processing circuit 166,
A phase error detection circuit 85 that amplifies the phase difference between the signals and outputs a signal s, and a signal s from the phase error detection circuit 85 are received to determine a phase advance angle β with respect to the output of the position detection means 88. It has a phase advance control circuit 86 that outputs this signal.

FIG. 8 is a specific circuit diagram of the phase error detection circuit 85. The D flip-flop 89 is composed of, for example, a μPD4013B which is a MOS type digital IC, and the input terminal D (hereinafter simply referred to as D) at the timing of the rising edge of the signal at the input terminal CP (hereinafter simply referred to as CP). ), And outputs the result to an output terminal Q (hereinafter simply referred to as Q). In the present embodiment, this D flip-flop 8
No. 9 uses a DC power source of 12V.

The signal p from the position detection means 88 is input to CP, and the signal r from the winding current detection circuit 83 is input to D. A low-pass filter 90 for removing the pulse frequency components of the signals p and r and passing the average value component is connected to Q. The low pass filter 90 is composed of a resistor 91 and a capacitor 92. The output of the low-pass filter 90 is the operational amplifier 9
It is connected to a kind of amplifier circuit using 3. The output of the low-pass filter 90 is connected to the minus input terminal of the operational amplifier 93 via the resistor 94, and the capacitor 95 and the resistor 9 are provided between the minus input terminal and the output terminal.
A feedback circuit composed of 6 series circuits is connected. A signal obtained by dividing the power supply voltage of 12 V by the resistors 97 and 98 is applied to the positive input terminal.
In this embodiment, the same resistors 97 and 98 are used, and a signal of just 6 V is applied to the positive input terminal.

The operation of this embodiment will be described below. The operation of reducing the DC component of the current flowing through the winding 67 to zero is completely the same as the operation described in FIG. The point of the operation in this embodiment is that the first object 6
This is a method of controlling the current flowing through the winding 67 so that the moment when the polarities of the electromagnetic force generated between 0 and the second object 61 are not reversed, that is, the reverse torque is not generated. .

According to the experiments conducted by the inventors, if the phase of the current i _M flowing through the winding 67 and the phase of the signal p of the position detecting means 88 match each other, the first object 60 and the second object 60 Object 61
The moment when the polarities of the electromagnetic force generated between and are not reversed does not occur. That is, no reverse torque is generated.

Here, the case where the phase of the current i _M flowing through the winding 67 is delayed from the signal p of the position detecting means 88 will be described. In the case where the phase of the current i _M flowing through the winding 67 is ahead of the signal p of the position detecting means 88, the opposite of the following description is made.

It is assumed that the signal p from the position detecting means 88 is input to the CP of the D flip-flop 89 and the potential of CP rises from low to high. At this moment, the voltage of D is still low input, so the signal output from Q is low. Therefore, the output level of the low-pass filter 90 becomes lower than 6V. The operational amplifier 93 and its peripheral circuits act so as to amplify the error voltage between the output of the low-pass filter 90 and the voltage (6 V) at the positive input terminal, and output the amplified component of this error voltage as a signal from the S terminal. . Here, the capacitor 95 connected to the operational amplifier 93 operates so as to integrate this signal voltage.

Therefore, in this embodiment, when the DC component of the signal output from Q is slightly deviated from 6 V, that is, when the duty ratio of Q is slightly deviated from 1/2, the error is integrated. Is output. That is, when the feedback operation is performed, the phase error between p and r can be almost completely reduced to zero.

Since the operational amplifier 93 and its peripheral circuits are connected so that the sign is inverted and output, the phase error detection circuit 85 is provided when the phase of i _M is delayed.
The output s of the phase error detection circuit 85 is low when the phase of i _M is advanced.

In the circuit shown in FIG. 8, the D flip-flop 89 is used to form the phase error detection circuit 85. However, it is not always necessary to use such a component, and it is general. Phase detection circuit (Phase detect circuit)
Even with a circuit configuration called r), similar operation can be expected.

The signal s as described above is input from the phase error detection circuit 85 to the phase advance control circuit 86. The phase advance control circuit 86 receives the input signal s and detects the position detecting means 88.
The leading phase angle β with respect to the output signal p from is determined as shown in FIG. 9, and this signal is output to the drive circuit 84. That is, when the signal voltage s is 10 V, the lead phase angle β is 40 °, and when the signal voltage s is 10 V, the lead phase angle β is 25 °, and the relations are set by connecting them in a straight line. . In this embodiment, the rotation speed is 55000r.
In the steady state under the condition of / m, that is, the phase difference between p and r is zero, the voltage value of s is about 6V.
Thus, the lead phase angle β is about 25 °. Thus, by determining the lead phase angle β with respect to the output signal p from the position detecting means 88 as shown in FIG. 9, the phase of the current i _M flowing through the winding 67 and the signal p of the position detecting means 88 are determined. The phase can be matched and the first object 60
The moment at which the polarities of the electromagnetic force generated between the second object 61 and the second object 61 are reversed does not occur. That is, no reverse torque is generated.

As described above, in the present embodiment, the winding 6 is always driven by the phase error detection circuit 85 and the phase advance control circuit 86.
The position detecting means 88 detects the difference between the phase of the current flowing through the signal No. 7 and the phase of the signal whose magnetic pole changes, and uses this difference signal as a feedback signal. Further, this feedback control causes the advance phase angle β to be zero so that the phase difference becomes zero.
Is the one that controls. Therefore, for example, even when the power supply voltage fluctuates, the load fluctuates, or circuit component parts vary, accurate control can be performed.

FIG. 10 shows operation waveforms when the value of the lead phase angle β is insufficient. 10A shows the output signal p of the position detecting means 88, and FIG. 10A shows the winding current i _M.
Is shown. It is assumed that the DC component of the winding current i _M is in a zero state. In this case, the on / off switching timings t ₁ and t ₄ of the switching element are delayed, so that at the timings t ₂ and t _{5 at} which the output signal p of the position detection means 66 is switched, i is still i.
_M has not reached zero. Since it is the timing of t ₃ · t _{6 that} i _M = 0, torque in the reverse direction is generated during the period of t _{2 to} t _{3 and} the period of t _{5 to} t ₆ .

That is, during the period from t _{2 to} t ₃ , the N pole faces the position detecting means 88, and the positional relationship is exactly as shown in FIG. 1, and i _M <0. . Therefore, the direction of the magnetic flux Φ flowing through the iron core 68 is Φ <0, and the counterclockwise torque opposite to the arrow shown in FIG. 7 is generated. Similarly, in the hatched period in FIG. 10, torque in the opposite direction is generated in all directions, and since these are in the opposite directions to the original rotation direction, they act as a brake. As a result, the ripple of the generated torque increases, the torque generated by the device decreases, and the winding current increases, the current value of the switching element increases, and the efficiency of the device decreases.

On the contrary, FIG. 11 shows an operation waveform when the lead phase angle β becomes excessively large. In this case, as shown in FIG. 11A, since the switching timings t ₁ and t ₄ of the switching elements are too advanced,
The timing t ₂ · t _{5 at} which the winding current i _M = 0 becomes earlier than the edge time t ₃ · t ₆ of the output signal p of the position detection means 88, and the opposite direction is maintained in the hatched period. A torque is generated.

In this respect, as in the present embodiment, by advancing to the state where no reverse torque is generated and adjusting the phase angle β, the operation is good, the performance is high, the size is small and the cost is low.
This is to realize a lightweight and highly efficient power generator.

(Fifth Embodiment) Next, a vacuum cleaner according to a fifth embodiment of the present invention will be described with reference to FIG. The power generation device 105 described in each of the embodiments is provided in the housing. A fan 106 is connected to the output shaft of the power generator 105. A paper pack 107 is provided in front of the fan 106, and the nozzle 109 and the hose 1 are provided.
It accommodates the dust sucked through 08. Rectifier circuit 1
13 uses, for example, four silicon diodes, and is connected to a commercial power source by a power cord 110.

In order to facilitate the movement of the vacuum cleaner,
A front wheel 111 and a rear wheel 112 are provided.

The operation of this embodiment will be described below. When the power cord 110 is connected to a commercial power source and a switch (not shown) is turned on, the power generation device 105 starts operating. When the power generation device 105 starts rotating, the fan 1
06 starts rotating, and dust is stored in the paper pack 107 via the nozzle 109 and the hose 108.

Power generator 105 used here
Is the one described in each of the above-mentioned embodiments, and has a very simple structure without a commutator or a brush, using a single-phase winding, and a bidirectional switching element. Therefore, reliability can be sufficiently ensured even after long-term use, and it is low-priced and small.

Further, the power generator 105 is provided with an inclination in the gap 79 as described with reference to FIG.
The first stop position can be a position where the dead center is removed.
The fan 106 uses, for example, a bearing to minimize friction during rotation. Therefore, the size of the gap is as small as 0.2 to 0.5 mm. Therefore, the power generation device 105 requires less torque for starting, and can start reliably.

[0064]

According to the invention described in claim 1, a first object having a single-phase winding, and a second object having a permanent magnet movably provided relative to the first object are provided. An inverter circuit having a first switching element and a second switching element for supplying a current to the winding, a control circuit for controlling the inverter circuit, and a position detecting means for detecting the position of the permanent magnet. The control circuit has a simple configuration and a single-phase winding as a configuration for adjusting the ON time ratio of the switching element so that the magnitude of the winding current in the positive direction becomes equal to that in the negative direction. The power supply device is realized in which the current supplied to the line is controlled so that the magnitudes in the positive direction and the negative direction are equal to each other, and the switching elements forming the circuit can be effectively used.

In the invention described in claim 2, the control circuit is
A DC component detection circuit for detecting a DC component of the winding current and an ON period ratio control circuit for controlling a ratio of ON periods are provided, and the ON period ratio control circuit includes a first switching element and a second switching element. The ON period ratio is controlled so that the output of the DC component detection circuit becomes zero, and the switching elements that make up the circuit are effectively used by controlling the size of the positive direction and the negative direction to be equal. It realizes a power generation device that can perform.

In the invention described in claim 3, the control circuit is
An unbalanced amount detection circuit circuit that detects an unbalanced amount of the input current and an ON period ratio control circuit that controls a ratio of ON periods are provided, and the ON period ratio control circuit includes a first switching element and the second switching element. The ON period ratio of the switching element is controlled so that the output of the unbalanced amount detection circuit becomes zero, and the circuit is configured by controlling the magnitudes in the positive direction and the negative direction to be equal. The present invention realizes a power generation device that can effectively use a switching element.

In the invention described in claim 4, the control circuit is
By adjusting the turn-on timings of the first switching element and the second switching element, it is possible to prevent the moment when the polarities of the electromagnetic forces generated between the first object and the second object are reversed from occurring. In this configuration, the reverse control torque is not generated, the performance is high, and the power generation device that is small in size, low in cost, lightweight, and highly efficient is realized.

The invention described in claim 5 is a structure having the power generation device according to any one of claims 1 to 4 and a fan connected to the output of the power generation device, and is small, lightweight, and It is a low-cost, highly efficient vacuum cleaner.

[Brief description of drawings]

FIG. 1 is a circuit diagram showing a configuration of a power generation device that is a first embodiment of the present invention.

FIG. 2 is a waveform chart showing the operation of each unit.

FIG. 3 is a waveform chart showing the operation when the setting is not appropriate.

FIG. 4 is a circuit diagram showing a configuration of a power generator which is a second embodiment of the present invention.

FIG. 5 is a circuit diagram showing a configuration of a power generation device that is a third embodiment of the present invention.

FIG. 6A is a waveform diagram showing the input current of the inverter circuit. FIG. 6B is a waveform diagram showing the operation when the setting is not appropriate.

FIG. 7 is a circuit diagram showing a configuration of a power generation device that is a fourth embodiment of the present invention.

FIG. 8 is a circuit diagram showing a configuration of a phase error detection circuit of the same.

FIG. 9 is a characteristic diagram showing control of the phase advance control circuit.

FIG. 10A is a waveform diagram showing the output signal of the position detecting means. FIG. 10B is a waveform diagram showing the winding current i _M when the value of the lead phase angle β is insufficient.

FIG. 11A is a waveform diagram showing the output signal of the position detecting means. FIG. 11B is a waveform diagram showing the winding current i _M when the value of the lead phase angle β is excessive.

FIG. 12 is an explanatory diagram showing the configuration of a vacuum cleaner that is a fifth embodiment of the present invention.

FIG. 13 is a circuit diagram showing a configuration of a conventional brushless motor.

[Explanation of symbols]

 60 First Object 61 Second Object 64 Inverter Circuit 65 Control Circuit 66 Position Detection Means 67 Winding 69 Permanent Magnet 70 Permanent Magnet 71 First Switching Element 72 Second Switching Element 73 Second Switching Element 74 First Switching device 105 Power generator 106 Fan 150 Control circuit 151 DC component detection circuit 157 ON period ratio control circuit 160 Control circuit 161 Unbalanced component detection circuit 162 ON period ratio control circuit 165 Control circuit

Claims (5)

[Claims] A first object having a single-phase winding;
A second object having a permanent magnet movably provided relative to the object, an inverter circuit having a first switching element for supplying a current to the winding and a second switching element, A control circuit for controlling the inverter circuit,
Position control means for detecting the position of the permanent magnet is provided, and the control circuit controls the ON time ratio of the switching element so that the magnitudes of the winding current in the positive and negative directions become equal. Power generator. 2. The control circuit includes a DC component detection circuit for detecting a DC component of a winding current and an ON period ratio control circuit for controlling a ratio of ON periods, and the ON period ratio control circuit is a first circuit. The power generator according to claim 1, wherein the ratio of the ON period of the switching element and the second switching element is controlled so that the output of the DC component detection circuit becomes zero. 3. The control circuit comprises an unbalanced component detection circuit for detecting an unbalanced component of the input current, and an ON period ratio control circuit for controlling a ratio of ON periods. The ON period ratio control circuit comprises: 2. The ratio of the ON period of the first switching element and the ON period of the second switching element is controlled so that the output of the unbalanced amount detection circuit becomes zero.
The power generator described. 4. The control circuit adjusts the turn-on timing of the first switching element and the second switching element so that the polarity of the electromagnetic force generated between the first object and the second object is reversed. The power generator according to any one of claims 1 to 3, wherein the current flowing through the winding is controlled so that the moment at which 5. A vacuum cleaner comprising a power generator according to any one of claims 1 to 4, and a fan connected to an output of the power generator.