JPS6033723A - tuner device - Google Patents

Abstract

PURPOSE:To incorporate an inductor component and a capacitor component onto a circuit board by operating one electrode of the circuit board as a distributed inductance and operating the other electrode as a distributed capacitance. CONSTITUTION:The respective electrodes 21, 24 of optional shape are placed on one side of a dielectric circuit board 20 so as to constitute a tuner circuit block. On the other hand a component 26 other than that for the tuner is mounted on the circuit board 25 so as to constitute a universal circuit block. A required connection circuit part in the tuner circuit block and the universal circuit block is connected by connection conductors 27 and 28 and further connected to a common circuit board 29.

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention relates to an implementation configuration of a cheese device that can be used in receivers and transmitters for televisions, radios, stereos, personal radios, and other communication devices in general. .

Conventional configurations and their problems In recent years, reducing the manufacturing costs of receivers, transmitters, and communication devices has become a major issue, and in particular, the implementation of high-frequency circuits, which is difficult to rationalize, requires extensive technological development. is necessary. Furthermore, in addition to streamlining the adjustment in the tuning circuit section, improving the stability of the performance of the tuning circuit section after adjustment has also become a major issue.

The mounting structure and tuner components of a conventional cheese device will be described below with reference to the drawings. FIG. 1 shows a side view of an embodiment of a conventional tuner device. In FIG. 1, an inductor 2, a trimmer capacitor 3, a voltage variable capacitance diode 4,
A tuning section consisting of a fixed capacitor 5 and a fixed capacitor 5 was connected to a circuit section such as other circuit components (for example, an ice, a resistor 7, etc.) by a circuit conductor 8.

FIG. 2 shows a configuration diagram of conventional tuning components in a tuning section. An inductor 9, a trimmer capacitor 1o1, a voltage variable capacitance diode 11, and a fixed capacitor 12 were connected by circuit conductors 13 and 14.

However, regarding the tuner with the above configuration, (1) The inductor component and capacitor component are large in size compared to other high frequency components, and the height dimension in particular hinders miniaturization and thinning of the device.

■ The inductance of inductor parts tends to shift due to mechanical vibration, and since the ferrite core has a large temperature dependence, the inductance is unstable and the tuning frequency fluctuates greatly.

■ Inductor and capacitor components exist as separate components and are connected by a conductor routing circuit, which causes a large amount of lead inductance and stray capacitance, making circuit operation unstable.

■ Since it is a collective circuit of individual parts with independent minimum unit functions, there are limits to reducing the number of parts and rationalizing manufacturing.

Furthermore, as for the tuner device, ■ The area occupied by all the components distributed and the area occupied by the circuit conductors is required, which increases the area of the circuit board, which impedes miniaturization of the device.

■ Changes in device specifications require design changes in the mounting configuration of the entire circuit board, making it difficult to shorten and rationalize design time.

■ The circuit board only has the function of connecting and holding components together, so it has low added value and becomes a factor in increasing costs.

It had the following problems.

Purpose of the Invention The purpose of the present invention is to realize a circuit board block forming a tuner in which an inductor part and a capacitor part are integrated, and to rationally interconnect the circuit board block and the circuit board block on which other parts are mounted. The object of the present invention is to provide a cheese device that provides a high level of comfort.

Structure of the Invention The tuner device of the present invention includes a tuning section configured such that the ground terminals of the electrodes that are arranged opposite to each other via a dielectric substrate or arranged in parallel on the surface of the dielectric substrate are opposite to each other. a first circuit board on which at least one or more tuners are formed; and a second circuit board on which circuit components other than the tuner are mounted;
The required circuit parts to be connected between the two circuit boards are connected by conductors, and the tuner on the first circuit board has opposing electrodes, one of which acts as a distributed inductor, and This electrode and the other electrode face each other to form a distributed constant circuit with an open tip, thereby realizing distributed capacitance due to the negative reactance generated, and acting in parallel with the above distributed inductor to function as a resonant circuit. It is something that makes you

DESCRIPTION OF EMBODIMENTS Hereinafter, embodiments of the present invention will be described with reference to the drawings.

FIG. 3 shows a configuration diagram of a tuner circuit block board constituting a cheese device in an embodiment of the present invention.

Electrodes 16 to 19 having an arbitrary shape are installed on one side of the dielectric circuit board 150, and electrodes (not shown) having the same shape as the electrodes 16 to 19 are installed on the other side of the dielectric circuit board 15. ) are installed opposite each other.

FIG. 4 shows a side view of a tuner device according to an embodiment of the present invention. The electrode 21 is connected to the circuit board 20.
The circuit board blocks on which the circuit boards 24 to 24 are installed are the tuner circuit blocks described in FIG. 3 above. On the other hand, a circuit board block in which components 26 other than the tuner are installed with respect to the circuit board 25 is a universal circuit block.

The required connection circuit parts in the above tuner circuit block and universal circuit block are connection conductors 27 and 2.
8 and further connected to a common circuit board 29. In this embodiment, the tuner circuit block is constructed to be ultra-thin, the area occupied by the common circuit board 29 can be reduced, and the number of connecting conductors 27 and 28 installed can be reduced. Needless to say, the installation relationship between the tuner circuit block and the universal circuit block is arbitrary.

FIG. 5 shows a side view of a tuner device according to another embodiment of the present invention. Tuner circuit block consisting of circuit board 20 and electrodes 21 to 24 and circuit board 2
5 and components 26 other than the tuner, the universal circuit block is connected to the common circuit board 29 by connecting conductors 32 and 33, and then the tuner The circuit blocks are adapted to be connected by connecting conductors 30 and 31. Here, the installation position of the tuner circuit block is arbitrary on the upper surface or the lower surface of the universal circuit board.

FIG. 6 shows a side view of a tuner device according to another embodiment of the present invention. The circuit board 20 and electrodes 21 to 24: the tuner circuit block and the universal circuit block comprising the circuit board 26 and components 26 other than the tuner are similar to those described in FIGS. 3 and 4, respectively. On the other hand, regarding their connection and installation,
They are arranged separately on both sides of the common circuit board 29 and connected by connection conductors 3o to 33, respectively. Here, the installation position of the tuner circuit block is arbitrary on the upper surface or lower surface of the common circuit board 29. Furthermore, the tuner circuit block is also optional.

In the case of the embodiments shown in FIGS. 6 and 6 above, the tuner circuit block can be installed in any positional relationship with respect to the universal circuit block, and the design can be designed to prevent mutual electrical interference. can.

FIG. 7 shows a side view of the structure of a cheese device in another embodiment of the present invention. Tuner circuit block consisting of circuit board 20 and electrodes 21 to 24 and circuit board 2
5 and components 26 other than the tuner are similar to those described in FIGS. 3 and 4, respectively. On the other hand, regarding their connection and installation relationship, they are distributed on one side of the common circuit board 29 and connected by connection conductors 30 to 33, respectively. Here, the installation position of each circuit block is arbitrary on the upper surface or lower surface of the common circuit board 29. In this embodiment, the thickness size can be reduced.

FIGS. 8 to 1Q show a tuner device according to another embodiment of the present invention. In each of the embodiments, a circuit board 20 and electrodes 21 to 24 form a tuner circuit block, and those shown in FIGS. ing.

Further, the circuit board 26 and the components 26 other than the tuner form a universal circuit block. In FIG. 8, it is constructed of a chip carrier type that is connected to the common circuit board 29 via the connection electrode 34. In FIG. 9, circuit boards 20 and 26 are inserted into through holes provided in a common circuit board 29 and are connected via connection electrodes 35. In FIG. 10, the respective circuit blocks are pasted together and connected via connection electrodes 36. In the case of the embodiments shown in FIGS. 8 to 10, connection can be made without using a connection conductor such as a metal pin, and the thickness size can be further reduced,
The circuit formed by the connecting conductor can be shortened.

FIGS. 11 to 18 show examples of the structure of one representative tuner section in the tuner circuit block described in FIGS. 3 to 10. In FIG. 11, a shows a front view, b shows a side view, and C shows a back view. (
12 to 18) In FIG. 11, 100 is a dielectric substrate, and 101 and 102 are electrodes forming a distributed constant circuit to realize a distributed inductor and a distributed capacitor. The ground terminals of the electrodes 101 and 102 are set so that the opposing electrodes are arranged in arbitrary directions opposite to each other as shown in FIG. (The same applies to FIGS. 12 to 18 below) A side shown in FIG. 11a,
B corresponds to side A and B shown in Figure C, respectively. (The same applies to FIGS. 12 to 18 below.) In FIG. 2, electrodes 104 and 105 each having one bent portion are placed facing each other with a dielectric substrate 103 in between.

As shown in FIG. 13, electrodes 107 and 108 having a plurality of bent portions are placed facing each other with a dielectric substrate 106 in between.

Meander-shaped electrodes 11Q and 111 are placed facing each other.

In FIG. 16, spiral-shaped electrodes 113 and 114 are placed facing each other with a dielectric substrate 112 in between.

In FIG. 16, an electrode 11 is placed on the surface of a dielectric substrate 115.
6 and 117 are installed laterally facing each other.

In FIG. 17, an electrode 11 is provided inside a dielectric substrate 118.
9 and 120 are installed facing each other.

In FIG. 18, an electrode 12 is provided inside a dielectric substrate 121.
2 is installed, and an electrode 123 is installed on the surface of a dielectric substrate 121, with the electrodes 122 and 123 facing each other.

In the embodiments shown in Figures 1 to 18 above, the electrodes that are installed oppositely or in parallel have the same shape and completely face each other, but any one electrode has a different isolateral skin compared to the other electrode. Even if you are, you can still appear. Further, the shapes of the electrodes used in the embodiments shown in FIGS. 16 to 18 can also be realized using those shown in the embodiments shown in FIGS. 11 to 15.

In each of the above embodiments, the one shown in FIG. 11 can be constructed with a simple electrode pattern, and the one shown in FIGS. 12 to 15 has a relatively large distributed inductance and distributed capacitance with a small tuner occupation area. Therefore, a tuner with a relatively low tuning frequency can be constructed, and the one shown in FIG. 16 can be easily constructed because the electrode is formed on only one side of the dielectric, The ones shown in Figures and Figure 18 are compatible with multilayer boards, and have built-in electrodes, so the performance of the tuner is less affected by external factors and can be constructed as a stable device. I'm hitting on it.

Regarding the tuner used in the tuner device in the embodiment of the present invention described above, it is also possible to operate it as a variable tuner by connecting and installing a variable reactance element. It is also possible to adjust.

Next, the operating principle of the tuner used in the tuner device of the present invention will be explained.

FIGS. 19a to 19q are circuits illustrating the operation of the tuner of the present invention. In FIG. 19a, a signal source 272 that generates a voltage e is connected to a transmission line formed by transmission line electrodes 270 and 271 having an electrical length t and whose ground terminals are set in opposite directions. It is assumed that it is connected to the transmission path electrode 270 to supply a signal. As a result, a traveling wave voltage eA is excited at the oven terminal at the tip of the transmission line electrode 270.

On the other hand, since the transmission line electrode 271 is disposed close to and opposite to the transmission line electrode 270, a voltage is induced by mutual induction. The transmission line electrode 271
Let eB be the traveling wave voltage induced in the oven terminal at the tip of .

Here, since the ground terminals of the transmission line electrodes 270 and 271 are set in opposite directions, the induced traveling wave voltage QB has an opposite phase to the excited traveling wave voltage eA. Since the tip of the transmission line is in an oven state, the respective traveling wave voltages eA and QB are
It helps to form a voltage standing wave in the transmission line made up of the transmission line electrodes 270 and 271. Here, transmission line electrode 2
If the voltage distribution coefficient indicating the distribution mode of the voltage standing wave at 70 is expressed as K, then the voltage distribution coefficient at the transmission line electrode 2 to 1 can be expressed as (1-K).

Therefore, next, if we include the potential difference ■ generated at arbitrary opposing parts of the transmission line electrodes 270 and 271, we get V = K QA (I K ) QB -'・(')
It can be expressed as Here, if each transmission line electrode 270 and 271 has the same electrical length, then the potential difference ■ in the first equation is V=K
eA+(IK)8A=eA (3). In other words, a potential difference (2) can be generated in all parts where the transmission line electrodes 270 and 271 face each other.

Here, the transmission line electrodes 270 and 271 are connected to the electrode 111.
(W) and the electrode thickness is thin).
Furthermore, it is assumed that they are opposed to each other at a distance d via a dielectric material having a dielectric constant ε8. In this case, the capacitance co formed per unit length of the transmission path is co-foot-to-day (4) Q= , eW-V (es) OB dO8
d, therefore W CO−ε0ε, T −°−(6).

Therefore, the transmission line shown in FIG. 19a becomes a transmission line including a distributed capacitor 273 of CO expressed by the formula 6 per unit length as shown in FIG. 19S. Furthermore, since the voltage standing wave distribution (or current standing wave distribution) in each transmission line electrode 270 and transmission line electrode 271 are in an antiphase relationship with each other as described above, this transmission line is isometric. It will operate as a balanced mode transmission line. This results in an equilibrium voltage e' as shown in FIG. 19C.
is equivalent to a balanced mode transmission line formed by transmission line electrodes 276 and 276 excited in a balanced mode by a balanced signal source 274 having . Needless to say, its electrical length is the same as the original electrical length t shown in FIG. 19a. Furthermore, as shown in FIG. 19d, this balanced mode transmission line has integrated distributed inductors 277 and 278 and a distributed capacitor due to the distributed inductor component of the transmission line and the lumped inductor component generated due to the bent shape of the transmission line. It can be equivalently expressed as a distributed constant circuit consisting of 273 circuits.

Next, the relationship between the formation of the distributed capacitor 273 and the electrical length t of the transmission path will be described.

The characteristic impedance ZO per unit length in a balanced mode transmission line as shown in FIG. 20a can be expressed by the equivalent circuit shown in FIG. 16. Its characteristic impedance Zo is generally as follows. Here, if the transmission path is lossless, then This assumption can be applied to many of the embodiments of the tuner of the present invention, and to simplify the explanation, the characteristic impedance Z○ shown in the following equation 8 is used. The capacitance CO in the eighth equation is the same as the capacitance co per unit in the transmission line calculated in the sixth equation. That is, the characteristic impedance ZO per unit length in the transmission line is a function of the capacitance co, which is also a function of the dielectric constant ε8° of the dielectric material involved in the capacitor co, 1 of the transmission line electrode.
] W and the installation interval d of each transmission line electrode.

As described above, the equivalent reactance X generated at the terminal of the transmission line whose characteristic impedance per unit length in the transmission line is Z□, whose electrical length is t, and whose tip is in an oven state is X = -Z( ) c o tθ (9). Here, θ-2π 2 . That is, the equivalent reactance at the terminal of the transmission line can be considered as capacitance reactance. Therefore, when θ corresponds to Equation 11 depending on the electrical length t of the transmission path, a capacitor can be formed by setting the electrical length t to λ/4 or less, for example. and,
The capacitance C of the capacitor that can be formed can be realized by changing θ, that is, by setting the electrical length t of the transmission line.

FIG. 21 is a diagram illustrating the operation mode. FIG. 21 shows how the equivalent reactance X generated at the terminal changes in accordance with the change in the electrical length t of a transmission path with the tip in an open state. As is clear from Fig. 21, when the electrical length t of the transmission line is less than λ/4 or between λ/2 and 4λ/3, it is possible to form a negative terminal reactance, that is, the equivalent Capacitors can be formed in a similar manner. Further, by arbitrarily setting the electrical length t of the transmission path under conditions that generate negative terminal reactance, it is possible to realize the capacitance C to an arbitrary value.

The capacitor C formed in this way is shown in FIG.
It can be equivalently replaced as a lumped constant capacitor 279 shown in FIG. The inductor formed by combining the distributed inductor component existing in the transmission path and the lumped inductor component generated by bending the transmission path can be equivalently replaced as the lumped constant inductor 280. Then, if the virtual balanced signal source 274 and the ground in each transmission line are replaced so that they are equivalent to the state shown in FIG. 19a, the state shown in FIG. 19f is obtained. Become. If the ground terminal is shared in this Figure 19f, the final result will obviously be as shown in Figure 19Q,
Lumped constant capacitor 279 and lumped constant inductor 2
This is equivalent to a parallel resonant circuit consisting of 80 circuits, and a tuner can be realized.

The configuration and operation described above realize the tuner of the present invention, but the configuration and operating principles of the tuner of the present invention are completely different from those of conventional tuners. .

Therefore, in order to prove that the tuner according to the present invention is completely different from conventional tuners or those having other configurations even if they use the same transmission line as the tuner of the present invention. The structure and operation of a conventional tuner or a tuner with other transmission line configurations will now be described and compared. This clarifies the difference from the tuner according to the present invention and also clarifies the novelty of the tuner according to the present invention.

FIG. 22 shows the operation when the transmission line electrode is made of the same material as that used in the tuner of the present invention, but the difference is that the ground terminals are set in the same direction. be. In FIG. 22a, a transmission line with an open end consisting of transmission line electrodes 281 and 282 is shown.
Assume that it is driven by a signal source 283 that generates voltage e. As a result, a standing wave voltage eA is excited at the open terminal at the tip of the transmission line electrode 281,
It is assumed that a standing wave voltage eB is induced in the open terminal at the tip of the transmission line electrode 282 which is disposed opposite to or in parallel with the transmission line electrode 282. Here, each transmission line electrode 281
Since the ground terminals 282 and 282 are set in the same direction, their standing wave voltages eA and eB are in phase with each other. Therefore, transmission line electrodes 281 and 28
Each voltage distribution coefficient in 2 will have the same K. As a result, the potential difference V at any portion where the transmission line electrodes face each other becomes V=KeAKeB...-64. Here, assuming that the electrical lengths of the respective transmission line electrodes 281 and 282 are the same, aA=QB, -Ql, and therefore the potential difference (■) in equation 14 is V=Kep, -KeA==Q, . ---QC9. In other words, no potential difference occurs in any part of the transmission path. Signal source 283 in Figure 22a
FIG. 22 shows a configuration in which the voltage e' is replaced at the end of the transmission line, and is equivalent to installing an unbalanced signal source 284 that generates the voltage e'. In these circuits, there are only parallel transmission lines with no potential difference between them. It is clear that this is equivalently the same as the case where only one transmission line electrode 285 exists, as shown in FIG. 22C. Then, by replacing equal parts of the signal source 283 and the ground terminal with the original circuit as shown in FIG. 22a, the circuit becomes as shown in FIG. 22d. In other words, only an equivalent lumped constant inductor 286 is formed, which is composed of a distributed inductor component of the transmission line and a lumped inductor component generated by the curved shape of the transmission line. As is clear from the above, since a capacitor cannot be formed in parallel with an inductor, the intended parallel resonant circuit tuner cannot be realized.

FIG. 23 shows a general nano-strip line formed with the same transmission line electrode as in the tuner of the present invention as one side of the transmission line electrode, but the electrode facing the transmission line electrode has a sufficiently wide ground. This shows the operation when the points are different. In FIG. 23a, a transmission line electrode 287 faces a sufficiently wide ground electrode 288, is driven by a signal source 289 that generates a voltage e, and a standing wave voltage eA is excited at the open terminal at the tip of the transmission line. Let K be the voltage distribution coefficient. on the other hand,
Assuming that a standing wave voltage eB having a voltage distribution coefficient K is virtually generated in the ground electrode 288, the potential difference (2) at any part where the transmission line electrode 287 and the ground electrode 288 face each other is V=KeAKaB −・However, the standing wave voltage eB at the earth electrode 288 is uniformly at the earth potential (zero potential) and becomes e B-0- α8).Therefore, the earth electrode 288 has a voltage distribution coefficient. As a result, the potential difference V is V = KeA-・=
・QI becomes. This makes it possible to form a distributed capacitor between the transmission line electrode 287 and the ground electrode 288. However, the transmission line electrode 287 is
8 and 8, it is equivalent to a state in which the leading edge of the image in the transmission path electrode 287 is almost short-circuited due to the mutual induction effect. Therefore, the transmission line electrode 28
This will significantly degrade the Q performance of the inductor component at 7. That is, this microstrip line includes a lumped constant inductor 291 including an equivalent loss resistance 290 and a lumped constant capacitor 29 as shown in FIG.
2 to form a parallel resonant circuit. Here, since the equivalent loss resistance 290 actually has a considerably large resistance value, the loss in the resonant circuit becomes very large. Therefore, as a tuner, the Q performance was obviously very poor.

It is only possible to realize something, and in reality, it is not suitable for practical use.

Figure 24 shows λ/4, which is the most commonly used
This figure shows the circuit configuration of the resonator and shows that it is completely different from the tuner of the present invention in terms of the conditions at the end of the transmission line, the setting of the length of the transmission line, and the setting of the ground. In FIG. 20, the balanced mode transmission line electrodes 293 and 294 have an electrical length t set equal to λ/4 at the resonance frequency, and their tips are short-circuited. It is assumed that each transmission line electrode is driven in a balanced mode by a balanced signal 295 that generates a voltage e. The ground terminal is set at the neutral point of the balanced signal source 295, and does not specifically ground any terminal in the transmission line electrode. Equivalent terminal reactance X generated at the terminal of the transmission line in this case
If the characteristic impedance of the transmission path is Zo, then X=Z()tanθ --=H. Here, the characteristic impedance ZQ is the same as that shown in the 8th equation, and θ is also the same as the first
This is the same as shown in formula 0. In this resonator, the electrical length of the transmission path is t-λ/4...Qυ, so it is 0-π/2...(2). Therefore, the terminal reactance X in the second o equation is X = 7. o12n, = oo −...−E+, and parallel resonance characteristics can be obtained on the equal side. However, when comparing the configuration of this λ/4 resonator with the configuration of the tuner of the present invention, first of all, regarding the terminal conditions of the transmission line, the tuner of the present invention is in an open state, whereas the conventional λ/4 resonator has an open state. It is clear that the /4 resonator is in a short-circuit condition and therefore has a completely different configuration in terms of terminal conditions. Furthermore, regarding the setting of the electrical length t of the transmission line, in the tuner of the present invention, it is set to λ/4 or less of the tuning frequency, and in practice it is set to a very short value of about λ/16. However, in a conventional λ/4 resonator, the resonant frequency is strictly set to λ/4, and therefore the configuration may be fundamentally different in setting the electrical length t of the transmission path. it is obvious. Furthermore, due to the difference in the electrical length t of the transmission path in the configuration, the tuner of the present invention can be made smaller even if both are designed to have the same tuning frequency or resonant frequency; In the case of four resonators, it is necessary to provide a very long transmission path, which has the disadvantage of increasing the size. In order to miniaturize the conventional λ/4 resonator, some have shortened the length of the transmission path by interposing a dielectric material with a very high permittivity, but the dielectric material with a high permittivity used for this is generally a dielectric material. There was a disadvantage that the body loss -δ was very high, and therefore the Q performance as a resonator was significantly lowered. Furthermore, the temperature dependence of the dielectric constant of a dielectric material having a high dielectric constant is generally large, and therefore, there is also the disadvantage that it is difficult to ensure the stability of the resonance frequency.

Next, in order to clarify the superiority of the performance of the tuner of the present invention, experimental results will be shown and explained in comparison with the performance of a conventional tuner. FIG. 25 is a graph showing the experimental results of measuring the temperature dependence of the tuning frequency. FIG. 26 is a graph showing the experimental results of measuring the temperature dependence characteristics of resonance Q. In FIGS. 26 and 26, characteristic A is the temperature dependence of the tuner according to the present invention, and is an experimental result when an alumina ceramic material or a resin-based printed circuit board is used as the dielectric.

On the other hand, characteristic B, as shown in FIG. 2, is a temperature dependent characteristic in a tuner that has been most commonly used in the past. From these experimental results, it is clear that in the tuner of the present invention, even if it is constructed using a general dielectric material, its tuning frequency is extremely stable, and furthermore, the resonance Q is high and it is stable. On the other hand, in conventional tuners, the tuning frequency and It was difficult to ensure the stability of resonance Q. Thereby, other temperature compensation components or other self-stabilizing compensation circuits were added to compensate for the instability.

Next, the operation of the tuner to which the voltage variable capacitance element is connected and installed in the tuner device of this embodiment will be described below. FIG. 19 shows an operational equivalent circuit of the tuner. In FIG. 27a, the grounding of electrodes 124 and 125, which are placed opposite to each other with a dielectric (not shown) interposed therebetween, are set in opposite directions, and a voltage variable capacitance element 127 is connected to an open terminal 126 of electrode 124. A basic circuit is formed as follows. Open terminal 1.2 here and now
When an AC signal is applied to the electrodes 124 and 126, since the ground terminals of the electrodes 124 and 126 are set in opposite directions, the AC currents driven to the electrodes 124 and 126 have opposite phases to each other. A distributed capacitance can be generated therebetween.

This situation is shown in FIG. 27.A distributed capacitor 128 is formed and an electrode 125 shown in FIG.
The inductive component of is canceled out and becomes equivalent to the ground plane 129. A distributed inductance exists in the electrode 124, forming a distributed inductor 130 and a distributed capacitor 128 as shown in FIG. 27C, forming a distributed constant circuit. If this is equivalently converted into a lumped constant circuit, a parallel resonant circuit of the inductor 131, capacitor 132, and voltage variable capacitance element 127 will be constructed. and voltage variable capacitance element 127
The tuning frequency of this tuner can be variably controlled by changing the tuning control voltage applied to the control terminal 133 of the tuner.

It goes without saying that a tuner, tuning component, or filter other than the tuner explained in FIG. 3 may be installed in the tuner circuit block of the tuner device in each of the above embodiments. Furthermore, metal conductors, printed thick film conductors, thin film conductors, etc. can be used as the electrodes of the tuner of the tuner device in each embodiment, and the dielectric circuit board can be alumina ceramic, chitavari, plastic, Teflon, glass, etc. Other resin-based printed circuit boards, such as mica, can also be used.

Effects of the Invention As is clear from the above description, the present invention is directed to a tuner circuit block having a tuner made of electrodes that are arranged opposite to each other via a dielectric circuit board or arranged in parallel on the surface of a dielectric, and other circuits. First, regarding the tuner in the tuner circuit block, the inductor and capacitor parts of the tuner can be integrated with a simple configuration. can be configured.

■ An ultra-thin and compact tuner can be realized.

■ Since the inductor and capacitor of the tuner are connected in a leadless manner, there is no influence of lead inductors or stray capacitors, so the operation of the tuner is extremely stable and the tuning accuracy is improved.

■ Since a modular tuner can be realized, there is no constant fluctuation of the inductor and capacitor due to mechanical vibration, and the tuning frequency is extremely stable.

■ By using a material with low temperature dependence for the dielectric circuit board, it is possible to realize a tuner whose tuning frequency is extremely stable against changes in ambient temperature.

■ It is possible to reduce the number of parts in the tuner, streamlining manufacturing and reducing costs.

Furthermore, as for the tuner device, (1) it can be made thinner as a cheese device, and the occupied area can be reduced, making it possible to realize ultra-miniaturization of the device.

■ It is possible to respond to changes in equipment specifications by simply changing the tuner circuit block, which shortens and streamlines design time.

■ Design time can be further shortened and streamlined by preparing various tuner circuit blocks in advance in anticipation of changes in equipment specifications.

■ By separating the circuit blocks of the tuning section and other circuit sections, three-dimensionally shortened and streamlined circuit connections are possible, making it possible to stabilize tuner performance.

■ The circuit board in the tuner circuit block not only has the function of simply holding components, but also has the function of forming a tuner and capacitor, making it possible to improve the added value of the circuit board and reduce the cost of the tuner device. I can do it.

Excellent effects such as these can be obtained.

[Brief explanation of drawings]

FIG. 1 is a side view of the configuration of a conventional tuner device, FIG. 2 is a perspective view of the configuration of tuner parts used in the conventional tuner device, and FIG. 3 is a side view of the configuration of a tuner device according to an embodiment of the present invention. Perspective view of the tuner circuit block used, No. 4
10 to 10 are side views of the structure of a tuner device according to an embodiment of the present invention, and FIGS. 11 to 18 are block diagrams of a tuner used in the tuner device of the present invention, in each of which a is a surface view. , b is a side view, C is a back view, Figures 19a-q, Figures 2o a and b, and Figure 21 are explanatory diagrams showing the operating principle of the tuning circuit used in the tuner device of the present invention, Figure 22a ~d, Figures 23a, b, and 24 are explanatory diagrams showing the operating principle of the conventional tuner. Figures 25 and 26 are the tuning frequency and resonance with respect to temperature changes of the tuner Q of the present invention and the conventional tuner. The characteristic diagram of Q, FIG. 27, is an explanatory diagram of the operating principle of the variable tuner used in the tuner device in the embodiment of the present invention. 15.20,25,100,103,106°109.
112, 115, 118, 121...Circuit board, 16 to 18, 20 to 24, 101゜102
．． 104, 105, 107, 108, 110°111
, 113 , 114 , 116 , 117.119゜1
20.122,123,124,125...tuner electrode, 27,28.30 to 36...-connecting conductor,
26...Cheese components other than tuner parts, 29
... Common circuit board, 127 ... Voltage variable capacitance diode. Name of agent: Patent attorney Toshio Nakao and 1 other person No. 1
Figure 2 Figure 3 Figure 7 Figure 5 Figure 6 Figure 7 Figure 8 Figure 9 Figure 10 Figure 11 (α) (b) CC) Figure 12 (α) (b) (C) Figure 13 (α) (b) (C) Figure 14 (α) (b) (c) Figure 15UgJ (a) (b) (c) @ Figure 16 (α) Cb) (C) Figure 17 (( 11-), Cb) (Fig. 18 (α) (b) ((') 1911 CI-K) 2'/6 Figure (/-K) z'/4 Figure 25 Humidity ('C) @26[lJ Humid layer ('C) Figure 27

Claims (1)

[Claims] (1) The terminals connected to the ground of the electrodes that are arranged opposite to each other with a dielectric substrate interposed therebetween or arranged in parallel on the surface of the dielectric substrate are set in opposite directions. A first circuit board on which at least one or more tuners including a tuning section are formed, and a second circuit board on which circuit components other than the tuner are mounted, and between the first and second circuit boards, respectively. A cheese device characterized in that the required circuit parts to be connected in the circuit are connected by conductors. ? ) The circuit board according to claim 1, wherein a variable reactance element is connected and installed to the tuner on the first circuit board.
equipment. (3) The tuner device according to any one of claims 1 and 2, wherein the tuning frequency is arbitrarily set by cutting a required portion of the electrode of the tuner on the first circuit board. (4) The tuner device according to any one of claims 1 to 3, wherein the first circuit board and the second circuit board are connected via a circuit conductor on a third common circuit board. (5) The tuner device according to any one of claims 1 to 4, wherein a tuner or filter other than the tuner described in claim 1 is installed on the first circuit board. (6) The cheese device according to claim 2, which uses a voltage variable capacitance diode as the variable reactance element. (The tuner device according to any one of claims 1 to 6, wherein the tuner device has at least one bending part exhibiting an arbitrary bending angle or bending rate and an arbitrary bending direction as the force electrode. (8) The cheese device according to any one of claims 1 to 6, using electrodes having a spiral shape. (9) The length of one electrode is the length of the other electrode. Claims 1 to 8 are arbitrarily set to be shorter than the length, and are installed facing each other or in parallel at any arbitrary part.
The tuner device according to any of paragraphs. 00 The tuner device according to any one of claims 1 to 9, wherein each electrode or a portion or all of one of the electrodes is installed inside a dielectric. θυ The tuner device according to any one of claims 1 to 10, wherein the respective electrodes are installed at the inner circumference and/or outer circumference of a cylindrical or prismatic dielectric body. The tuner device according to any one of claims 1 to 11, wherein the terminals connected to the ground in each of the θo electrodes are not connected to the ground but are used as a common terminal. θ葎 Claims 1 to 1 in which the variable tuning frequency range is arbitrarily set and controlled by arbitrarily cutting out a required portion of the other electrode to which the variable actance element is not connected.
The tuner device according to any one of Item 2. θ→ The cheese device according to claim 13, wherein the electrode is arbitrarily cut by a non-contact cutting means. Oo According to any one of claims 1 to 14, the variable tuning frequency range is arbitrarily set and controlled by setting a required part of the other electrode to which the variable reactance element is not connected as a terminal connected to ground. Cheesing device.