589780 五、 發 明說明 (1) 本 發明 涉 及線性放 大 器中使功率損耗降低所用 之方法 ， 其 係用 在 OFDM 放 大 器中。此外，本發明涉及 重疊之 正 弦 信號 放 大時所 用 之 相關裝置，其具有至少一 個末端 級 〇 例 如， 在 PLC(P 〇 wer L i n e C a r r i e 1·)技術中放大 所謂 OFDM(Orthogonal Fr eq uency Division Multiplex! ng)信 號 時 ，會 發 生已重 疊 之 正弦信號之放大問題。這 些信號 具 有 高的 頂 端（cres Λ)因 素，其可標示尖峰値及有 效値所 形 成 之比 (ratio) 〇 先 前技 藝 中使用 線 性放大器或時脈驅動之放大 器。特 殊 之 時脈 驅 動之放 大 器 理論上可以無損耗之方式 來操作 1 其 在低 its 頻 時之損 耗 較 線性放大器中者小很.多。 在高頻 時 切 換損 耗 當然會 大 大 地提局，因此由某一頻率 開始就 總 損 耗而 言 即不再 具 有 優勢。反之，線性放大器 可對輸 出 電 壓進 行 調整， 使 電 源電壓及該閥上之輸出電 壓（即 ， 輸 出電 晶 體上之 電 壓 )之間之差下降。因此可 達成一 種 損 耗功 率 ，其在 輸 出 電流固定時隨著輸出電壓 之下降 而 上 操 控性較 小 時 效率大大地下降。若待放 大之信 號 具 有一 種 高的頂 端 (c rest)因素時，則對效率是 不利的 y 此 乃因 放大器之 電 源 電壓須設計在尖峰値處， 但平均 而 言 只需 - 種小很 多 之 輸出電壓，於是在輸出閥 上會產 生 一 種高 的 電壓降 0 本 發明 之 目的是 提 供 一種較佳之方法使放大器 中之功 率 損 耗下 降 ，其特 別 可 用來放大及/或計算OFDM信號 -3-589780 V. Description of the invention (1) The present invention relates to a method for reducing power loss in a linear amplifier, which is used in an OFDM amplifier. In addition, the present invention relates to a related device used in the amplification of overlapping sinusoidal signals, which has at least one end stage. ! ng) signal, the problem of amplification of sinusoidal signals that have overlapped will occur. These signals have a high crest Λ factor, which can indicate the ratio of the peaks and effective peaks. 〇 In the prior art, linear amplifiers or clock-driven amplifiers were used. Special clock-driven amplifiers can theoretically operate in a lossless manner. 1 Their losses at low frequencies are much smaller than those of linear amplifiers. At high frequencies, switching losses will of course be greatly improved, so the total loss from a certain frequency will no longer have an advantage. On the contrary, the linear amplifier can adjust the output voltage to reduce the difference between the power supply voltage and the output voltage on the valve (that is, the voltage on the output transistor). Therefore, a loss power consumption rate can be achieved. When the output current is fixed, the efficiency is greatly reduced when the controllability is small as the output voltage decreases. If the signal to be amplified has a high c rest factor, it is detrimental to the efficiency. This is because the power supply voltage of the amplifier must be designed at the peak, but on average only a small output is needed. Voltage, so a high voltage drop will be generated on the output valve. The object of the present invention is to provide a better method to reduce the power loss in the amplifier, which is particularly useful for amplifying and / or calculating OFDM signals.
589780 五、 發明說明 ( 2〕 J 本 發 明 亦 涉 及 相 關 之 裝 置 〇 本 發 明 中 上 述 冃 的 以 串 請 專 利 範 圍第 1 項 之措 施 及 第 5 、6 項所 述 之 相 關 丨裝 置 來 :達 :成 〇 本 :方法 ;及 .相 丨關之 ，裝 :置 :之 其 它 形 式 描 述 在各 附 屬 項 中 〇 利 用 本 發 明 > 可 以 下 述 方 式使 損 耗功 率 最 小化 : 不 是 在 整 個 控 制 中 利 用 相 同 之 末 端 級 來放 大 而是 在 至 少 二 個 部 份 區 ( 其 間 溫 和 地 改 變 ) 中 放大 0 這 亦可 以 各 別 之 可 分 離 之 末 丄山 觸 級 來 進 行 > 但 亦 能 以一 種 可 分離 地 連 接 至 不 同 之 電 源 電 壓 之 末 丄山 聰 級 來 進 行 。結 果 是 可使 末 端 級- 閥 上 之 電 壓 降 減 低 〇 這 樣 亦 可使 損 耗功 率 降 低。 本 發 明 中 以 有 利 之 方 式 來 劃 分 各 別所 需 之 動態 區 其 中 在各 別 之 部 份 區 之 間 之 邊 界 1¾ 中 平滑 地 ( 即， 溫 和 地 ) 改 變 0 特 殊 之 轉 移 (transition)失 真因 此 可保持很小 〇 整 體 而 言 效 率 可 明 顯 地 增 大 例 如 ，在 以 二 個末 丄山 m 級 來 進 行 時 效 率 大 約 成 爲 二 倍 〇 本 發 明 之 其 它 細 節 及 優 點 以 下 將 依據 圖 式 來詳 述 〇 圖 式 簡 單 說 明 ； 第 1 圖 理 想 之 線 性放 大 器 之 末 端 級。 第 2 圖 理 想 之 線 性放 大 器 之 功 率 及效 率 0 第 3 圖 具 有 多 個 電 源 電 壓 之 可分 離之 放 大 器之 末 端 級 〇 第 4 圖 — 種 可分 離 之 放 大 器 之 末 端級 ， 其 以轉 換 器 及 反 時 脈 來 操 作 〇 第 5 圖 種 可 分 離 之 放 大 器 4- 之 末 端級 其 電源 電 壓 可 589780 五、發明說明（3) 再調整。 第6圖OFDM丨目號之結構。 第7圖溫和地改變時電流之分佈圖。 第8圖正弦信號中一種溫和之變化。 第1圖中一種未詳細顯示之線性放大器1之末端級以 1 〇表示。末端級1 〇以二個相耦合之電晶體11、1 2構成 ，一種負載阻抗1 3連接至電壓U a之接點。此種末端級 提供+Us及-Us之間之電壓且與電流閥形成一種放大器 〇 利用此種放大器，特別是可使所謂具有大約是4之頂 端（crest)因素之OFDM信號被放大。OFDM是一種特別 適用於所謂PLC (Power Line Communication)技術之調變 方法。OFDM信號例如位於40至l5〇KHz之傳輸帶中， 因此，以時脈驅動之放大器較不適用於此目的中。 第2圖是線性放大器之功率P及效率7?作爲振幅A之 函數時之圖解。曲線26表示輸入功率Pin且曲線27表 示輸出功率P^t，它們分別是一種連續之函數。效率7? 以曲線2 8表示，其是一種線性上升形式。 依據曲線2 8例如在8 0%之控制區中效率是在6 0 %之 數量級中。若考慮各種損耗，例如，控制上之損耗，傳 輸時之歐姆損耗或類似情況等，則在正弦信號時效率最 大時大約50%。在具有頂端因數是4之OFDM信號（其 平均控制率因此是30%)中，該線性放大器之效率只有 2 0%至3 0%。這可以第3圖之配置來大大地改良。589780 V. Description of the invention (2) J The present invention also relates to related devices. The above-mentioned invention in the present invention is related to the measures in item 1 of the patent scope and the related devices described in items 5 and 6. 〇 This: methods; and. Related: Equipment: Other forms are described in each subsidiary item. Using the present invention > The loss power can be minimized in the following way: Instead of using the same end in the entire control Level to zoom in but to zoom in 0 in at least two partial regions (with mild changes during this time). This can also be done with separate separable end points. But it can also be detachably connected to different At the end of the power supply voltage, it is carried out by Satoshi Yamashita. As a result, the voltage drop at the end stage-the valve can be reduced. This can also reduce the power loss. In the present invention, the respective needs are divided in an advantageous manner. The dynamic zone where the boundary 1¾ between the individual partial zones changes smoothly (ie, gently). The special transition distortion can thus be kept small. Overall, the efficiency can be significantly increased, for example, The efficiency is approximately doubled when it is performed with two end-stage m stages. Other details and advantages of the present invention will be described in detail with reference to the diagrams. The diagrams are briefly explained; Fig. 1 is the ideal end stage of a linear amplifier. Figure 2 Power and efficiency of an ideal linear amplifier 0 Figure 3 Terminal stage of a separable amplifier with multiple supply voltages Figure 4-Terminal stage of a separable amplifier with a converter and anticlockwise Let's operate. The fifth stage of the separable amplifier 4- can have a power supply voltage of 589780. 5. Description of the invention (3) Re-adjust. Figure 6 Structure of the OFDM number. Figure 7 shows the current distribution when the temperature changes gently. Figure 8 A gentle change in the sinusoidal signal. The end stage of a linear amplifier 1 which is not shown in detail in Fig. 1 is indicated by 10. The end stage 10 is composed of two coupled transistors 11, 12 and a load impedance 13 is connected to the contact of the voltage U a. This end stage provides a voltage between + Us and -Us and forms an amplifier with the current valve. Using this amplifier, in particular, the so-called OFDM signal with a crest factor of about 4 can be amplified. OFDM is a modulation method particularly suitable for so-called PLC (Power Line Communication) technology. OFDM signals are located, for example, in a transmission band of 40 to 150 KHz, so clock-driven amplifiers are less suitable for this purpose. Figure 2 is a diagram of the power P and efficiency 7? Of the linear amplifier as a function of amplitude A. Curve 26 represents the input power Pin and curve 27 represents the output power P ^ t, which are each a continuous function. Efficiency 7? Is represented by curve 2 8 which is a linear rise. According to the curve 28, for example, the efficiency is in the order of 60% in a 80% control region. If various losses are considered, for example, control loss, ohmic loss during transmission, or the like, the maximum efficiency is approximately 50% when the sinusoidal signal is used. In an OFDM signal with a top factor of 4 (the average control rate is therefore 30%), the efficiency of the linear amplifier is only 20% to 30%. This can be greatly improved by the configuration of Fig. 3.
五、發明說明（4) 第3圖是一種可分離之放大器，其由第1圖之末端級 1 〇及另一末端級2 0所構成，此二者組合成一種負載。 OFDM信號中線性放大器效率惡化之原因是一種平均 而言很小之控制率。因此會產生很多損耗功率，此乃因 電源電壓須依該信號之尖峰値來設計且對電晶體上之輸 出信號之以電壓降來表示之差須消除。反之’若依據第 3圖設有二個末端級1 〇及20，則可設有不同之電源電 壓且可使各末端級能以最佳之效率在不同之振幅範圍中 操作。 這在第3圖中表示：級1至Ub 1是在接合狀態且在此 區域中該級2截止。損耗功率因此由（Ub 1 -UA)所決定。 反之，若輸出電壓大於Ubl (例如，直至Ub2 )，則級 1進入飽和區且級2被驅動。 利用第3圖之電路，則OFDM信號中該效率可由25% 提高至5 0%。情況需要時可另外藉由其它之末端級對控 制區作相對應之劃分使效率進一步提高，在此種情況下 當然須以較高之耗費來操作。 模擬計算及實驗上之探討已顯示：利用線性放大器（ 其具有第3圖所示之二個末端級，特別是用於OFDM信 號中）可達成一種依問題來調整之放大作用。 第4圖是第3圖之末端級以輸出轉換器來操作時之另 一種形式，其以推挽方式（push-pull)來操作，其具有二 個末端級10、20，各具有電晶體1 1、12及21、22以作 爲電流閥，其中各電晶體Π、1 2及2 1、22分別配置在 589780 五、發明說明（5) 推挽式電路中。各電晶體1 1、1 2或2 1、22經由繞組4 1 、42、43、44而連接至電源電壓+Ub，其中二次繞組未 顯示在第4圖中。 以不同之插栓（tap)來進行推挽式操作，則只以一種電 源電壓即可進行一種可分離之操作。轉換器之其它優點 是：不同之轉換比（ratio)及不同之分離極限只可藉由轉 換器之修改來選取而不必改變該放大器。在0FDM信號 模擬時ni = 1:1對效率而言是一種很好之値。此種方 式被歸列爲是有效的且在詳細模擬時將繼續探討。 藉由電源電壓之再調整，則第4圖之形式對放大器而 言可具有更好之效率。電源電壓可適當地改變或固定地 保持在不同之値。 第5圖是第4圖中一種具有轉換器之推挽式末端級。 轉換器上之電源電壓可選擇式地由Ub 1導出或經由電晶 體53而由較高之電壓Ub2導出。Ubl因此經由二極體 5 1及第4圖之繞組而接通，電晶體5 3則由一調整電路 52 (其由電晶體1 1及2 1獲得各實際信號）所控制。 在製備一適當之電源電壓之此種過程中，須使用該電 壓Ub 1 —段期間，直至末端級電晶體1 1及2 1進入飽和 狀態且集極-射極-電壓低於一預設之値爲止。然後藉由 該調整電路52經由電晶體53來對電源電壓進行再調整 ，使集極-射極-電極不低於該極限値。 因此，利用第5圖同樣可使較小振幅之區域可由Ub 1 所覆蓋。較小之損耗藉由較高之控制率而達成。較大振 五、發明說明（6) 幅之區域中可使用較高之電壓Ub2。此種再調整又可溫 和地（即，以一種由U b 1至U b 2之流動式變化）進行。 爲了進一步說明問題之解法，第6圖中顯示〇fdM信 號在50ms時段中之變化情形。此信號結構以丨⑽表示 且各別之電壓尖端以105表示。 由第6圖可知：在信號結構1 00中分別存在1 2ms期 間之信號封包（packet)，其亦可以時框（frame)來表示。 在該時框區域中存在著不同振幅之信號，其中各別之信 號尖峰由各正弦信號之疊加所形成。各信號之頻率典型 上是在40KHz至數個ΙΟΟΚΗζ之範圍中偏移，例如，在 5 0KHz及150KHZ之範圍中偏移。各信號具有不利之頂 端（crest)因素，其定義成尖峰電壓對有效電壓之比，己 如上所述。整體而·言，第6圖顯示各信號之包封線 (envelope) 〇 由於各別尖峰之不同之振幅（其在縱座標中以0 %至 100%來表示），則須使用一種可對特定成份放大之放大 器，特別是第3至5圖中具有可分離性之放大器是適當 的。依據第7、8圖來說明此種新OFDM放大器之操作 方式。 第7圖中橫軸是總電流（作爲信號振幅用之準則）且 縱軸是二級式放大器中各閥上之電流分佈。在信號振幅 之方向中存在著各個互相接續之動態區1 1 〇及1 20。在 正常情況時，各放大器互相對應地設有其各自之閥。 在新的OFDM放大器中，在動態區1 10中各別之電流 589780 五、發明說明（7) 1 1 1在第一閥中由〇%上升至40%，然後下降且在60%向 0接近。電流成份120在40%時由0上升且在大約60% 時倂入信號曲線1 2 1中。各閥之電流在重疊區中相加， 因此可確保一種平滑（已如上所述）之〃溫和〃之改變 〇 動態區之邊界例如只以凸出形式來表示。其它値亦是 可能的且可依特定問題來調整。 由於各別之信號尖峰1 05分別由正弦波之重疊所形成 ，則可依據第8圖來描述正弦半波函數之〃溫和〃之變 化。第8圖是正弦半波函數對時間（任意單位）之曲線 圖（週期=100)，其中縱座標已依據第7圖來校準。可 辨認的是：正弦半波之起始及末端分別存在一種信號 101，其首先對應於正弦半波而上升，然後在40%時又 下降，在此區域中電流由第二閥所承擔，其中形成該信 號102。藉由疊加而產生該尖峰105以成爲正弦半波。 以相同方式形成該負的半波。 總之，由第6至8圖之詳述中可知：第3至5圖之放 大器分別具有可分離之二個部份區之特性且特別適用於 OFDM信號，若提供一種平滑（即，溫和）之改變時。 因此，重要的是：OFDM信號結構由較高頻率之正弦波 之疊加所形成。上述之放大器特別適用於PLC技術領域 中。 符號說明 1…放大器 ___^ 589780 五、發明說明（8) 1 〇…末端級 1 1 ' 12…電晶體 1 3…負載阻抗 2 0…第二末端級 21、22…電晶體 26、27··· Pin、Pout 之特性曲線 28…特性曲線 5 1…截止二極體 52···調整電路 53…電晶體 100··· OFDM 信號 101…閥1之電流 102…閥2之電流 105…信號尖峰 1 10…動態區1 1 1 1…閥1電流之相對成份 1 12…閥2電流之相對成份 120…動態區2 150…溫和變化之區域 土Ubl…第一級之電源電壓 土Ub2…第二級之電源電壓 -10V. Description of the Invention (4) Figure 3 is a separable amplifier, which is composed of the end stage 10 and the other end stage 20 of Fig. 1, which are combined into a load. The reason for the degradation of linear amplifier efficiency in OFDM signals is an average control rate that is small. Therefore, a lot of loss power will be generated. This is because the power supply voltage must be designed according to the peak value of the signal and the difference expressed by the voltage drop of the output signal on the transistor must be eliminated. On the contrary, if two end stages 10 and 20 are provided according to FIG. 3, different power supply voltages can be provided and each end stage can operate in different amplitude ranges with the best efficiency. This is shown in Figure 3: Stages 1 to Ub 1 are in the engaged state and Stage 2 is off in this region. The power loss is therefore determined by (Ub 1 -UA). Conversely, if the output voltage is greater than Ubl (for example, up to Ub2), stage 1 enters the saturation region and stage 2 is driven. Using the circuit in Figure 3, the efficiency in an OFDM signal can be increased from 25% to 50%. When the situation requires, the control zone can be further divided by other end stages to further increase the efficiency. In this case, of course, it is necessary to operate with a higher cost. Simulation calculations and experimental discussions have shown that the use of a linear amplifier (which has the two end stages shown in Figure 3, especially for OFDM signals) can achieve a magnification effect adjusted according to the problem. Fig. 4 is another form when the end stage of Fig. 3 is operated by an output converter. It operates in a push-pull mode. It has two end stages 10, 20, each having a transistor 1 1, 12 and 21 and 22 are used as current valves, in which the transistors Π, 12 and 2 1, 22 are respectively arranged in 589780 V. Description of the invention (5) Push-pull circuit. Each transistor 1 1, 12 or 2 1, 22 is connected to a power supply voltage + Ub via a winding 4 1, 42, 43, 44, and the secondary winding is not shown in the fourth figure. For push-pull operation with different taps, a separable operation can be performed with only one power supply voltage. Another advantage of the converter is that different conversion ratios and different separation limits can only be selected by modifying the converter without having to change the amplifier. In the 0FDM signal simulation, ni = 1: 1 is a good idea for efficiency. This approach is classified as effective and will be explored in the detailed simulation. By readjusting the power supply voltage, the form of Figure 4 can have better efficiency for the amplifier. The power supply voltage can be changed appropriately or fixedly maintained at different levels. Figure 5 is a push-pull end stage with a converter in Figure 4. The power supply voltage on the converter is optionally derived from Ub 1 or higher voltage Ub2 via the electric crystal 53. Ubl is therefore switched on via the windings of diode 51 and Fig. 4, and transistor 53 is controlled by an adjustment circuit 52 (which obtains actual signals from transistors 11 and 21). In such a process of preparing a suitable power supply voltage, the voltage Ub 1 must be used for a period of time until the end-stage transistors 1 1 and 21 are in a saturated state and the collector-emitter-voltage is lower than a preset So far. Then, the power supply voltage is readjusted by the adjustment circuit 52 through the transistor 53 so that the collector-emitter-electrode is not lower than the limit 値. Therefore, Ub 1 can also be used to cover the smaller amplitude area by using Figure 5. Smaller losses are achieved with higher control rates. Larger V. Invention description (6) The higher voltage Ub2 can be used in the area of (6). This readjustment can again be carried out gently (i.e., in a mobile variation from U b 1 to U b 2). To further illustrate the solution to the problem, Figure 6 shows how the 0fdM signal changes during a 50ms period. This signal structure is represented by 丨 ⑽ and the respective voltage tip is represented by 105. It can be seen from FIG. 6 that there are signal packets with a period of 12 ms in the signal structure 100, which can also be represented by a frame. There are signals with different amplitudes in the time frame area, and the respective signal spikes are formed by the superposition of the sinusoidal signals. The frequency of each signal is typically offset in the range of 40KHz to several 100KHz, for example, in the range of 50KHz and 150KHZ. Each signal has an adverse crest factor, which is defined as the ratio of the peak voltage to the effective voltage, as described above. Overall, Figure 6 shows the envelope of each signal. Because of the different amplitudes of the individual spikes (which are represented by 0% to 100% in the ordinate), you must use a Component amplification amplifiers, especially those with separability in Figures 3 to 5, are suitable. The operation of this new OFDM amplifier will be described with reference to Figs. In Figure 7, the horizontal axis is the total current (as a guideline for signal amplitude) and the vertical axis is the current distribution across the valves in the two-stage amplifier. In the direction of the signal amplitude, there are successive dynamic zones 1 1 0 and 1 20. Under normal conditions, each amplifier is provided with its own valve corresponding to each other. In the new OFDM amplifier, the respective currents in the dynamic zone 1 10 589780 V. Description of the invention (7) 1 1 1 In the first valve, it rises from 0% to 40%, then decreases and approaches 0 at 60%. . The current component 120 rises from 0 at 40% and enters the signal curve 1 2 1 at approximately 60%. The currents of the valves are added in the overlapping area, so a smooth (already described above) change of 〃 mild 〃 is ensured. 〇 The boundaries of the dynamic zone are, for example, only expressed in convex form. Other slugs are possible and can be adjusted to specific issues. Since the respective signal spikes 105 are formed by the overlap of sine waves, the changes in 〃 mildness and 〃 of the sine half-wave function can be described according to Figure 8. Figure 8 is a plot of the sine half-wave function versus time (in arbitrary units) (period = 100), where the vertical coordinate has been calibrated according to Figure 7. It is identifiable that there is a signal 101 at the beginning and the end of the sine half wave, which first rises corresponding to the sine half wave and then decreases at 40%. In this area, the current is borne by the second valve, where This signal 102 is formed. This spike 105 is generated by superposition to become a sine half wave. This negative half wave is formed in the same way. In summary, from the detailed description of Figures 6 to 8, the amplifiers of Figures 3 to 5 have the characteristics of two separate regions that are separable and are particularly suitable for OFDM signals. If a smooth (ie, mild) When changing. Therefore, it is important that the OFDM signal structure is formed by the superposition of sine waves at higher frequencies. The aforementioned amplifiers are particularly suitable for use in the field of PLC technology. Explanation of symbols 1 ... Amplifier ___ ^ 589780 5. Description of the invention (8) 1 〇 ... End stage 1 1 '12 ... Transistor 1 3 ... Load impedance 2 0 ... Second end stage 21, 22 ... Transistor 26, 27 ... ·· Characteristic curve 28 of Pin and Pout · Characteristic curve 5 1 · Cut-off diode 52 ·· Adjusting circuit 53 · Transistor 100 ··· OFDM signal 101 ... Valve 1 current 102 ... Valve 2 current 105 ... Signal Spike 1 10 ... Dynamic area 1 1 1 1 ... Relative component of valve 1 current 1 12 ... Relative component of valve 2 current 120 ... Dynamic area 2 150 ... Moderately changing area Ubl ... First-level power supply voltage Ub2 ... Secondary power supply voltage -10