US5978365A - Communications system handoff operation combining turbo coding and soft handoff techniques - Google Patents

Communications system handoff operation combining turbo coding and soft handoff techniques Download PDF

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Publication number
US5978365A
US5978365A US09/110,395 US11039598A US5978365A US 5978365 A US5978365 A US 5978365A US 11039598 A US11039598 A US 11039598A US 5978365 A US5978365 A US 5978365A
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Prior art keywords
receiver
handoff
digital
mobile
code
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English (en)
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Byung Kwan Yi
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LG Electronics Inc
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Orbital Sciences LLC
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Assigned to ORBITAL SCIENCES CORPORATION reassignment ORBITAL SCIENCES CORPORATION ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: YI, BYUNG KWAN
Priority to US09/110,395 priority Critical patent/US5978365A/en
Priority to KR10-2001-7000239A priority patent/KR100370425B1/ko
Priority to EP99935426A priority patent/EP1095529B1/de
Priority to AU50907/99A priority patent/AU749517B2/en
Priority to DE69939261T priority patent/DE69939261D1/de
Priority to JP2000558683A priority patent/JP3671149B2/ja
Priority to BRPI9912256A priority patent/BRPI9912256B1/pt
Priority to CNB99808316XA priority patent/CN1154383C/zh
Priority to PCT/US1999/015223 priority patent/WO2000002404A1/en
Priority to US09/377,701 priority patent/US6094427A/en
Publication of US5978365A publication Critical patent/US5978365A/en
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0076—Distributed coding, e.g. network coding, involving channel coding
    • H04L1/0077—Cooperative coding
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/24—Radio transmission systems, i.e. using radiation field for communication between two or more posts
    • H04B7/26—Radio transmission systems, i.e. using radiation field for communication between two or more posts at least one of which is mobile
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
    • H03M13/00—Coding, decoding or code conversion, for error detection or error correction; Coding theory basic assumptions; Coding bounds; Error probability evaluation methods; Channel models; Simulation or testing of codes
    • H03M13/63—Joint error correction and other techniques
    • H03M13/635—Error control coding in combination with rate matching
    • H03M13/6362—Error control coding in combination with rate matching by puncturing
    • H03M13/6368—Error control coding in combination with rate matching by puncturing using rate compatible puncturing or complementary puncturing
    • H03M13/6381—Rate compatible punctured turbo [RCPT] codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/14—Relay systems
    • H04B7/15—Active relay systems
    • H04B7/185—Space-based or airborne stations; Stations for satellite systems
    • H04B7/1853—Satellite systems for providing telephony service to a mobile station, i.e. mobile satellite service
    • H04B7/18539—Arrangements for managing radio, resources, i.e. for establishing or releasing a connection
    • H04B7/18541—Arrangements for managing radio, resources, i.e. for establishing or releasing a connection for handover of resources
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0045—Arrangements at the receiver end
    • H04L1/0047—Decoding adapted to other signal detection operation
    • H04L1/005—Iterative decoding, including iteration between signal detection and decoding operation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0064—Concatenated codes
    • H04L1/0066—Parallel concatenated codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0067—Rate matching
    • H04L1/0068—Rate matching by puncturing
    • H04L1/0069—Puncturing patterns
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/20—Arrangements for detecting or preventing errors in the information received using signal quality detector
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L2001/0092—Error control systems characterised by the topology of the transmission link
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W36/00—Hand-off or reselection arrangements
    • H04W36/0005—Control or signalling for completing the hand-off
    • H04W36/0055—Transmission or use of information for re-establishing the radio link
    • H04W36/0069—Transmission or use of information for re-establishing the radio link in case of dual connectivity, e.g. decoupled uplink/downlink
    • H04W36/00692—Transmission or use of information for re-establishing the radio link in case of dual connectivity, e.g. decoupled uplink/downlink using simultaneous multiple data streams, e.g. cooperative multipoint [CoMP], carrier aggregation [CA] or multiple input multiple output [MIMO]

Definitions

  • the present invention relates to communications systems. More specifically, the present invention relates to a novel and improved system for providing communications with a mobile station during a handoff between cell base stations or sectors thereof or between satellite beams and/or between satellites.
  • the present invention combines a soft handoff mechanism with code diversity combining techniques, packet diversity combining techniques, and an iterative decoding algorithm (known as turbo coding).
  • the system operates in either a code division multiple access (CDMA), frequency division multiple access (FDMA) or time division multiple access (TDMA; communications system.
  • CDMA code division multiple access
  • FDMA frequency division multiple access
  • TDMA time division multiple access
  • the second base station can either be on a second satellite or can be associated with a second antennae on the first satellite which services a second beam (geographic region).
  • base station refers to a fixed base station on the ground or a base station provided on board an orbiting satellite.
  • a hard handoff is characterized by a temporary disconnection of the forward and reverse channels and is typical in an FDMA or TDMA environment.
  • the received signal becomes weak and a handoff is required.
  • the communications system switches the communications session to a new channel while the session continues.
  • the receiver in the mobile unit stops demodulating and decoding information transmitted on the old channel link, from the cell or satellite link initially servicing the session, and then starts demodulating and decoding information transmitted via a second channel link.
  • the handoff scheme implemented is intended to allow a call to continue when a mobile telephone crosses the boundary between cells. Then handoff from one cell to another is initiated when the receiver in the cell base station handling the call notices that the received signal strength from the mobile station falls below a predetermined threshold value.
  • a low signal to noise ratio indication implies that the mobile telephone is on the cell boundary.
  • the base station asks the system controller to determine whether a neighboring base station received the mobile signal with better signal strength than the current base station.
  • the system controller in response to the current base station's inquiry sends messages to the neighboring base stations with a handoff request.
  • the base stations neighboring the current base station employ scanning receivers which receive the signal from the mobile station on the specified channel.
  • a handoff will be attempted once one of the neighboring base stations reports an adequate signal level to the system controller. This scenario is called a "base station initiated handoff process.” Handoff is then initiated when an idle channel from the channel set used in the new base station is selected. A control message is sent to the mobile station commanding it to switch from the current channel to the new channel. At the same time, the system controller switches the call from the first base station to the selected base station. In the conventional FDMA or TDMA system, a call will be dropped if the handoff of the new base station is unsuccessful. There are several reasons that a failure in handoff may occur.
  • a handoff can fail if there is no idle channel available in the neighboring cells with proper signal strength.
  • a handoff can also fail if another base station reports hearing the mobile station in question, when in fact, the base station actually hears a different mobile station using the same channel in a completely different cell.
  • break before connect Because a hard handoff is completed by a temporary disconnection of the traffic channel, information in the received signal may be lost.
  • the soft handoff (as used in a CDMA environment) alleviates the problem of the temporary disconnection.
  • a soft handoff two or more received signals through different cells or satellites are simultaneously demodulated, combined, and decoded by the same receiver unit. Because the CDMA environment enables the receiver to simultaneously demodulate, combine and decode signals from more than one base station, the soft handoff does not require any disconnection of the traffic channels.
  • a user moving into the service area of another base station or satellite beam does not need to change its receiving or transmitting frequency.
  • a soft handoff is characterized by initiating communications using a new code sequence (i.e., with a new base station at a new cell or satellite) on the same CDMA frequency before terminating communications with the old code sequence.
  • a typical CDMA soft handoff is implemented by diversity combining (i.e., combining signals from either the same or different base stations) in conjunction with a RAKE receiver, thereby providing better call reliability than a hard handoff and supporting the handoff process between cells or beams in a manner that is transparent to the user.
  • the mobile initiated handoff method is different from the base station initiated handoff method.
  • the mobile initiated handoff relies on the mobile station to detect the presence or absence of pilot signals and the signal strength of the pilot signals.
  • the mobile station is equipped with a search receiver to scan pilot signals from other base stations.
  • One reason to employ a mobile initiated handoff method is that the mobile station is more sensitive than base stations to changes in path between itself and various neighboring base stations.
  • CDMA-to-CDMA hard handoff In a conventional CDMA system, two types of handoff operations are implemented; the soft handoff and CDMA-to-CDMA hard handoff.
  • the CDMA-to-CDMA hard handoff is similar to that of the TDMA or FDMA system, and call interruption may occur. It may be helpful in understanding the problems with existing systems to consider a CDMA and its soft handoff procedures in somewhat more detail.
  • the mobile station initiates the handoff process.
  • the mobile station performs the signal diversity combining to/from multiple base stations.
  • the mobile station employs RAKE receivers to receive communications simultaneously from the multiple base stations.
  • a soft handoff occurs when the mobile station is communicating simultaneously with two or more base stations or with two or more sectors of the same base station before communications with the previous base station or sector is dropped. The latter case (i.e., between sectors within a cell) is called a "softer handoff". This is a special type of soft handoff, and no distinction is made herein between a soft and a softer handoff.
  • the call between a mobile station and an end user is not interrupted by the eventual handoff from the base station corresponding to the cell from which the mobile station currently is being serviced to the base station corresponding to the cell from which the mobile station is to receive services.
  • FIGS. 1-3 depict a conventional CDMA system.
  • the diversity combiner receiver of the CDMA system at the mobile receiver includes a diplexer feeding a front end analog receiver 101, which supplies signals to multiple digital RAKE receivers 102A, 102B, 102C and to a searcher receiver 103.
  • the receivers provide data to a diversity combiner 104.
  • the output of the diversity combiner is connected to a decoder 105. If the mobile unit provides telephone service, the decoder supplies signals through base band processing circuitry and a vocoder, to provide signals to drive the handset speaker.
  • the diversity combiner receiver of the conventional CDMA system at the base station has the same configuration as the mobile station except for the diplexer and the number of front end antennae and receivers.
  • two receiver systems are used for antenna diversity reception. These two systems independently receive the same CDMA signals and are combined at the diversity combiner 204.
  • antennae 200A, 200B separately receive a signal from the mobile station, and each antenna supplies the signal to an analog receiver 201.
  • the analog receiver is followed by multiple RAKE receivers 202A and 202B and a searcher receiver 203.
  • the RAKE receivers 202A, 202B output the signals to a diversity combiner 204.
  • the signal is then decoded in decoder 205.
  • the base station forwards the decoded reverse channel information over a digital link to a master switching center (MSC).
  • MSC master switching center
  • FIG. 3 depicts the operation of the diversity combiner 104 or 204 in either the mobile station or the base station.
  • the diversity combiner utilizes a maximal ratio combiner.
  • the combiner first applies a specific weighted-signal-to-noise-ratio at 301A, 301B, 301C (which is based on their measured signal strength) to the incoming data signals from the individual receivers, here represented generically by receivers 302A, 302B, 302C.
  • the diversity combiner then combines these weighted signals in the adder 303.
  • the diversity combining scheme is termed "a maximal ratio combiner.”
  • the combining is coherent, since pilot signal demodulation allows aligning of multiple streams of received signals.
  • the resulting combined signal is then decoded by decoder 304 using forward error correction.
  • the conventional forward error correction uses the convolutional code with an appropriate Viterbi algorithm decoder.
  • An exemplary conventional CDMA cellular system uses convolutional codes. Such a system has a code rate of 1/2 for the forward link from a base station to a mobile station and a code rate of 1/3 for the reverse link from a mobile station to the base station.
  • the conventional call processing operations during a soft handoff from base station A to base station B include the following:
  • the mobile station served by base station A scans and measures potential pilot signals for two or more base stations.
  • the mobile receiver detects the pilot signal from base station B which exceeds a predetermined threshold level.
  • the mobile station sends a pilot strength measurement message to base station A.
  • Base Station A receives the pilot strength measurement message and relays the message to base station B through the Master Switching Center.
  • Base station B begins transmitting the same traffic for the particular mobile station on the forward channel as that transmitted by base station A and acquires the reverse traffic channel from the mobile station.
  • Base stations A and B each send a handoff direction message to the mobile station to start demodulating signals from A and B.
  • the mobile station receives the handoff direction messages, acquires and demodulates the signal from base station B and begins diversity combining the signals from base stations A and B.
  • the mobile station sends a message to both base stations A and B informing both base stations that it is receiving signals from them both.
  • the mobile station sends a pilot strength measurement message to base stations A and B. If a signal from a base station remains below a predetermined threshold value for a predetermined amount of time (i.e., the period of the handoff Drop Timer), the signal from that base station will be dropped from the set of signals being processed by the mobile station as described in steps 10-13.
  • the base stations A and B send a handoff direction message to use only B to the mobile station.
  • the mobile station sends the handoff completion message to the base stations A and B informing the base stations that it will stop receiving signals from base station A.
  • the mobile station receives the handoff direction message, stops diversity combining and begins demodulating signals from base station B only.
  • base station A stops transmitting on the forward traffic channel of the mobile station and receiving on the reverse traffic channel.
  • the mobile station initiated handoff method provides more reliable handoff and increased system performance than the base station initiated handoff.
  • Diversity combining at the mobile station receiver of signals from multiple base stations in conjunction with the RAKE receiver allows the mobile receiver to receive multiple copies of the same CDMA signal from different base stations and multiple copies of the same signal from each base station.
  • the softer handoff which is one special case of the soft handoff operation, occurs when a mobile station is moving from one sector coverage to another sector coverage in the same CDMA cell.
  • the softer handoff uses the same procedures of the soft handoff except that the softer handoff occurs between sector antennae of the same base station instead of between base stations.
  • Cell boundaries also include beam boundaries for satellite systems and cell refers both to the coverage of a ground base station antenna or of a satellite beam) usually offer poor coverage coupled with increased interference from other cells. Therefore, forward traffic channel diversity from additional cells or satellites will improve link quality.
  • a mobile unit consists of a mobile station for the cellular environment and a relatively fixed ground terminal from the satellite environment. While on a cell boundary, the mobile unit's interference to mobile units in other cells is maximal. The soft handoff enhances the ability to control the signal power of the mobile unit from these cells, thereby minimizing such interference.
  • a slow handoff process coupled with a vehicle moving at a high speed or a fast moving satellite may cause the call to be dropped if the mobile unit is no longer able to demodulate the forward link transmitted from the original cell, thereby losing the handoff direction commands.
  • the multitude of signals that eventually reach the receiver may also have traveled via different paths from the transmitter. Because the path lengths are different, the signals will not arrive at the receiver at the same time. Thus, the receiver may process two different versions of the same information, causing frequency selective fading.
  • channel coding the signals used to communicate with the mobile station.
  • Present channel coding systems do not differentiate the signal sent from different base stations to the same mobile station as a handoff occurs.
  • conventional CDMA cellular systems utilize multiple receivers to detect multipath signals and/or signals from different base stations. These signals are time delayed versions of the same coded signal and can be combined by a RAKE receiver and a diversity combiner.
  • the conventional diversity combiner uses the maximal ratio combiner on the "same" signals received from different base stations, from different sectors or on different multipath signals. The receiver thus receives the same exact signal from both base stations during a handoff operation. Because the signals received from both base stations in the handoff region are the same coded signal, the amount of gain is limited to only the diversity combining gain and the designed coding gain.
  • turbo coding Such a coding scheme as described in the Berrou patent is commonly known as "turbo coding.”
  • turbo coding allows a single signal to be encoded in multiple manners for simultaneous transmission.
  • multiple coded versions of the single signal can be received and combined to achieve increased coding gain.
  • a receiver that receives only one of the coded versions of the single signal still has enough information about the signal to adequately decode it.
  • the present invention solves the above described problems by combining a constituent coding/encoding sequence such as turbo coding with a soft handoff operation, so that a station (mobile or master) can receive two differently coded data streams based on the same information signal via two different base stations involved in the handoff.
  • the invention utilizes iterative decoding together with a combination of code combining and packet combining, in cellular and satellite based mobile communication systems. This enables the receiver to effectively combine the two coded information signals during the handoff, thus giving rise to lower code rates and enhanced performance of the cellular system.
  • Another object of the invention is to enhance the performance of a communications system along the boundaries of a cell.
  • turbo coding or similar coding it is an object of the present invention to use turbo coding or similar coding to enhance the performance of a soft handoff operation in a communications system.
  • turbo coding it is also an object of the invention to use turbo coding to provide two differently coded signals that can be combined by a mobile stations more clearly to achieve a powerful and higher code rate.
  • the invention relates to a method for effectuating handoff of service for a mobile station between base stations, in a cellular communications system.
  • appropriate cellular systems include land-based cellular systems and satellite type cellular systems.
  • the method involves communicating information between the mobile station and a first one of the base stations, using a turbo coding/decoding scheme with respect to a first version of the information.
  • the strength of transmitted pilot signals from the first base station and from another base station are measured, to determine a need for handoff.
  • the communication of the information between the mobile station and the first base station continues, while communications are established between the mobile station the other base station.
  • the communications between the mobile station and the second base station also use a turbo coding/decoding scheme, but the turbo coding for these communications is with respect to a second version of the information.
  • the two versions of the information include the input information and an interleaved version of the input information.
  • the method also includes terminating communications between the mobile station and the first base station when the pilot signal strength of the first base station falls below a predetermined level for a predetermined time period.
  • the communications with the other base station continue after termination of the communications with the first base station.
  • the continuing communications utilize the turbo coding/decoding scheme based on the second version of the information.
  • the system includes a source of digital data, for communication to or from a predetermined one of a plurality of mobile stations.
  • the source might be a vocoder, either in the handset or somewhere in the cellular network.
  • a first constituent encoder coupled to the source, encodes the digital data into a first code sequence.
  • the system also includes an interleaver, to interleave the digital data.
  • a second constituent encoder coupled to the interleaver, encodes the interleaved digital data into a second code sequence.
  • the system also includes two code puncturers, coupled to the constituent encoders. The first code puncturer selectively replaces data in the first code sequence with selected data from the second code sequence to form a first punctured code sequence. The second code puncturer selectively replaces data in the second code sequence with selected data from the first code sequence to form a second punctured code sequence.
  • Two transmitters send information on two logical channels assigned to the predetermined mobile station.
  • the system includes a control coupled to the first and second transmitters.
  • the control causes the first transmitter to broadcast the first channel carrying the digital data together with the first punctured code sequence.
  • the control also causes the second transmitter to broadcast the second channel carrying the interleaved digital data together with the second punctured code sequence.
  • the system elements may be elements of the network, for example including transmitters in base stations.
  • the elements may be part of the mobile station.
  • the mobile station would include transmitters for transmitting signals to two base stations during handoff.
  • Preferred embodiments of the invention utilize the turbo coding/decoding scheme on both the forward channel from the base stations to the mobile station and on the reverse channel from the mobile station to the base stations.
  • the receiver system includes at least one antenna for receiving signals from the transmitters.
  • Processing circuitry coupled to the antenna, recovers data from the two logical channels during handoff.
  • the receiver system includes an intelligent decoder, coupled to the processing circuitry. This element decodes signals from the first and second logical channels during handoff, to recover an accurate representation of the digital data.
  • the receiver includes two demultiplexers, a code combiner and the intelligent decoder.
  • the first demultiplexer processes the first received data stream, to recover digital data corresponding to the digital communication information and a first coded sequence.
  • the second demultiplexer processes the second received data stream, to recover digital data corresponding to an interleaved version of the digital communication information and a second coded sequence.
  • the code combiner is coupled to the first and second demultiplexers.
  • the code combiner processes the two coded sequences, to recover a first constituent encoded sequence corresponding to the digital communication information and a second constituent encoded sequence corresponding to the interleaved version of the digital communication information.
  • the intelligent decoder is coupled to the code combiner.
  • the decoder processes the recovered digital data corresponding to the digital communication information, the recovered interleaved version of the digital communication information and the first and second constituent encoded sequences, to produce an accurate representation of the digital communication information.
  • the intelligent decoder preferably is an iterative turbo decoder, although the invention encompasses other types of iterative decoders.
  • the preferred iterative turbo decoder includes two MAP decoders, a packet combiner, two interleavers and two deinterleavers.
  • the first MAP decoder is coupled to outputs of the code combiner corresponding to the recovered digital data corresponding to the digital communication information and the first constituent encoded sequence.
  • the first interleaver interleaves the recovered data corresponding to the digital communication information and supplies the result to an input of the packet combiner.
  • the packet combiner combines that data with the recovered interleaved version of the digital communication information and supplies the result to one input of the second decoder.
  • the second interleaver interleaves the output of the first MAP decoder and supplies the result to a second input of the second MAP decoder.
  • the second MAP decoder also is responsive to an output of the code combiner corresponding to the second constituent encoded sequence.
  • the first deinterleaver provides feedback of extrinsic information regarding the uninterleaved information sequence from the second decoder to the first decoder, and the second deinterleaver deinterleaves an output from the second decoder to provide the output of the intelligent decoder after completion of a predetermined number of iterations.
  • turbo coding other coding schemes such as conventional convolutional codes and product codes also could be used in connection with the present invention.
  • This new technique provides (1) improved communication performance as measured by the BER (Bit Error Rate) and (2) improved communication-drop-probability compared to that of the conventional handoff system. Therefore, the present invention increases system capacity through improved handoff reliability.
  • the present invention provides, for example, code rates of 1/4 and 1/6 (1 over number of coded symbols per bit), respectively, during handoff without increasing the bandwidth requirement, and still provides respective forward and reverse link coding rates of 1/2 and 1/3 during normal in-cell (or single satellite beam) operation served by a single base station.
  • This code rate enhancement is achieved by transmitting the original sequence with the properly punctured parity checks through one base station and interleaved data sequence with the other pattern of the punctured parity check sequence through the other base station.
  • the interleaved sequence and the uninterleaved original sequence are combined by the packet combiner, and punctured parity check sequences are combined by the code combiner.
  • the code combining and the packet combining techniques provide coding gain and mitigate detrimental fading effects on cellular and satellite systems.
  • the combination in the present invention of the handoff process with the iterative decoding process provides an inherently robust, seamless transition which is completely transparent to users. It provides the "softest” and the most reliable handoff in a cellular and multibeam and/or multiple satellite environment compared to prior art handoff methods.
  • the present invention allows even FDMA and TDMA systems a type of soft handoff mechanism by combining code diversity and packet combining with an iterative decoding; provided that the receiving entity has the capability of communicating via two channels--two frequency diversity receivers for FDMA and for multicell TDMA, or two time slots in single cell TDMA.
  • the signal from the two base stations in an FDMA or TDMA environment are differently coded with appropriate puncturing and are differently combined at the receivers to achieve a higher code rate.
  • FIG. 1 is a block diagram of a conventional CDMA diversity combiner receiver at a mobile station
  • FIG. 2 is a block diagram of a conventional CDMA diversity combiner at a base station operating on a reverse traffic channel
  • FIG. 3 is a graphical representation of a diversity combiner at either a mobile station or a base station
  • FIG. 4 is a schematic representation of two base stations engaging in a hand-off of a mobile station
  • FIG. 5 is a block diagram of forward traffic signal processing for transmission during a hand-off period
  • FIG. 6 is a block diagram of a turbo encoder used during a handoff period
  • FIG. 7 is a diagram of the puncturers and multiplexers used in the turbo encoder of FIG. 6;
  • FIG. 8 is a block diagram of a mobile station receiver
  • FIG. 9 provides a diagram illustrating a packet/code combiner and iterative decoder used in the receiver of FIG. 8;
  • FIG. 10 is a block diagram of a reverse traffic signal transmitter at a mobile station, showing the signal processing during a handoff period;
  • FIG. 11 is a block diagram of reverse traffic receivers at two a base stations, and a master switching center, with emphasis on illustration of the reverse channel signal processing during a handoff period;
  • FIG. 12 is a representation of a multiple satellite system with a mobile station, which may incorporate the invention.
  • FIG. 13 is a representation of a multi-beam satellite system, which may incorporate concepts of the invention.
  • FIG. 14 is a functional block diagram illustration of an embodiment of a turbo encoder system, for example, for a reverse link with a code rate 1/6.
  • FIG. 15 shows the puncturers and multiplexers of the embodiment of FIG. 14 with the various input and output bit streams, and should be helpful in understanding the operations of the punctures as well as the code rate produced in that embodiment.
  • FIG. 16 depicts an exemplary reverse traffic signal decoder at the base stations and master switching center, during handoff, for the case of a code rate of 1/6.
  • the present invention improves call reliability during the handoff operation, when compared to that of the conventional, diversity combining soft handoff technique.
  • This enhancement is provided by implementing code diversity combining and packet combining in conjunction with an iterative decoding process during handoff operations.
  • the improved communications may be used on either the forward link, the reverse link, or both.
  • the present invention is applicable both to land-based cellular systems and satellite-based cellular systems.
  • a handoff process typically occurs when the mobile station 401 is in the handoff region 404.
  • the example shown is a land-based cellular network having separate base stations serving different cells or areas of coverage.
  • the term ⁇ base station ⁇ here refers to any station having a relatively fixed service area in relation to the mobile station, at least during the communication session with the mobile station.
  • the base stations may be collocated and effectively form one station serving separate cells.
  • the ⁇ base stations ⁇ may include transceivers in one or more satellites, and a variety of other arrangements are contemplated.
  • both base stations communicate with the mobile station 401 during the handoff process.
  • both base stations send turbo encoded signals to the mobile station to provide the seamless and transparent or "softest" handoff.
  • both of the base stations A and B receive turbo encoded signals from the mobile station 401 during handoff.
  • the iterative coding scheme of the turbo encoded signal provides not only unprecedented coding gain for the given code rate which is near the theoretical channel capacity limit, but also a highly flexible system approach by utilizing inherently built in features--code diversity combining, and interleaving.
  • the current novel invention provides higher call reliability during handoff than that of in-cell normal single path operation using only one base station with a strong signal strength above the threshold level.
  • This invention is not limited to the mobile initiated handoff process described earlier. It can be used for the base station initiated handoff process without its previously described shortcomings, since the performance of this invention is more robust against signal fluctuation which causes unstable and frequent handoffs.
  • This invention also is not limited to voice communication.
  • the wireless communications can carry any digital data, including voice, image, video, text file, or multimedia information.
  • the master switch center (MSC) 504 first digitizes and properly encodes the forward traffic signal, for example through the use of a vocoder 501.
  • the digital data here is that intended for transmission to a predetermined user's mobile station or receiver.
  • the vocoder 501 supplies the digital data for that station to a turbo encoder 502. If the traffic is some information other than voice, the digital information may come from some other type of source within or connected to master switch center 504.
  • the forward traffic signal is turbo encoded in 502, to combat the channel noise and fading.
  • the outputs of the turbo encoder 502 at MSC 504 are separately switched to appropriate base stations A (505A) and B (506B).
  • the data stream sent to one of these base stations comprises the digital data stream intended for the particular mobile receiver and a first punctured code sequence.
  • the data stream sent to the other base station comprises an interleaved version of the same data intended for the particular mobile station and a second punctured code sequence.
  • the data streams are modulated by the proper Walsh sequences W i 506 and W j 507 in the known manner for the conventional CDMA systems, and power control bit insertion schemes and synch, paging and other traffic channels are omitted in FIG. 5 to simplify presentation of the current invention.
  • Walsh modulated pilot signals 503A, 503B are then added with the respective Walsh modulated turbo encoded signals 506A, 506B.
  • the resulting signal 508A, 508B are modulated then transmitted from the respective base stations.
  • the turbo coding technique of the preferred embodiment produces at least four streams of bits for transmission.
  • the first stream is the digital data stream or traffic information intended for the particular mobile station.
  • the encoder also generates an interleaved representation of the digital data stream or traffic information intended for the particular mobile station.
  • the other two streams are punctured code sequences.
  • Each punctured code sequence comprises selected portions of two constituent encoded parity sequences.
  • One constituent encoded parity sequence is formed by processing of the digital data or traffic information intended for the particular mobile station.
  • the other constituent encoded sequence is formed by processing of the interleaved representation of the digital data stream or traffic information intended for the particular mobile station.
  • one base station 505A transmits or broadcasts the signal 508A containing the digital data or traffic information intended for the particular mobile station and the first punctured code sequence.
  • a mobile station may receive this signal 508A while in a first area comprising the cell coverage area or sector serviced by the base station transmitter 505A.
  • the other base station involved in the handoff transmits or broadcasts the signal 5082 containing the interleaved version of the digital data or traffic information intended for -he particular mobile station and the second punctured code sequence.
  • the transmission from the second station is not the same as that from the first station.
  • the mobile station receives the broadcasts from both base stations, including all four of the bit streams.
  • the mobile station 401 receives up to four bits of turbo encoded information from the two base stations 505A, 505B, for a code rate of ⁇ 1/4 ⁇ .
  • the mobile station completes the handoff from the station A to the station B.
  • the system terminates the transmissions from the station A but continues the transmissions from the station B.
  • the receiver in the mobile station continues to receive the signal 508B for as long as it remains in the second area comprising the cell coverage area or sector serviced by the base station transmitter 505B.
  • the operating status whether a mobile station is operating the signal through base station A, through base station B or both, is controlled by the master switching center and is broadcast to the mobile station.
  • the mobile station may pass back through the same handoff region into the cell for base station A or pass through another handoff region into a cell for a third base station.
  • This second handoff will operate much the same as the first, except that the new station will be sending the uninterleaved data signal and the equivalent of the first punctured code sequence.
  • the mobile station actually may receive transmissions from three or more base stations during a handoff.
  • one, two or more base stations may transmit the uninterleaved data and associated punctured stream; and one, two or more base stations may transmit the interleaved data and associated punctured stream.
  • the receiver treats these duplicative transmissions much the way it would treat multi-path versions of the transmissions from one base station.
  • the front end circuitry in the receiver combines all copies of the uninterleaved data and associated punctured stream into one set of those signals for decoding; and the front end circuitry in the receiver combines all copies of the interleaved data and associated punctured stream into one set of those signals for decoding.
  • the central processing unit of the master switching center 504 tracks which bit streams go to each of the base stations.
  • the central processing unit in turn controls the switching functionality of the center to supply the correct streams to the respective base stations.
  • the control in the receiver also controls operations based on notation of the particular streams communicated to or from respective base stations.
  • the transmitter and the receiver configuration is the same as for a handoff period.
  • the receiver at the mobile station of this invention automatically estimates missing elements of the interleaved sequence and the punctured parity sequences for the iterative decoding from the systematic uninterleaved sequence and by inserting neutral values: "zeros".
  • the receiver automatically estimates missing elements and the interleaved sequence and the punctured parity sequences from the systematic interleaved sequence and by inserting neutral values: "zeros".
  • FIG. 6 depicts the functional elements of the previously discussed turbo encoder 502.
  • the turbo encoder 502 includes an interleaver 601 between two constituent recursive convolutional encoders 602A, 602B to permute the incoming digital voice information sequence in a random fashion.
  • the two encoders could implement a variety of coding algorithms.
  • the size of the interleaver 601 and the permutation algorithm are important parameters in turbo coding performance. Typically, as the interleaver size increases, the performance of the system is likewise enhanced. However, the interleaver size is limited by system constraints such as allowable voice latency and frame error rate. For example, voice communication cannot tolerate high latency; thus, it can have an interleaver (size up to approximately 400 bits. Other data communications such as image, video, file transfer do not have such limitations on the interleaver size. Typical cellular system applications transport a variety of digital data, but they also must accommodate digital communication of voice telephone-type traffic.
  • Permutation by the interleaver 601 breaks the cross-correlation between the two encoded sequences.
  • the permutation method can be a purely random interleaver whose permutation map is generated randomly or can be the systematic algorithm proposed in the Berrou patent.
  • the small interleaver permutation should be optimized using the interleaver design algorithm proposed by P. Roberson (Ref.; Interleaver Design Method).
  • the present invention is not limited to any permutation algorithm or interleaver size.
  • exemplary constituent encoders 602A, 602B in FIG. 6 can be described by the polynomial representation:
  • the parity sequence outputs Y 1 , Y 2 of the two encoders 602A, 602B are input to parity punctures 603A, 603B to gererate two different punctured sequences described in greater detail with regard to FIG. 7.
  • the puncturers 603A, 603B output the punctured sequences to the multiplexer 604 and the multiplexer 605, respectively.
  • the punctured parity sequence outputs are multiplexed with the data streams X 1 and X 2 , which represent the unaltered source sequences d k and interleaved sequences d ki .
  • the original voice data sequences represented as d k in FIG. 6 are supplied to the encoder 602A, which outputs an unaltered copy of the systematic voice data X 1 to one input of multiplexer 604 for ultimate transmission to the signal path to base station A.
  • the voice data d k is also supplied to the first constituent recursive convolutiona encoder 602A, which supplies parity output Y 1 to one input of the first puncturer 603A and to one input of the second puncturer 603B.
  • the voice data sequences d k are also supplied to interleaver 601.
  • the interleaver 601 permutes the received sequence of d k and generates d ki , through the permutation method described above.
  • the second constituent recursive convolutional encoder 602B receives an interleaved voice data signal d ki .
  • Unaltered interleaved signal d ki is supplied in systematic form as sequence X 2 to one input of the multiplexer 605 for ultimate transmission to the signal path to base station B.
  • a copy of d ki is supplied to the second constituent encoder 602B which encodes each interleaved bit of audio data and generates a parity sequence Y 2 , which is supplied to both puncturers 603A, 603B.
  • the first puncturer 603A punctures the parity outputs Y 1 and Y 2 , generated by voice data sequence d k and d ki (as shown in FIG. 6), according to the puncturing pattern [0,1/1,0] in an alternating Y 1 and Y 2 bit output sequence.
  • the second puncturer 603B punctures the parity outputs Y 2 and Y 1 generated by uninterleaved voice data sequence d k and interleaved voice data sequence d ki , according to the puncturing pattern [1, 0/0, 1] in an alternating Y 1 and Y 2 bit output sequence.
  • the master switch center supplies two streams to each base station.
  • the master switch center supplies the data stream X1 for the original digital information and the first punctured code sequence from the puncturer 603A in multiplexed form to the base station A.
  • the master switch center supplies the interleaved version X2 of the digital information and the second punctured code sequence from the puncturer 603B in multiplexed form to the base station B.
  • the forward transmissions can provide a punctured code rate of 1/2 for each signal path to one of the base stations A and B during handoff (or during an in-cell operation).
  • the system provides an overall code rate 1/4 during handoff, to provide improved performance over the known handoff methods.
  • the forward channel of the conventional CDMA system is limited to a code rate of 1/2.
  • the turbo encoded voice data signal to be transmitted is comprised of data sequences X 1 , Y 1 , X 2 , and Y 2 .
  • the wholly unaltered voice data and information portion of d k represented as X 1 has the following sequence:
  • N frame size
  • the frame size N is determined by adding the interleaver size and tail bit sequence to terminate the trellis being zero state.
  • a 4 tail bit sequence is needed because of the four bit memory as shown in FIG. 6.
  • the second interleaved uncoded voice data sequence d 2 is represented as X 2 and has the following sequence:
  • n the bit timing index
  • N frame size
  • the first constituent encoder 602A generates (1) the systematic sequence output X 1 ; and (2) the parity sequence output Y 1 using uninterleaved sequence d k .
  • the second constituent encoder 602B generates (1) the systematic interleaved sequence X 2 ; and (2) parity sequence output Y 2 using interleaved sequence d ki .
  • Parity sequence output Y 1 has the following sequence:
  • N frame size
  • Parity sequence output Y 2 has the following sequence:
  • N frame size
  • the output of the first puncturer 603A has the following sequence
  • the output of the second puncturer has the following sequence:
  • the resulting punctured outputs are multiplexed with sequence X 1 and X 2 at multiplexer 604, 605, respectively.
  • the outputs of the two encoders yield the code rate of 1/4 overall, and are punctured and multiplexed into two separate signal paths A and B--each with the individual code rate of 1/2. Accordingly, the output sequence from multiplexer 604 is represented as:
  • the output sequence of multiplexer 605 is represented as:
  • the output of multiplexer 604 is transmitted to the base station A and the output of multiplexer 605 is transmitted to the base station B simultaneously.
  • Spreading and combining processes are performed on each of the forward traffic channels associated with the base stations involved in a handoff, for example in a manner described U.S. Pat. No.
  • This coding process greatly enhances the performance of conventional CDMA cellular systems. Such systems are compromised because the same signal is present at the mobile station's receiver from each base station, wasting valuable power and bandwidth without improved coding gain.
  • the conventional CDMA mobile station receiver receives the same signal from both base stations and overall performance is limited to a code rate of 1/2.
  • the signal from each base station will have all the information necessary for estimating the missing voice data from any other base station in communication with the mobile station and for successfully performing the iterative algorithm.
  • other advantages include reduction or mitigation of fading, shadowing, and/or other loss of transmitted signal.
  • bit error rate (BER) of the present invention during a handoff with a code rate of 1/4 results in better performance than that of the normal in-cell operation served by a base station with a code rate of 1/2. This performance advantage and the user transparency during the handoff period provides "the softest handoff”.
  • FIGS. 8 and 9 depict an exemplary mobile station receiver of the present invention.
  • the mobile station includes an antenna 801, which is connected to a diplexer 802 to permit simultaneous transmission and reception through the single antenna.
  • FIG. 8 shows only the received signal processing elements.
  • the diplexer 802 provides the received signals to the analog receiver 803.
  • the antenna collects signals from a singular serving base station.
  • the analog receiver 803 receives RF signals from the Diplexer, amplifies, and converts the signals to an IF frequency, for application to a digital receiver 804A, 804B and a search receiver 805.
  • the antenna collects transmitted signals from base station A and base station B.
  • the antenna 801, diplexer 802, and analog receiver 803 are of standard elements of the CDMA cellular circuitry described for example in U.S. Pat. No. 5,109,390 entitled "Diversity Receiver in a CDMA Cellular Telephone System” and incorporated herein by reference.
  • the standard design of the mobile station includes a transmit signal amplifier, a transmit power control unit, and a transmit modulator. However, these units are omitted from the FIGS. 8 and 9 for ease of illustration.
  • the IF signal pass through a bandpass filter with a proper bandwidth to match the transmitted waveform.
  • the output of the matched filter is then digitized by an A/D converter (not shown) for converting IF signals to a digital signal.
  • the digitized signal is provided to each of three receivers, one of which is a searcher receiver 805, with others being data receivers 804A, 804B.
  • the searcher receiver 805 continuously scans the pilot signals from the base station currently serving the mobile station, as well as the pilot signals from other base stations in the vicinity, for the handoff processing. It measures the ratio of a received pilot signal's energy-per-chip to total received interference spectral density, including the noise as a measure of the pilot signal strength.
  • the measured pilot signal strength is used by the control processor 816 to select and to process signals from two different base stations A and B during the handoff period.
  • Receiver 804A processes signals from base station A including a multipath signal from base station A.
  • Receiver 804B processes signals from base station B including a multipath signal from base station B.
  • the receivers 804A, 804B of the present invention process two differently coded signal streams from two different base stations, instead of processing the same signals from both base stations as in a conventional CDMA receiver.
  • the outputs of receivers 804A and 804B are RxA and RxB, respectively. These digital output sequences are provided to packet/code combiner and iterative decoder 806.
  • the packet/code combiner and iterative decoder 806 facilitates the improved handoff method.
  • the outputs RxA and RxB are fully demodulated signal streams from base station A and B.
  • the RxA input at the packet/code combiner and iterative decoder 806 comprises the sequence of
  • the packet/code combiner and iterative decoder 806 advantageously performs demultiplexing to separate systematic voice data sequence from the multiplexed signals and depunctures parity check sequences. Through this depuncturing and reshuffling processes, code combining is achieved.
  • the packet/code combiner and iterative decoder 806 includes a demultiplexing stage having two demultiplexers 901A, 901B that demultiplex each of the signals RxA and RxB, respectively. As noted, these input signals to the demultiplexers 901A, 901B are estimations of the encoded voice data signal sequences corrupted with channel noise and other external factors such as fading.
  • Each of the demultiplexers 901A and 901B separates the RxA and RxB data into systematic recovered data information sequences 902XA and 902XB and recovered punctured parity check data sequences 902YA and 902YB.
  • the code combiner 904 depunctures the sequences and achieves the code diversity combining, so as to output systematic forms of uninterleaved recovered information signal sequence X 1 and a recovered first depunctured parity sequence Y 1 to a first MAP decoder 905.
  • This first MAP decoder 905 is symmetric to the first recursive systematic convolutional encoder 602A of the turbo encoder.
  • the diversity combiner 904 also outputs systematic form of recovered interleaved information signal sequence X 2 and corresponding recovered second depunctured parity sequence Y 2 .
  • the recovered interleaved information signal sequence X 2 is output to the maximal ratio packet combiner 909, and the second depunctured parity sequence Y 2 is output to a second MAP decoder 906.
  • the operation of the second decoder 906 is likewise symmetric to a second recursive systematic convolutional encoder 602B.
  • input signals to the parity sequence combiner 904 from the two demultiplexers may be as follows:
  • the parity sequence combiner 904 reshuffles both the uninterleaved and interleaved parity sequences 902YA and 902YB.
  • the outputs of the parity sequence combiner 904 are as follows:
  • the first MAP decoder 905 further receives a feedback loop from the second MAP decoder 906 as defined herein. Such use of the previously estimated data sequence improves the reliability of successive iterations. This reliability information and feedback loop has been depicted as "extrinsic information" in the turbo code literature and is well understood.
  • the MAEP decoders 905, 906 are known in the art as powerful constituent Maximum A Posteriori Probability (MAP) decoders.
  • the MAP decoder accepts the input of the noise-ridden X 1 and Y 1 sequences as supplied by the parity sequence combiner 904 and the feedback signal is set to a neutral value (set to "zero").
  • the output of the first MAP decoder 905 is indicative of extrinsic information of the original digital information signal d k , which is the reliability of the decoded data sequence and is represented as ⁇ 1 .sup.(x1).
  • the extrinsic information signal is supplied to an interleaver 307 to interleave the information with the same permutation algorithm as the encoder interleaver 601.
  • the output signal ⁇ 1 .sup.(x2) from the interleaver is fed to the second MAP decoder 906 as a priori information about the data sequence X 2 .
  • the output X 1 of the parity sequence combiner 904 is supplied to the interleaver 908, to interleave that information with the same permutation algorithm as the encoder interleaver 601.
  • the output of the interleaver 908 is combined with X 2 in the maximal ratio packet combiner 909, to achieve packet diversity combining of the encoded signals from the base station A and the bases station B, using a conventional maximal ratio combining algorithm.
  • the maximal ratio combining is accomplished by adding two weighted signal streams whose weighing factors are proportional to the measured signal strengths.
  • the output of the maximal ratio combiner is expressed by:
  • the maximal ratio packet combiner 909 provides a significant improvement over the prior art and operates to combine digital data information from base station A and interleaved voice data information from base station B.
  • the signal output from the maximal ratio packet combiner 909 is supplied as one input of the second MAP decoder 906.
  • the interleaved extrinsic information of the first MAP decoder 905 output is supplied to the second MAP decoder 906 as a priori information.
  • the output Y 2 of the parity sequence combiner 904 is supplied to the second MAP decoder 906.
  • the second MAP decoder 906 operates on the extrinsic information, namely combined interleaved sequences X 2 (combined) and Y 2 .
  • the second MAP decoder 906 also outputs the reliability data about d ki as an extrinsic feedback signal ⁇ 2 .sup.(x2).
  • This signal is supplied to a deinterleaver 910 (of the feedback loop) which operates to undo the interleaving of the estimated voice data sequence of d k .
  • the second deinterleaver 911 supplies the final d k estimation output signal to a hard limiter 912 after the predetermined number of iterations between the first MAP decoder 905 and the second MAP decoder 906.
  • the number of iterations performed depends on the system performance criteria such as final bit error rate, latency tolerance, and allowable processing power. Because the tight limitation of the voice communication in latency, the number of iterations is bounded at two and a half (21/2) for the exemplary presentation. However, data such as video, images, and multimedia communications which do not suffer by the latency can have a higher number of iterations as needed.
  • the hard decision maker (limiter) 912 operates in a known manner on the supplied signal to form d k after a predetermined number of iterations, so as to output one of two binary states for each bit. For example, everything above zero is assigned +1, everything below zero is assigned -1.
  • the d k signal is supplied to the user base band process 913 and vocoder, to decode the voice data signal and to supply it to a speaker for listening by a user.
  • the bit stream output of the limiter may go to appropriate digital data processing equipment, e.g., for data display, video processing, etc.
  • a simpler from of MAP decoders 905, 906 can also be used with the present invention, such as a SOVA (soft output Viterbi algorithm) decoder as suggested by Hagenauer or simpler form of soft input soft output decoders.
  • SOVA soft output Viterbi algorithm
  • the cellular network utilized the inventive coding/decoding for handoff for communication on the forward channel.
  • the invention can also can be applied to the reverse traffic signal from a mobile station to the base stations A and B.
  • FIGS. 10 and 11 depict the reverse channel processing elements of the mobile station and base station, particularly as used during a handoff operation.
  • the mobile station contains a vocoder 1001 and a turbo encoder 1002.
  • the vocoder 1001 supplies the turbo encoder 1002 (FIG. 14) with voice signals.
  • the vocoder 1001 supplies the turbo encoder 1002 with unaltered voice signal d k as shown in FIGS. 10 and 14.
  • d k unaltered voice signal
  • the signal is first modulated by orthogonal modulators 1003A, 1003B and then marked with the appropriate long code at 1004A, 1004B for the respective base stations servicing the call during the handoff.
  • orthogonal modulators 1003A, 1003B are used to mark with the appropriate long code at 1004A, 1004B for the respective base stations servicing the call during the handoff. This modulation and masking of the code is conventional and known in the art.
  • Each of the base stations has at least two antennae 1103A1, 1103A2, 1103B1 and 1103B2. Each antenna connects to a receiver 1104A1, 1104A2, 110431 and 1104B2. Each antenna provides its received signal to its respective receiver. Only details for one of the receivers 1104A1 is shown. The other receiver 1104A2, 1104B1 and 1104B2 are similar).
  • the receivers in the base station contain an analog receiver 1105, various digital data receivers 1106, 1107 and a searcher receiver 1108. These perform functions similar of the analogous components in the recovery of FIG. 8. Due to the path diversity generated by the two antennae, e.g., 1103A1, 1103A2, the signals received by the separate receivers in a single base station must be combined by a diversity combiner 1109 prior to decoding. The combined signal is finally supplied to the packet/code combiner and iterative decoder 1121 at the master switching center 1120. The packet/code combiner and iterative decoder 1121 operate in a manner illustrated in FIG. 16. Once the signal is decoded, it is fed through the switch network (not shown) to a user base band processor 1123 and a vocoder 1124 to transmit the signal as audio information to a speaker 1125 for listening by an end user.
  • the invention can be utilized in the multiple satellite system, which must have the handoff ability to maintain either a voice communication or data communication session.
  • the handoff occurs when a mobile unit 1205 enters an area 1206 where the footprints from two satellites overlap.
  • a satellite's footprint is the area on he ground that is covered by the satellite's beam.
  • a first satellite 1201 has a footprint 1203.
  • the satellite 1201 has a transmitter for broadcasting signals into the footprint and a receiver system for receiving signals from the footprint, in a manner analogous to the cellular embodiments.
  • a second satellite 1202 has a separate footprint 1204.
  • Satellite communications systems typically arrange the satellite beams such that the footprints overlap in order to insure that there is no gap in service between footprints.
  • the mobile unit 1205 enters the handoff area 1206, the same exact soft handoff procedures and recursive convolutional iterative decoding described above can be used to effectuate the handoff in this multiple satellite system.
  • yet another embodiment of the invention envisions the soft handoff procedures and recursive convolutional iterative decoding effectuating handoffs in the handoff regions 1301 located between overlapping footprints 1302, 1303, and 1304 of a multibeam satellite system 1305.
  • the transmitter and receiver circuitry for beam communication to and from the various footprints all ride in the one satellite.
  • the code rate during handoff was 1/4 (1 input bit encoded into 4 transmitted bits).
  • the transmission side sent one channel of information, containing the original digitized information and a first punctured code stream.
  • the transmission side sent a second channel of information, containing the interleaved version digitized information and a second punctured code stream.
  • communications in accord with the invention may utilize turbo encoding to achieve even lower code rates.
  • the reverse channel communications in a CDMA cellular system might operate with encoding for a 1/6 code rate.
  • FIGS. 14 and 15 depict elements of a turbo coding system providing a 1/6 code, preferably for use in reverse channel communications.
  • FIG. 14 provides a high-level functional illustration of this embodiment of the turbo encoder.
  • the turbo encoder receives the digital information d K intended for transmission at an input 1401.
  • the digital information d K would be a digitized and compressed voice signal from a vocoder or the like.
  • the digital information d K could be virtually any other type of digital data that a user may want to send over the wireless air interface.
  • the digital information d K input at 1401 is supplied as a data stream X 1 directly to one input of a first multiplexer 1407A.
  • the input 1401 also couples the digital information d K to the input of an interleaver 1402.
  • the interleaver 1402 interleaves the digital information d k in a manner similar to that of the interleaver 601 in FIG. 6, to break up cross-correlation between later developed coded sequences.
  • the turbo encoder also includes two constituent recursive convolutional encoders 1403A, 1403B.
  • the first encoder 1403A receives the digital information X 1 directly from the input 1401.
  • the interleaver 1402 supplies an interleaved version of the digital information to the constituent recursive convolutional encoder 1403B.
  • the constituent recursive convolutional encoder 1403A processes the digital information to produce the two parity sequences Y 1 , Y 2 .
  • the constituent recursive convolutional encoder 1403B processes the interleaved version of the digital information to produce the two additional parity sequences Y 3 , Y 4 .
  • Each convolutional encoder 1403 includes a series of delay elements D, shown as four in the illustrated example, and a feedback loop. In each encoder, two different series of taps from the line of delay elements provide the different encoded parity sequences.
  • FIG. 14 shows the constituent encoders 1403A and 1403B as identical systems, each having four delay elements and the same polynomial representations for the two parity sequences.
  • the present invention is not limited by the particular polynomials nor by the number of memory elements, which is one less than the constraint length.
  • Each constituent recursive convolutional encoder 1403A, 1403B supplies its two parity code sequences to inputs of both of two puncturers 1405A, 1405B.
  • the four inputs to each of the punctures 1405A, 14052 comprise the four parity code sequences Y 1 , Y 2 , Y 3 and Y 4 .
  • Each puncturer supplies two separated punctured code sequences to inputs of the corresponding multiplexer.
  • the first puncturer 1405A supplies its two punctured code sequences to the second and third inputs of the multiplexer 1407A.
  • the multiplexer 1407A combines the first punctured code sequence and second punctured code sequence together with the original digital information in stream X 1 .
  • the multiplexer 1407A supplies the combined information to a first transmission circuit, for CDMA transmission over a first logical channel to the base station A.
  • the second puncturer 1405B supplies its two punctured code sequences to the second and third inputs of the multiplexer 1407B.
  • the multiplexer 1407B combines the third punctured code sequence together with the interleaved version of the digital information in the stream identified as X 2 .
  • the multiplexer 1407A would supply the combined information to a second transmission circuit, for CDMA transmission over a second logical channel to the base station B.
  • FIG. 15 shows the puncturers and multiplexers of the embodiment of FIG. 14 with the various input and output bit streams.
  • the operation of the punctures 1405A and 1405B is similar to that of the puncturers in the earlier embodiment, except that the puncturers are adapted to select and combine portions of four input parity signals to form two punctured sequences.
  • FIG. 15 depicts the puncturing matrices of the two punctures 1407A and 1407B.
  • the puncturer 1405A actually functions much like a combination of two of the punctures 603A, one of which processes the signals Y 1 and Y 2 and the other of which processes the signals Y 3 and Y 4 .
  • the puncturer 1405B actually functions much like a combination of two of the punctures 603B.
  • the parity sequence outputs may be represented by:
  • the first output of the puncturer 1405A has the following sequence
  • the second output of the puncturer 1405A has the following sequence
  • the overall combined puncturing pattern matrix of the puncturer 1405A is [0101/1010].
  • the first output of the second puncturer 1405B has the following sequence:
  • the second output of the puncturer 1405B has the following sequence
  • the overall combined puncturing pattern matrix of the puncturer 1405B is [1010/0101].
  • the puncturer 1405A supplies the first two streams (17), (18) to inputs of the first multiplexer 1407A.
  • the multiplexer 1407A cycles repetitively through its three inputs to connect bits therefrom to its one output.
  • the multiplexer 1407A thus combines the bit stream X1 representing the input information together with the first and second punctured sequences.
  • the multiplexer essentially produces a bit stream sequence of:
  • the puncturer 1405B supplies the first two streams (19), (20) to inputs of the first multiplexer 1407B.
  • the multiplexer 1407B cycles repetitively through its three inputs to connect bits therefrom to its one output.
  • the multiplexer 1407B thus combines the bit stream X2 representing the interleaved version of the input information together with the third and fourth punctured sequences.
  • the multiplexer essentially produces a bit stream sequence of:
  • the outputs of the two encoders yield four-bits for each single input bit, the combination of the four-bits of encoded signals with a bit of the input information and a bit of the interleaved version of the information produces a total of six bits for transmission derived from the one input bit.
  • the outputs of the multiplexers provide six bits for transmission for each input bit, yielding a code rate of 1/6.
  • the sequence (21) goes from the first multiplexer 1407A to a first reverse channel transmission to the base station A.
  • the sequence (22) goes from the first multiplexer 1407B to a second reverse channel transmission to the base station B.
  • the base stations and associated master switching center receive and decode the 1/6 rate reverse channel transmissions in a manner similar to that used in the receiver of FIGS. 8 and 9.
  • the packet/code combiner and iterative decoder is adapted to six bit streams, specifically the recovered stream corresponding to the input information, the recovered stream corresponding to the interleaved version of the information and the recovered streams corresponding to the four punctured sequences.
  • the two MAP decoders are adapted to process three sequences each, and in particular to perform the inverse of the coding operations of the two encoders 1403A, 1403B.
  • the mobile station transmits one of the streams from one multiplexer to one of the base stations.
  • the mobile station transmits the sequence (21) from the first multiplexer 1407A to the base station A.
  • the base station A and master switching center process the bits for the three sequences in that stream (code rate 1/3) to derive an accurate representation of the original input information.
  • the mobile station transmits over the reverse channel only to the base station B.
  • the mobile station transmits the sequence (22) from the second multiplexer 1407B.
  • the base station B and master switching center process the bits for the three sequences in that stream (code rate 1/3) to derive an accurate representation of the original input information.
  • FIG. 16 An example of the reverse channel parity code combiner in conjunction with an iterative decoder is shown in detail in FIG. 16.
  • the operational concept is similar to that of the forward channel.

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US09/110,395 US5978365A (en) 1998-07-07 1998-07-07 Communications system handoff operation combining turbo coding and soft handoff techniques
BRPI9912256A BRPI9912256B1 (pt) 1998-07-07 1999-07-02 sistema de comunicação móvel e sistema receptor para operação em um sistema de comunicação móvel sem fio
PCT/US1999/015223 WO2000002404A1 (en) 1998-07-07 1999-07-02 Communications system handoff operation combining turbo coding and soft handoff techniques
AU50907/99A AU749517B2 (en) 1998-07-07 1999-07-02 Communications system handoff operation combining turbo coding and soft handoff techniques
DE69939261T DE69939261D1 (de) 1998-07-07 1999-07-02 Betrieb des weiterreichens zwischen kommunikationssstemen mit kombination von turbokodierung und technichen für weiches weiterreichen
JP2000558683A JP3671149B2 (ja) 1998-07-07 1999-07-02 ターボコーディングおよびソフトハンドオフ技術を結合する通信システムハンドオフ操作
KR10-2001-7000239A KR100370425B1 (ko) 1998-07-07 1999-07-02 터보 부호화와 소프트 핸드오프 기술을 결합한 통신시스템의 핸드오프 방법
CNB99808316XA CN1154383C (zh) 1998-07-07 1999-07-02 移动通信系统、接收机、越区切换及传送和接收数据方法
EP99935426A EP1095529B1 (de) 1998-07-07 1999-07-02 Betrieb des weiterreichens zwischen kommunikationssstemen mit kombination von turbokodierung und technichen für weiches weiterreichen
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BRPI9912256B1 (pt) 2015-11-17
KR100370425B1 (ko) 2003-02-05
CN1154383C (zh) 2004-06-16
CN1308821A (zh) 2001-08-15
JP3671149B2 (ja) 2005-07-13
JP2003503863A (ja) 2003-01-28
EP1095529B1 (de) 2008-08-06
AU5090799A (en) 2000-01-24
US6094427A (en) 2000-07-25
EP1095529A4 (de) 2006-03-29
WO2000002404A1 (en) 2000-01-13
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KR20010083095A (ko) 2001-08-31
AU749517B2 (en) 2002-06-27

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