US6166526A - DC/DC converter - Google Patents

DC/DC converter Download PDF

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Publication number
US6166526A
US6166526A US09/272,508 US27250899A US6166526A US 6166526 A US6166526 A US 6166526A US 27250899 A US27250899 A US 27250899A US 6166526 A US6166526 A US 6166526A
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United States
Prior art keywords
comparator
input
converter
transistor
switching transistor
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Expired - Lifetime
Application number
US09/272,508
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English (en)
Inventor
Norbert Greitschus
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Entropic Communications LLC
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TDK Micronas GmbH
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Assigned to MICRONAS INTERMETALL GMBH reassignment MICRONAS INTERMETALL GMBH ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: GREITSCHUS, NORBERT
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Assigned to TRIDENT MICROSYSTEMS (FAR EAST) LTD. reassignment TRIDENT MICROSYSTEMS (FAR EAST) LTD. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: MICRONAS GMBH
Assigned to ENTROPIC COMMUNICATIONS, INC. reassignment ENTROPIC COMMUNICATIONS, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: TRIDENT MICROSYSTEMS (FAR EAST) LTD., TRIDENT MICROSYSTEMS, INC.
Assigned to ENTROPIC COMMUNICATIONS, INC. reassignment ENTROPIC COMMUNICATIONS, INC. MERGER AND CHANGE OF NAME Assignors: ENTROPIC COMMUNICATIONS, INC., EXCALIBUR ACQUISITION CORPORATION
Assigned to ENTROPIC COMMUNICATIONS, LLC reassignment ENTROPIC COMMUNICATIONS, LLC MERGER AND CHANGE OF NAME Assignors: ENTROPIC COMMUNICATIONS, INC., ENTROPIC COMMUNICATIONS, LLC, EXCALIBUR SUBSIDIARY, LLC
Assigned to JPMORGAN CHASE BANK, N.A., AS COLLATERAL AGENT reassignment JPMORGAN CHASE BANK, N.A., AS COLLATERAL AGENT SECURITY AGREEMENT Assignors: ENTROPIC COMMUNICATIONS, LLC (F/K/A ENTROPIC COMMUNICATIONS, INC.), EXAR CORPORATION, MAXLINEAR, INC.
Anticipated expiration legal-status Critical
Assigned to MUFG UNION BANK, N.A. reassignment MUFG UNION BANK, N.A. SUCCESSION OF AGENCY (REEL 042453 / FRAME 0001) Assignors: JPMORGAN CHASE BANK, N.A.
Assigned to EXAR CORPORATION, MAXLINEAR, INC., MAXLINEAR COMMUNICATIONS LLC reassignment EXAR CORPORATION RELEASE OF SECURITY INTEREST Assignors: MUFG UNION BANK, N.A.
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter

Definitions

  • This invention relates to DC/DC converters and more particularly to a DC/DC converter adapted to convert an input voltage to an output voltage greater or less than the input voltage.
  • DC/DC converters are known from "Analoge Heidelberg", M. Seifert, VEB Verlagtechnik Berlin, 1987, pp. 540 et seq.
  • a DC/DC converter can be designed as a step-up converter, which produces an output voltage greater than the input voltage, or as a step-down converter, which produces an output voltage less than the input voltage.
  • Such a DC/DC converter has a high efficiency.
  • the ratio of output voltage to input voltage is determined by the duty cycle of the switching transistor.
  • An inductor serves as an energy store in the DC/DC converter. It generally consists of a coil with a ferrite core. In such a DC/DC converter, the inductor current is a function of the load current. When the inductor current exceeds a given value, the ferrite material quickly loses its permeability since the inductor becomes saturated, whereby a further increase in current is caused, which may result in the circuit or parts thereof being destroyed.
  • a DC/DC converter including a switching transistor (1), an inductor (2), a smoothing capacitor (3), and a switching element (4) which are connected so as to convert an input voltage U E to an output voltage U A greater or less than the input voltage U E .
  • the current through the inductor can be measured by providing a comparator (5) having a first input connected to the switching transistor (1), and a second input connected to a reference transistor (7) and a reference current source (6) so as to fix the switching threshold of the comparator (5) at the second input.
  • FIG. 1 illustrates a first embodiment of the DC/DC converter according to the present invention as a step-up converter.
  • FIG. 2 illustrates another embodiment of the DC/DC converter according to the present invention as a step-up converter.
  • FIG. 3 illustrates another embodiment of the DC/DC converter according to the present invention as a step-up converter.
  • FIG. 4 illustrates another embodiment of the DC/DC converter according to the present invention as a step-up converter.
  • FIG. 5 illustrates an embodiment of the DC/DC converter according to the present invention as a step-down converter.
  • a DC/DC converter which includes a comparator having a first input connected to the switching transistor, and a second input connected to a reference transistor and a reference current source in such a way as to fix the switching threshold of the comparator at the second input.
  • the inductor current can be measured without an additional sensing resistor being required, so as not to reduce the operating efficiency of the DC/DC converter. Since, in the on state, the switching transistor is operated in its resistance region or triode region, the inductor current can be measured via the voltage drop across the switching transistor. In the circuit according to the invention, the voltage drop across the switching transistor is compared with the voltage drop across the reference transistor. The latter voltage drop is caused by the fact that the reference current from the reference current source flows through the reference transistor. This determines the switching threshold of the comparator. The switching threshold will be chosen so that the maximum permissible current through the inductor or the switching transistor will be detected.
  • the comparator senses when the current in the DC/DC converter exceeds the maximum permissible value.
  • the switching transistor and the reference transistor are MOS transistors
  • the reference transistor is operated as a triode transistor
  • the ratio of the gate-source voltage of the switching transistor to the gate-source voltage of the reference transistor is constant. This ensures that comparable conditions exist for the reference transistor and the switching transistor, so that the current through the switching transistor can be determined more reliably.
  • the ratio of the gate-source voltages of the two transistors is 1.
  • the reference transistor advantageously has a smaller width to length (w/l) ratio than the switching transistor. The w/l ratio of the transistors determines their parameters. As a result of the smaller w/l ratio of the reference transistor, a reference current smaller than the current through the switching transistor is needed, whereby any unnecessarily high current in the reference circuit is avoided.
  • the output of the comparator is applied to a control unit for controlling the duty cycle of the switching transistor.
  • the output of the comparator thus acts on the control of the DC/DC converter. If the current through the switching transistor exceeds the predetermined maximum value, the duty cycle of the switching transistor is changed so that the output voltage, and thus the current through the DC/DC converter, changes.
  • the reference transistor comprises several series-connected, like transistors whose gate electrodes are tied to a common, fixed potential.
  • the fixed potential may be the operating voltage; in the case of a step-down converter, it may be ground.
  • the reference current is reduced by a factor equal to the number of transistors. A high reference voltage is thus obtained. Further, because the voltage drops across the individual transistors are small, the resulting back-bias effect of the transistors is negligible.
  • a first auxiliary switching element is provided between the first input of the comparator and the switching transistor for separating the comparator input from the switching transistor during the off state of the switching transistor.
  • the auxiliary switching element prevents the comparator from being overdriven when the switching transistor is turned off.
  • the auxiliary switching element can be implemented with a transistor.
  • a second auxiliary switching element may be provided between the first input of the comparator and a fixed potential.
  • the first input of the comparator is preferably grounded; in the case of a step-down converter, it is preferably connected to the operating voltage.
  • the comparator input is prevented from being cyclically overdriven.
  • the reference current source may be designed to be adjustable from outside.
  • the reference current may be adjustable digitally, i.e., in steps, or continuously, for example by means of a potentiometer.
  • the comparator may have a predetermined offset voltage. This permits a further shift of the switching threshold of the comparator.
  • the reference voltage can be increased without using too many transistors for forming the measuring transistor and without the reference current being increased.
  • the comparator may exhibit hysteresis, i.e., it may be designed as a Schmitt trigger.
  • the arrangement is implemented using monolithic integrated circuit technology.
  • the reference transistors can then be disposed near the switching transistor, so that comparable conditions exist for the two transistors and no matching problems are caused by excessive spacing, masking differences, differences in implementation, temperature, and the like.
  • FIG. 1 illustrates a first embodiment of the DC/DC converter according to the present invention as a step-up converter. It serves to convert an input voltage U E to an output voltage U A which is greater than the input voltage U E .
  • the DC/DC converter comprises a switching transistor 1, an inductor 2, a smoothing capacitor 3, and a switching element 4 in the form of a diode.
  • the switching transistor 1 an n-channel MOS transistor is used here. Instead of MOS transistors, bipolar transistors can be used in this circuit.
  • the input voltage is applied across the series combination of the inductor 2 and the switching transistor 1 such that the source terminal of the switching transistor 1 is grounded.
  • the smoothing capacitor 3 and the switching element 4 are connected in parallel with the source-drain direction of the switching transistor 1.
  • the circuit is designed so that the current through the inductor 2 can be measured in the on state of the switching transistor 1. In its on state, the switching transistor 1 is operated in the linear region, i.e., in the triode region. Therefore, the voltage drop across the switching transistor 1 is nearly proportional to the current through the inductor 2.
  • the voltage drop across the switching transistor 1 is applied to the first input of a comparator 5.
  • the other input of the comparator 5 is connected to a reference voltage. The latter is generated by applying a reference current from a reference current source 6 to a reference transistor 7.
  • the reference transistor 7 is also an n-channel MOS transistor which is operated in its linear region, i.e., in the triode region. In the on state of the transistors, the ratio of the gate-source voltage of the switching transistor 1 to the gate-source voltage of the reference transistor 7 is constant.
  • the reference transistor 7 is basically of the same design as the switching transistor 1. However, it can have a smaller width/length (w/l) ratio than the switching transistor 1.
  • the reference transistor 7 can produce the same voltage drop as the voltage drop at the first input of the comparator 5.
  • the reference current source 6 and the reference transistor 7 are chosen so that a predetermined reference voltage is generated which corresponds to the voltage at the switching transistor caused by the maximum permissible current through the inductor 2.
  • the voltage at the first input of the comparator 5 rises above the reference voltage at the second input of the comparator 5, so that the state of the output signal of the comparator changes.
  • the output of the comparator 5 is applied to a control unit 8 which controls the gate of the switching transistor 1.
  • the duty cycle of the switching transistor 1 can be controlled directly. Since the duty cycle determines the ratio of output voltage U A to input voltage U E , the output voltage can thus be readjusted in case of changes in input voltage.
  • An increase in the current through the inductor 2 can be counteracted by controlling the duty cycle.
  • the output signal of the comparator 5 causes the duty cycle of the switching transistor 1 to be reduced, thereby reducing the output voltage and, thus, the inductor current.
  • This circuit does not require an additional sensing resistor to sense the current through the switching transistor. Hence, the efficiency of the DC/DC converter is retained.
  • the entire arrangement of FIG. 1 can be integrated on a semiconductor, particularly on a silicon substrate.
  • the reference transistor 7 is disposed close to the switching transistor 1, so that comparable conditions exist for the two transistors. Thus, temperature effects as well as influences of the manufacturing process, such as dissimilar implementation, mask alignment processes, etc., are avoided.
  • FIG. 2 illustrates another embodiment of the DC/DC converter according to the present invention as a step-up converter. Like parts are designated by the same reference characters as in the embodiment of FIG. 1. Since the operation of the circuit corresponds to that of the embodiment of FIG. 1, only the differences will be discussed.
  • the reference transistor is formed from several like transistors 7a, 7b, 7c, 7d, 7e connected in series.
  • the gate electrodes of these transistors are tied to a common, fixed potential, the operating voltage. In this manner, a substantially higher reference voltage for comparison with the voltage at the first input of the comparator 5 can be generated without having to produce a large reference current.
  • a large voltage drop can be detected without producing a large voltage drop in the individual transistors.
  • the reference transistor is implemented with two transistors 7a, 7b.
  • the reference current of the reference current source 6 is variable.
  • An external current may be impressed as the reference current.
  • the current source is continuously adjustable, for example by means of a potentiometer.
  • a first auxiliary switching element 9 Connected between the first input of the comparator 5 and the switching transistor 1 is a first auxiliary switching element 9 which separates the comparator input from the switching transistor 1 during the off state of the switching transistor 1.
  • the first auxiliary switching element 9 is an n-channel MOS transistor. It prevents the comparator 5 from being overdriven when the switching transistor 1 is switched to the off state. Since the first auxiliary switching element 9 separates the line from the switching transistor 1 to the comparator 5, no increased voltage can reach the first input of the comparator.
  • a second auxiliary switching element 10 Connected between the first input of the comparator 5 and a fixed potential is a second auxiliary switching element 10 which holds the first input at the fixed potential during the off state of the switching transistor 1.
  • the second auxiliary switching element 10 is also implemented as an n-channel MOS transistor.
  • the reference current source 6 in this embodiment is digitally adjustable.
  • the digital register 13 of the reference current source 6 can be adjusted via a digital interface, for example.
  • the reference transistor comprises transistors 7a, 7b, 7c.
  • the comparator 5 is provided with an offset voltage 12. This allows the reference voltage to be further increased without the reference transistor 7 having to comprise further transistors and without a high reference current having to flow through the reference transistor 7.
  • the comparator 5 is a voltage comparator.
  • FIG. 5 therein is illustrated an embodiment of the DC/DC converter as a step-down converter according to the present invention.
  • the current-monitoring principle corresponds to that of FIG. 1.
  • like elements are designated by like reference characters and act in the same manner.
  • n-channel MOS transistors instead of n-channel MOS transistors, p-channel MOS transistors are used for the switching transistor 1 and the reference transistor 7. Accordingly, the ground connection and the terminal for the operating voltage V DD have been interchanged. Modifications of the reference transistor 7 and the reference current source 6 and the insertion of the auxiliary switching elements 9 and 10 are possible analogously to FIGS. 2, 3 and 4.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
US09/272,508 1998-03-20 1999-03-19 DC/DC converter Expired - Lifetime US6166526A (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE19812299A DE19812299A1 (de) 1998-03-20 1998-03-20 Gleichspannungswandler
DE19812299 1998-03-20

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EP (1) EP0944159B1 (de)
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Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6677738B1 (en) * 2002-08-23 2004-01-13 Texas Instruments Incorporated Overcurrent sensing using high side switch device in switching power converters
WO2003102749A3 (en) * 2002-05-28 2004-10-14 Sun Microsystems Inc Dynamic modulation of on-chip supply voltage for low-power design
US6867624B2 (en) 2000-01-19 2005-03-15 Koninklijke Philips Electronics N.V. Circuit for voltage level detection
EP1592117A1 (de) * 2004-04-30 2005-11-02 Texas Instruments Incorporated Gleichspannung- Hochfrequenz - Aufwärtswandler
US20060255774A1 (en) * 2005-05-10 2006-11-16 Mikio Motomori Step-up converter
US20090121696A1 (en) * 2007-11-09 2009-05-14 Upi Semiconductor Corporation Controller of DC-DC Converter And Controlling Method Thereof
US20120206123A1 (en) * 2011-02-11 2012-08-16 Michael David Mulligan Edge rate control gate driver for switching power converters

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE60045219D1 (de) * 2000-09-22 2010-12-23 Imec Verfahren und Vorrichtung zur Hochspannungserzeugung
US6531852B2 (en) 2000-09-22 2003-03-11 Interuniversitair Microelektronica Centrum (Imec) Device and method for generating a high voltage

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US4260946A (en) * 1979-03-22 1981-04-07 Rca Corporation Reference voltage circuit using nested diode means
US4584517A (en) * 1983-06-16 1986-04-22 Motorola, Inc. Self-oscillating DC-DC switching voltage regulator
DE3704609A1 (de) * 1986-02-13 1987-08-20 Toshiba Kawasaki Kk Vorrichtung zur erzeugung einer bezugsgleichspannung
JPH07110721A (ja) * 1993-08-17 1995-04-25 Mitsubishi Electric Corp 起動回路
EP0650250A1 (de) * 1993-10-22 1995-04-26 STMicroelectronics S.r.l. Gleichstromwandler im diskontinuierlichem Betrieb arbeitend
US5892389A (en) * 1997-06-03 1999-04-06 Motorola, Inc. Method and circuit for current limiting of DC-DC regulators
US5914589A (en) * 1996-09-04 1999-06-22 Stmicroelectronics, S.R.L. Voltage boosting circuit for high-potential-side MOS switching transistor
US5959439A (en) * 1997-05-23 1999-09-28 The Board Of Trustees Of The University Of Illinois Monolithic DC to DC converter

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JPH03296118A (ja) * 1990-04-13 1991-12-26 Oki Micro Design Miyazaki:Kk 基準電圧発生回路
US5646520A (en) * 1994-06-28 1997-07-08 National Semiconductor Corporation Methods and apparatus for sensing currents
US5723974A (en) * 1995-11-21 1998-03-03 Elantec Semiconductor, Inc. Monolithic power converter with a power switch as a current sensing element

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US4260946A (en) * 1979-03-22 1981-04-07 Rca Corporation Reference voltage circuit using nested diode means
US4584517A (en) * 1983-06-16 1986-04-22 Motorola, Inc. Self-oscillating DC-DC switching voltage regulator
DE3704609A1 (de) * 1986-02-13 1987-08-20 Toshiba Kawasaki Kk Vorrichtung zur erzeugung einer bezugsgleichspannung
JPH07110721A (ja) * 1993-08-17 1995-04-25 Mitsubishi Electric Corp 起動回路
EP0650250A1 (de) * 1993-10-22 1995-04-26 STMicroelectronics S.r.l. Gleichstromwandler im diskontinuierlichem Betrieb arbeitend
US5914589A (en) * 1996-09-04 1999-06-22 Stmicroelectronics, S.R.L. Voltage boosting circuit for high-potential-side MOS switching transistor
US5959439A (en) * 1997-05-23 1999-09-28 The Board Of Trustees Of The University Of Illinois Monolithic DC to DC converter
US5892389A (en) * 1997-06-03 1999-04-06 Motorola, Inc. Method and circuit for current limiting of DC-DC regulators

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Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6867624B2 (en) 2000-01-19 2005-03-15 Koninklijke Philips Electronics N.V. Circuit for voltage level detection
WO2003102749A3 (en) * 2002-05-28 2004-10-14 Sun Microsystems Inc Dynamic modulation of on-chip supply voltage for low-power design
US6677738B1 (en) * 2002-08-23 2004-01-13 Texas Instruments Incorporated Overcurrent sensing using high side switch device in switching power converters
US7180275B2 (en) 2004-04-30 2007-02-20 Texas Instruments Incorporated DC-DC high frequency boost converter
US20050242788A1 (en) * 2004-04-30 2005-11-03 Stefan Reithmaier DC-DC high frequency boost converter
EP1592117A1 (de) * 2004-04-30 2005-11-02 Texas Instruments Incorporated Gleichspannung- Hochfrequenz - Aufwärtswandler
DE102004021437B4 (de) * 2004-04-30 2007-08-23 Texas Instruments Deutschland Gmbh Gleichspannungs-Hochfrequenz-Aufwärtswandler
US20060255774A1 (en) * 2005-05-10 2006-11-16 Mikio Motomori Step-up converter
US7482789B2 (en) * 2005-05-10 2009-01-27 Panasonic Corporation Step-up converter
US20090121696A1 (en) * 2007-11-09 2009-05-14 Upi Semiconductor Corporation Controller of DC-DC Converter And Controlling Method Thereof
US8018218B2 (en) * 2007-11-09 2011-09-13 Upi Semiconductor Corporation Controller of DC-DC converter with input voltage and output voltage sensing from the phase node
US20120206123A1 (en) * 2011-02-11 2012-08-16 Michael David Mulligan Edge rate control gate driver for switching power converters
US8860398B2 (en) * 2011-02-11 2014-10-14 Fairchild Semiconductor Corporation Edge rate control gate driver for switching power converters
US9774240B2 (en) 2011-02-11 2017-09-26 Fairchild Semiconductor Corporation Edge rate control gate driver for switching power converters

Also Published As

Publication number Publication date
DE59913572D1 (de) 2006-08-03
EP0944159A3 (de) 2003-05-28
EP0944159A2 (de) 1999-09-22
EP0944159B1 (de) 2006-06-21
DE19812299A1 (de) 1999-09-30

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