WO2004105291A2 - Appareil de communication a bande ultra-large et debit binaire eleve et procedes associes - Google Patents

Appareil de communication a bande ultra-large et debit binaire eleve et procedes associes Download PDF

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Publication number
WO2004105291A2
WO2004105291A2 PCT/US2004/015060 US2004015060W WO2004105291A2 WO 2004105291 A2 WO2004105291 A2 WO 2004105291A2 US 2004015060 W US2004015060 W US 2004015060W WO 2004105291 A2 WO2004105291 A2 WO 2004105291A2
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Prior art keywords
signal
frequency
mixer
generator
transmitter
Prior art date
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WO2004105291A3 (fr
Inventor
Kazimierz Siwiak
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Time Domain Corp
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Time Domain Corp
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Priority claimed from US10/436,646 external-priority patent/US7206334B2/en
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Publication of WO2004105291A3 publication Critical patent/WO2004105291A3/fr
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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/7163—Spread spectrum techniques using impulse radio
    • H04B1/717—Pulse-related aspects
    • H04B1/7172—Pulse shape
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/02—Channels characterised by the type of signal
    • H04L5/023—Multiplexing of multicarrier modulation signals, e.g. multi-user orthogonal frequency division multiple access [OFDMA]
    • H04L5/026—Multiplexing of multicarrier modulation signals, e.g. multi-user orthogonal frequency division multiple access [OFDMA] using code division
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B2201/00—Indexing scheme relating to details of transmission systems not covered by a single group of H04B3/00 - H04B13/00
    • H04B2201/69—Orthogonal indexing scheme relating to spread spectrum techniques in general
    • H04B2201/7163—Orthogonal indexing scheme relating to impulse radio
    • H04B2201/71636—Transmitted reference

Definitions

  • This patent application relates generally to communication apparatus and, more
  • ultra- wideband (UWB) high data-rate (HDR) communication apparatus particularly, to ultra- wideband (UWB) high data-rate (HDR) communication apparatus.
  • UWB ultra- wideband
  • HDR high data-rate
  • IEEE 802.11b IEEE 802.11a
  • IEEE 802.11a IEEE 802.11a
  • the complex communication systems typically need significantly increased
  • One aspect of the invention relates to communication apparatus, such as
  • an RF transmitter according to the invention includes a reference
  • the reference signal generator provides a reference signal that has a prescribed or
  • the signal generator provides an operating signal in response to a
  • the operating signal has a frequency that equals the frequency of the
  • the reference signal multiplied by a number. More particularly, in some embodiments, the
  • number may constitute an integer number, whereas in other embodiments, the number
  • the mixer mixes the operating signal
  • an RF receiver according to the invention
  • the receiver includes two mixers, a first mixer and a second mixer.
  • the receiver further includes an
  • the first mixer receives as its inputs an input RF signal and a second input signal.
  • the first mixer mixes its input signals to generate a mixed signal.
  • the integrator/sampler receives the mixed signal and processes it to provide an output signal. The signal
  • the number may constitute an integer
  • the number may constitute a non-integer number
  • the second mixer mixes the operating signal with a template signal to
  • FIG. 1 shows several power spectral density (PSD) profiles in various scenarios
  • FIG. 2 illustrates exemplary signal waveforms corresponding to a high data-rate
  • FIG. 3 depicts an exemplary embodiment of a high data-rate UWB transmitter
  • FIG. 4 shows exemplary waveforms corresponding to a high data-rate UWB
  • FIG. 5 illustrates an exemplary embodiment of high data-rate UWB receiver
  • FIG. 6 depicts exemplary waveforms corresponding to a high data-rate UWB
  • FIG. 7 shows the timing relationship among various signals in a high data-rate
  • FIG. 8 illustrates exemplary desired or prescribed PSD profiles that correspond to
  • FIG. 9 shows a PSD profile for an exemplary embodiment of the invention that
  • FIG. 10 illustrates an illustrative PSD profile in an exemplary embodiment
  • FIG. 11A shows one cycle of an exemplary output signal of a transmitter in a
  • FIG. 1 IB illustrates one cycle of another exemplary output signal of a transmitter
  • FIG. 12 depicts a timing relationship between several signals in an exemplary
  • FIG. 13 shows several PSD profiles for an illustrative embodiment according to
  • FIG. 14 illustrates several PSD profiles for other exemplary embodiments
  • FIG. 15 depicts PSD profiles for other illustrative embodiments according to the
  • FIG. 16 shows PSD profiles for other exemplary embodiments of communication
  • FIG. 17 illustrates an exemplary embodiment according to the invention of a
  • FIG. 18 depicts illustrative chipping sequences for use in communication systems
  • FIG. 19 shows an exemplary embodiment 19 of a differential receiver according
  • FIG. 20 illustrates a set of offset quadrature phase shift keyed (OQPSK) UWB
  • FIG. 21 depicts a set of chipping signal waveforms in an exemplary embodiment
  • FIG. 22 shows an exemplary embodiment of a transmitter according to the
  • FIG. 23 illustrates an exemplary embodiment of a receiver according to the
  • FIG. 24 depicts a sample waveform in an illustrative embodiment according to the
  • FIG. 25 shows a Fourier transform of the signal in FIG. 24.
  • FIG. 26 illustrates sample waveforms in an exemplary embodiment of a
  • FIG. 27 depicts an exemplary in-phase channel pulse as a function of time in an
  • FIG. 28 shows the magnitude of the spectrum of the signal in FIG. 27.
  • FIG. 29 illustrates an exemplary quadrature channel pulse as a function of time in
  • FIG. 30 depicts the magnitude of the spectrum of the signal in FIG. 29.
  • FIG. 31 shows two signals as a function of time in illustrative embodiments
  • FIG. 32 illustrates the spectra resulting from using the signal shaping shown in
  • FIG. 33 depicts two signals as a function of time in other illustrative embodiments
  • FIG. 34 shows the spectra resulting from using the signal shaping shown in FIG.
  • This invention contemplates high data-rate communication apparatus and
  • Communication apparatus provide a
  • a high data-rate UWB Ultra-data-rate
  • BPSK binary phase shift keying
  • PSD power spectral density
  • j denotes the reference clock frequency
  • n represents the number of carrier
  • a chip refers to a signal element, such as depicted in FIG. 11A or FIG. 1 IB. Put another
  • a chip refers to a single element in a sequence of elements used to generate the
  • the transmitted signal results from multiplying the sequence of chips
  • the chip sequence by a spreading code, i.e., the code that spreads the transmitted signal spread over a relatively wide band.
  • a spreading code i.e., the code that spreads the transmitted signal spread over a relatively wide band.
  • the modulation chipping rate is commensurate with the
  • n is a relatively small number.
  • n has a value of less than ten, such as 3 or 4.
  • n in the range of 1 to 500, or 1 to 42.
  • n (rounded up to an integer value) corresponds to approximately the
  • n in the range of 1 to 42. More specifically, a 500-MHz-wide UWB system
  • the FCC has also allowed UWB signals of at least a 500-MHz bandwidth in the
  • the signal bandwidth varies inversely with the value of n.
  • FIG. 1 illustrates several PSD profiles for various values of n (the number of
  • PSD profile 11 corresponds to n - ⁇ , whereas PSD profile 12
  • PSD maximum spatial frequency
  • bandwidth depends on the chip rate, as manifested by the parameter n.
  • FIG. 2 depicts various signals corresponding to a BPSK
  • Carrier signal 21 may include only a fundamental frequency.
  • carrier signal 21 may include
  • FIG. 2 also shows a pseudo-random noise (PN)
  • n — 1 one chip per RF cycle (i.e., n — 1), and 4 chips per data bit.
  • the third waveform in FIG. 2 corresponds to data bits 23. Beginning at time 27
  • PN sequence 22 codes data bits 23.
  • Signal 24 modulates carrier 21 to generate modulated signal 25.
  • Signal 26 acts a gating signal. Put another way, the commumcation system transmits
  • Modulated signal 25 has a spectrum substantially the same as spectrum 11 in
  • FIG. 1 i.e., the case where the parameter n has a value of unity.
  • One may determine the data-rate or data throughput of the communication system
  • n ⁇
  • invention includes a high data-rate UWB transmitter and a high data-rate UWB receiver.
  • FIG. 3 shows an exemplary embodiment of high data-rate UWB transmitter 4 according
  • Transmitter 4 includes reference clock 41 (a reference clock generator), timing
  • controller 42 data buffer 43, PN generator 45 (a pseudo-random noise sequence
  • Reference clock 41 generates a signal with a desired frequency.
  • reference clock 41 corresponds to a carrier frequency for transmitter 4.
  • reference clock 41 corresponds to the desired carrier frequency.
  • Reference clock 41 couples to harmonic generator 49. Based a clock signal it
  • harmonic generator 49 generates one or more
  • harmonics of the carrier frequency (the frequency of clock reference 41). For example,
  • Harmonic generator 49 generates the one or
  • the reference clock i.e., the one or
  • harmonic generator 49 in a number of ways, for
  • divider circuitry By dividing a signal of a given frequency by various integers, one may
  • fractional-N synthesizers as desired.
  • a comb line generator may provide
  • Mixer 47 receives the one or more harmonics from harmonic generator 49. Mixer
  • Mixer 47 provides the
  • Antenna 48 propagates those signals into the
  • antenna 48 may constitute a wide ⁇
  • wide-band antennas examples include those described in the following patent
  • wire segment as a simple, effective, wide-band radiator.
  • wire segment as a simple, effective, wide-band radiator.
  • antennas for example, horn antennas, are of the "constant aperture” variety, and produce
  • Reference clock 41 also couples to timing controller 42.
  • Timing controller 42
  • timing controller 42 clocks the data in data buffer 43. Note that timing signals from timing controller 42 also generate timing signals from timing controller 42.
  • Data buffer 43 receives its input data from data port 44.
  • sequence from PN generator 45 modulates the data from data buffer 43 by using data/PN
  • data/PN combiner 46 constitutes an exclusive-OR (XOR) gate, although
  • unequal amplitudes By using unequal amplitudes,
  • FIG. 16 shows an example of such a
  • FIG. 4 illustrates exemplary waveforms corresponding to high data-rate UWB
  • Signal 421 corresponds to the output of harmonic generator 49.
  • Signal 422
  • transmitter 4 constitutes the output signal of reference clock 41.
  • chip sequences longer than 4 chips per bit may be desirable. For example, one may use such chip sequences when the
  • transmission medium constitutes an RF channel with substantial multipath, or when one
  • number of chips per bit may be very broad, as desired, depending on the design and
  • the number of the PN chips per data bit is a measure of coding
  • data/PN combiner 46 may implement data/PN combiner 46 using an exclusive-OR
  • Signal 424 depicts the result of an exclusive-OR operation on signals 422 and 423.
  • Modulated RF signal 425 results from combining signal 421 and signal 424 in mixer 47.
  • Timing signal 426 depicts the transmission time for the sequence of data bits 423.
  • FIG. 5 illustrates an exemplary embodiment of high data-rate UWB receiver 5
  • Receiver 5 includes reference clock 53, tracking loop 52,
  • integrator/sampler 51 PN generator 55, data/PN combiner 56, mixer 57, antenna 58, and
  • harmonic generator 59 Similarly named blocks and components in receiver 5 may have
  • Integrator/sampler 51 integrates the
  • Mixer 57 also receives template signal 567.
  • Data/PN combiner 56 generates
  • data/PN combiner 56 constitutes an exclusive-OR (XOR) gate, although one may use other suitable circuitry, as persons of
  • Harmonic generator 59 operates in a similar manner as harmonic generator 49 in FIG. 3,
  • a tracking loop 52 controls reference clock 53 and PN
  • Tracking loop 52 controls the timing of PN generator 55 for proper signal
  • Reference clock 53 provides reference clock
  • tracking loop 52 may implement tracking loop 52 in a variety of ways, as desired.
  • Tracking loop 52 operates in conjunction with template signal 567 to provide a locking
  • template receiver or matched template
  • Mixer 57 mixes the signal received from antenna 58 with template signal 567 to
  • Integrator/sampler 51 integrates signal 568 to generate recovered data signal 563. Integrator/sampler 51 drives tracking loop 52, which controls signal
  • FIG. 6 illustrates exemplary waveforms corresponding to high data-rate UWB
  • Signal 562 constitutes the output of PN generator 55.
  • Signal 561 conesponds
  • Signal 568 constitutes the output signal of mixer 57, which feeds
  • FIG. 7 shows further details of the timing relationship among various signals in
  • Waveform 76 shows the
  • transmission periods i.e., periods of time during which transmitter 4 transmits.
  • waveform 73 illustrates data bit stream 73 during transmission periods 76.
  • Waveform 79
  • Each mode may generate a particular or prescribed PSD profile by using
  • transmitter 4 By selecting a particular mode, one may operate transmitter 4 such
  • FIG. 8 depicts two exemplary desired or prescribed PSD profiles that conespond
  • a transmitter according to the invention is to the two modes of operation in such embodiments.
  • a transmitter according to the invention is to the two modes of operation in such embodiments.
  • inventions may produce outputs that conform to a selected one of predetermined PSD
  • the frequency of the reference clock i.e., the frequency of the reference clock
  • second and third harmonics appear at approximately 3.6 GHz and 5.4 GHz, respectively.
  • the transmitter has a chipping rate of 1.8 giga-chips per second.
  • transmitted PSD profile 83 has a substantially flat shape, and conforms to PSD mask 80 (i.e., it remains under
  • the transmitter has a chipping rate of
  • UWB apparatus that includes m operating modes, where m denotes an integer larger than
  • selectable harmonic filters i.e., selectable choice of which
  • harmonic orders to use to select any combination of one or more harmonics.
  • UWB radio apparatus may selectively avoid interference from or with other radio systems
  • FIG. 9 shows a PSD profile for an exemplary embodiment of the invention that
  • PSD profile 91 assumes modulation
  • PSD profile 92 and PSD profile 93 have substantially flat shapes. Note further that both PSD profile
  • PSD profile 93 conform to a prescribed or desired PSD amplitude profile mask
  • reference parameters and the harmonic carriers are selected so that the PSD of the high
  • the reference clock has a frequency of
  • the transmitter uses as " carrier frequencies
  • harmonics of the reference clock frequency i.e., 3.3 GHz and 4.4 GHz, respectively.
  • FIG. 10 shows an exemplary PSD profile for such an embodiment of the
  • Transmission PSD profile 101 fits between the 2.4 GHz ISM band 102 and
  • Signal harmonics may be added with a selectable, desired, or designed degree of
  • phase angle between 0 and 2 ⁇ radians Note that in exemplary embodiments according to
  • FIG. 11A illustrates one cycle of an
  • ending point 123 coincide with the chip boundaries, as illustrated, for example, by signal
  • xi(t) cos(2 ⁇ -3-f r t) + cos(2 ⁇ -4f r t + ),
  • f r represents the reference clock frequency and ⁇ denotes a selectable or
  • Output signal 121B has starting point
  • QPSK quadrature keying
  • signals 121 A and 12 IB have relatively small signal levels at both their
  • starting points i.e., 122A and 122B, respectively
  • ending points i.e., 123A and
  • Exemplary embodiments according to the invention switch signals ON and OFF
  • harmonic carriers by a composite signal S that constitutes a summation of sinusoidal
  • composite signal S constitutes a sum of harmonic carriers over a selected range, n.
  • n may range from 3 to 4 (conesponding to
  • FIG. 12 shows the timing relationship between several signals in such an
  • Signal 139 depicts a reference clock
  • Signal 131 conesponds to composite signal S, described above.
  • Signal 132
  • Reference clock signal 139 conesponds to the positive-going zero-crossings of sinusoidal
  • time displacement offsets the chipping signal from the carrier signal.
  • time displacement s appears as an offset between reference clock
  • FIG. 12 shows signals conesponding to several values of time displacement s.
  • Each time displacement s signifies the offset between reference clock signal 139 (or
  • chipping signal 133 conesponds to a time
  • Chipping signal 134 and chipping signal 135 denote,
  • FIG. 12 illustrates the chipping sequence "101" as an
  • FIG. 13 illusfrates several PSD profiles for an illustrative embodiment according
  • PSD profile 143 depicts the power spectral density of signal 131
  • PSD profile 144 conesponds to the
  • PSD profile 145 illustrates the power spectral density of signal 131 multiplied by PN
  • FIG. 13 also illustrates boundary 146 of the 2.4 GHz ISM band and boundary 147
  • FIG. 14 depicts several PSD profiles that conespond to exemplary
  • PSD profile 151 includes PSD profile 151, PSD profile 152, and PSD profile 153.
  • profile 152 pertains to a signal that includes the second through the seventh harmonics
  • PSD profile 153 conesponds to a
  • FIG. 14 illustrates. As noted above, using larger numbers of harmonics while
  • Transform of the composite signal S More specifically, where the data pulses have a generally rectangular shape and have not been filtered (e.g., chipping signal 422 in FIG.
  • the harmonics used i.e., the lower and upper boundaries of the range of harmonics used.
  • FIG. 15 shows an example of applying this technique.
  • PSD profile 161 shows the power spectral density for an
  • PSD profile 162 conesponds
  • PSD profile 163 conesponds to a system that uses the third
  • the system may effectively coexist with systems that operate in the 5-GHz UNII band. Note that one may use
  • design parameters e.g., clock frequency and the number and order of design parameters
  • FIG. 16 shows PSD profiles for other exemplary embodiments of communication
  • the mask specifies emissions at 10.6 GHz of at least -10
  • UNII band 267 extends from 5.15 GHz to approximately 5.9 GHz.
  • PSD profiles denotes four PSD profiles (denoted as profiles 261, 262, 263, and 264, respectively)
  • PSD profiles 261, 262, 263, and 264 denote various choices of
  • PSD profile 261 conesponds to a communication system
  • PSD profile 262 conesponds to a system that employs the 3rd, the 5th, the 6th,
  • the system conesponding to PSD profile 263 uses the 3rd through the 6th
  • PSD profile 264 pertains to a communication system that uses the 3rd, the 5th,
  • This system omits the fourth harmonic, which overlaps UNII band 267.
  • the system may switch its operation modes
  • the invention may include multi-mode operation. Such systems may switch from one
  • controller input signal 40 enables mode switching in
  • timing controller 42 determines the chipping duration relative to the reference clock cycle in a manner apparent to persons of ordinary skill in the art who have the benefit of
  • Communication systems according to the invention may perform mode switching
  • switching may occur in an automatic manner, for instance, in response to predetermined
  • the mode switching may occur in a semi-automatic manner
  • an internal or external variable or quantity for example,
  • the communication system may switch the operating mode.
  • radio-signal energy in a desired band or bands For example, in response to detecting the
  • UWB communication apparatus or system according to the invention may switch its
  • the new mode of operation may conespond to a PSD profile that tends to eliminate, reduce, or
  • the new PSD profile may constitute PSD profile 163 in FIG. 15.
  • the stimulus for the switching of modes in such systems is the detection of
  • FIG. 17 shows an exemplary embodiment according to the invention of a
  • transceiver 111 which has internal power source 112
  • System 11 also includes second transceiver 113,
  • the mode e.g., a battery or other power source.
  • the mode e.g., a battery or other power source.
  • PSD mask may operate in a mode that conforms to a particular PSD profile, for example, PSD mask
  • This mode may conespond, for example, to system operation indoors.
  • transceiver 111 and supplied through port 116 to transceiver 113), it may operate in
  • PSD mask 82 another mode that conforms to a different PSD profile, for example, PSD mask 82 in
  • the second mode may conespond, for example, to system operation outdoors.
  • UWB communication systems can meet more stringent PSD masks outdoors and yet conform to a more
  • system 11 senses the application of external power
  • timing controller 42 and harmonic generator 49 adjust pre-determined timing parameters
  • companion or conesponding transceiver similarly adjusts parameters in its transmitter
  • circuitry receives.
  • FIG. 17 shows a pair of transceivers
  • Another aspect of the invention relates to the shape of the pulses within chipping
  • Chipping signal 422 includes pulses
  • mixer 47 shifts that spectrum in the frequency domain and centers a copy of the
  • the pulses may have a more "rounded" shape.
  • One example of a more "rounded" pulse shape is the Gaussian impulse.
  • ⁇ denotes a parameter that defines the pulse width.
  • FIG. 18 shows a Gaussian impulse as one example.
  • chipping signal 133 chipping signal 134
  • chipping signal 135 chipping signal 135 in FIG. 12, as
  • PSD dt where p(t) denotes the baseband filtered data signal.
  • p(t) denotes the baseband filtered data signal.
  • p(t) denotes the baseband filtered data signal.
  • FIG. 18 shows chipping sequence 422 and chipping sequence 222 as
  • Quadrature phase shift keying (QPS ) systems quadrature phase shift keying (QPS ) systems.
  • QPS quadrature phase shift keying
  • OQPSK offset QPSK
  • embodiments using QPSK use two harmonic carriers, which
  • phase difference between the two reference clocks and an additional phase delay in one of the harmonic generator lines provide the
  • a QPSK-like UWB system according to the invention
  • OQPSK system has the additional desirable property of a smoothed PSD spectrum or
  • FIG. 20 shows one example of the waveforms of an OQPSK UWB signal set in
  • Signal 2110 comprises sinusoidal harmonics, such as the
  • signal shown in FIG 11 A while signal 2130 comprises cosinusoidal harmonics, like the
  • FIG. 11B illustrates. Data sfream 2120 modifies the polarity of signal 2110, and
  • data stream 2140 modifies the polarity of signal 2130, independent of data signal 2120.
  • the signal 2130 is furthermore shifted in time to the right of signal 2110 so that
  • the maximum envelope value 2135 of signal 2130 substantially conesponds with the
  • Signal 2150 represents the sum of quadrature signals 2110 and 2130. Persons of
  • the peak-to-average value of the composite signal is smaller than the peak-to-average
  • DPSK shift keying
  • transmitter 4 in FIG. 3 to generate DPSK signals, as persons of ordinary
  • Transmitter 4 generates DPSK signals as follows. Referring to FIG. 3, transmitter 4
  • Transmitter 4 encodes the data differentially, similar to
  • transmitter 4 encodes the data as changes in the
  • transmitter 4 it indicates that transmitter 4 had sent a "0” previously (no change). On the other hand, if a "0” follows the original "1,” then transmitter 4 encodes a "1.” Thus, transmitter
  • transmitter 4 encodes changes from 1 to -1 (or -1 to 1) as binary "l”s. Conversely, transmitter 4
  • data buffer 43 may perform the differential encoding
  • PN generator 45 generates chip sequences associated with a delay or
  • time period D that equals the number of chips for a single data bit.
  • the time delay D may
  • D may be the number of chips
  • Each chip sequence is equal in length to
  • transmitter 4 uses Barker sequences of
  • Table 2 also constitute Barker codes. Furthermore, the inverse of the listed code
  • Barker codes rather than using Barker codes, one may use other types of code, as
  • PN generator 45 multiples each bit obtained from data buffer 43 with the Barker
  • the signal 424 (output signal of data/PN combiner 46) constitutes
  • Barker sequence or the inverse of a Barker sequence (i.e., obtained by
  • the generator uses a Barker code of length 11 , the time period or delay D equals the length of
  • FIG. 12 illustrates one chip time, which relates to Barker
  • FIG. 19 illustrates an exemplary embodiment 19 of a differential receiver
  • antenna 910 includes antenna 910, mixer 916, integrator 918, sample-and-hold 920, and analog-to-
  • ADC analog digital converter 922.
  • Receiver 19 may optionally include amplifier 912 and
  • Antenna 910 receives differentially encoded signals.
  • Amplifier 912 amplifies the
  • the delay D provided by delay device 916 equals one bit time. Accordingly,
  • mixer 916 multiplies the received signal by a version of the received signal delayed by a
  • mixer 916 feeds integrator 918.
  • the output of mixer 916 feeds integrator 918.
  • Sample-and-hold 920 samples the output signal of integrator 918
  • Sample-and-hold 920 provides the sampled signal
  • ADC 922 provides output data bits.
  • the length of the integration may be the
  • time period D Based on design and performance specifications, however, one may use
  • Optional amplifiers 912 and optional amplifier 914 may constitute either linear
  • amplifiers or limiting amplifiers as desired.
  • delay device 916 may implement delay device 916 in a variety of ways, as persons of ordinary
  • a relatively simple delay device comprises a length of transmission line that has
  • Mixer 916 may have a variety of structures and circuitry,
  • mixer 916 may constitute a passive ring diode mixer
  • the data bits constitute a length D equal to the
  • Such systems modulate the phase of the carrier (0 or ⁇ d2 radians)
  • Barker encoded sequence of harmonic wavelets as shown, for example,
  • apparatus modulate the polarity of the wavelets (i.e., +1 or -1) at the chip rate. Furthermore, they polarity modulate the chip sequences at the bit rate.
  • the bit time (see signal 563 in FIG. 6) comprises a
  • receiver 19 and associated circuitry may perform additional tasks
  • such circuitry may recover the data bits, recover timing of
  • Barker codes More specifically, one may use Barker codes of
  • N 2, 3, 4, 5, 7, 11, and 13.
  • Barker code of length 7 see Table 2, above
  • sequence -1 -1 -1 1 1 -1 1 i.e., a sequence obtained by multiplying by -1
  • the spectrum of the resulting signal more closely resembles white noise (i.e., the
  • CDMA code division multiple access
  • the PN sequence (at the chipping rate) with a Hadamard code or a Walsh code (i.e.,
  • ECC enor-conection coding
  • ECC ECC
  • the carrier signal (e.g., carrier signal 21 in FIG. 2) may constitute
  • FIG. 21 shows examples of some signal
  • FIG. 21 includes a repeating
  • signal 2021 may have a gap 2023 of an arbitrary length
  • Another aspect of the invention relates to multiple independently modulated
  • harmonic signals e.g., harmonics of a given frequency, such as a clock frequency.
  • the effective data rate constitutes the sum of all
  • the harmonic signals are not ON or enabled simultaneously. In effect, one
  • the communication apparatus or system simplifying the communication apparatus or system.
  • Such apparatus or systems may operate in an environment
  • harmomc signal (as the embodiments described above do). Note, of course, that one may
  • systems according to the invention transmit one impulse on a given harmonic frequency or channel and then wait for the multipath echoes on that channel to decay before
  • FIG. 22 shows an exemplary embodiment of a transmitter 2200 according to the
  • FIG. 22 separate circuitry that operates at relatively lower frequency from other circuitry
  • Reference clock 41 generates a signal with a desired frequency, for example, a
  • reference clock 41 may implement reference clock 41 in a number of
  • Reference clock 41 couples to harmonic generator 2220. Based a clock signal it
  • harmomc generator 2220 receives from reference clock 41, harmomc generator 2220 generates an mtb harmonic
  • a second harmonic signal at the output of harmomc generator 2220 has a frequency
  • harmonic generator 2220 in a number of ways
  • harmonic generator 49 similar to harmonic generator 49, described above.
  • the frequency synthesizer By varying the control signal of the frequency synthesizer (e.g., a
  • control voltage one may vary the output frequency of the frequency synthesizer.
  • Harmonic generator 2220 generates the harmonic signals synchronously with
  • Transmitter 2200 may also include signal shaping circuitry 2218 and mixer 2202.
  • mixer 2202 generates an output signal 2208 that constitutes shaped data
  • Transmitter 2200 also includes mixer 2204 and antenna 48. Output signal 2208
  • mixer 2204. The output signal of mixer 2204 constitutes modulated RF
  • Antenna 48 accepts modulated RF signals 2212 from mixer 2204 and
  • mixer 2202 by using integer or non-integer values of m, as desired.
  • operating frequency of output signal 2208 of mixer 2202 need not (but may) constitute an
  • integer harmonic of the clock signal may relate to the clock frequency in any way.
  • the clock frequency may constitute a fraction of
  • synthesizers such as fractional-M synthesizers, to generate such operating frequencies, as
  • FIG. 23 illustrates an exemplary embodiment of a receiver 2300 according to the
  • antenna 58 includes antenna 58, mixer 2314, mixer 2316, integrator/sampler (integrator/sarnple-and- hold) 2303, controller 2306, baseband template generator 2312, phase-locked loop (PLL)
  • Antenna 58 receives RF signals and provides them to one input of mixer 2314.
  • Output signal of mixer 2316 constitutes a second input of mixer 2314.
  • template generator 2312 generates a template signal that constitutes one input of mixer
  • the output of harmonic generator 2220 constitutes a second input of mixer 2316.
  • the output of baseband template generator 2312 matches the output of signal
  • PLL 2319 generates a first output signal, reference signal 2322, which it provides
  • reference signal 2322 When receiver 2300 locks onto a desired RF signal, reference signal 2322
  • reference signal 2322 constitutes a signal similar to
  • PLL 2319 generates reference signal 2322 such that it has a frequency f osc .
  • PLL 2319 generates a second output signal 2328, which has a frequency f osc , that
  • Harmonic generator 2220 operates as described above in
  • harmonic generator 2220 provides a
  • mixer 2316 feeds one input of mixer 2314.
  • Receiver 2300 uses the output of mixer 2314 to control the feedback loop that includes
  • the control loop includes integrator/sampler 2303, controller 2306, and PLL 2319.
  • the output of mixer 2314 feeds the input of integrator/sampler 2303. Depending on the input of integrator/sampler 2303. Depending on the input of integrator/sampler 2303.
  • integrator/sampler 2303 provides one of
  • receiver 2300 receives a binary zero
  • output of integrator/sampler 2303 may constitute a negative voltage. Conversely, if
  • integrator/sampler 2303 may provide a positive
  • integrator/sampler 2303 feeds an input of controller 2306.
  • Controller 2306 generates a datum value depending on the voltage level it receives from
  • integrator/sampler 2303. in response to a positive voltage present at the output of integrator/sampler 2303, controller 2306 may generate a binary one bit that has
  • controller 2306 may perform filtering, shaping, and the like, of the data
  • Controller 2306 also provides feedback control signal 2325 to PLL
  • controller 2306 decides the value of m and provides that value to harmonic generator
  • harmonic generator 2220 generates as its output the r ⁇ fh
  • the receiver and the transmitter use various values of m according to the pre ⁇
  • the feedback loop uses
  • baseband template generator 2312 to provide a locking mechanism for receiving a transmitted signal (i.e., a template receiver or matched template receiver), as persons
  • value of m as a function of time varies the use of those channels as a function of time.
  • Table 3 shows an example of a channel frequency and timing plan in an
  • the apparatus or system uses six channels. Furthermore, the apparatus or system uses six time slots, each with an
  • m ranges from 28 to 38.
  • the channels range in frequency from 3.50
  • m 34 conesponds to a frequency of 4.25 GHz, which conesponds to channel 4, and so
  • the frequency shown in the second column of Table 3 denotes the frequency of the harmonic signal that is ON or enabled (i.e., modulated and transmitted by the

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  • Engineering & Computer Science (AREA)
  • Signal Processing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Transmitters (AREA)
  • Superheterodyne Receivers (AREA)

Abstract

L'invention concerne un émetteur RF comprenant un générateur de signaux de référence, un générateur de signaux, et un mélangeur. Le générateur de signaux génère un signal de référence avec une fréquence prédéterminée ou désirée. Le générateur de signaux génère un signal de fonctionnement en réponse à un signal de sélection. Le signal de fonctionnement possède une fréquence égale à la fréquence du signal de référence multipliée par un nombre. Le mélangeur mélange le signal de fonctionnement avec un autre signal pour générer un signal de transmission. Un récepteur RF comprend un premier mélangeur, un second mélangeur, un intégrateur/échantillonneur, et un générateur de signaux. Le premier mélangeur reçoit un signal RF d'entrée et un second signal d'entrée, et mélange lesdits signaux d'entrée pour générer un signal mélangé. L'intégrateur/échantillonneur reçoit le signal mélangé et traite celui-ci pour obtenir un signal de sortie. Le générateur de signaux génère un signal de fonctionnement en réponse à un signal de sélection. Le signal de fonctionnement possède une fréquence égale à la fréquence d'un signal de référence, multipliée par un nombre. Le second mélangeur mélange le signal de fonctionnement avec un signal modèle pour générer le second signal d'entrée du premier mélangeur.
PCT/US2004/015060 2003-05-13 2004-05-13 Appareil de communication a bande ultra-large et debit binaire eleve et procedes associes Ceased WO2004105291A2 (fr)

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US10/436,646 US7206334B2 (en) 2002-07-26 2003-05-13 Ultra-wideband high data-rate communication apparatus and associated methods
US10/436,646 2003-07-22

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CA2120077A1 (fr) * 1993-06-17 1994-12-18 Louis Labreche Systeme et methode de modulation de frequence de porteuse
SE510310C2 (sv) * 1996-07-19 1999-05-10 Ericsson Telefon Ab L M Förfarande jämte anordning för rörelse-esimering och segmentering
US6026125A (en) * 1997-05-16 2000-02-15 Multispectral Solutions, Inc. Waveform adaptive ultra-wideband transmitter
US6603818B1 (en) * 1999-09-23 2003-08-05 Lockheed Martin Energy Research Corporation Pulse transmission transceiver architecture for low power communications
US6668008B1 (en) * 2000-06-06 2003-12-23 Texas Instruments Incorporated Ultra-wide band communication system and method

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