WO2006098703A1 - Circuit et procede pour la regulation d'un moteur a reluctance - Google Patents

Circuit et procede pour la regulation d'un moteur a reluctance Download PDF

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Publication number
WO2006098703A1
WO2006098703A1 PCT/SI2006/000003 SI2006000003W WO2006098703A1 WO 2006098703 A1 WO2006098703 A1 WO 2006098703A1 SI 2006000003 W SI2006000003 W SI 2006000003W WO 2006098703 A1 WO2006098703 A1 WO 2006098703A1
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Prior art keywords
motor
circuit
voltage
power grid
current
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Ceased
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PCT/SI2006/000003
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English (en)
Inventor
Mitja Rihtarsic
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DOMEL ELEKTROMOTORJI IN GOSPODINJSKI APARATI DD
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DOMEL ELEKTROMOTORJI IN GOSPODINJSKI APARATI DD
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Publication of WO2006098703A1 publication Critical patent/WO2006098703A1/fr
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P1/00—Arrangements for starting electric motors or dynamo-electric converters
    • H02P1/16—Arrangements for starting electric motors or dynamo-electric converters for starting dynamo-electric motors or dynamo-electric converters
    • H02P1/163—Arrangements for starting electric motors or dynamo-electric converters for starting dynamo-electric motors or dynamo-electric converters for starting an individual reluctance motor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H02P25/092—Converters specially adapted for controlling reluctance motors

Definitions

  • the invention relates to a circuit and a method for controlling a reluctance motor, powered from the public power transmission system (the power grid) , and, in particular, it relates to a method of operation which allows the drive electronics to have fewer subsystems and consequently to be cheaper.
  • the universal collector motors are mainly used for their convenience. They consist of a stator with windings, a rotor with windings, and of brushes and a collector which commutate the current in the windings of the rotor. Due to the friction with the collector the brushes get worn out, causing such motors to have a short life span. Moreover, the brushes decay into dust that pollutes the environment. Also, the rubbing of the brushes against the collector gives rise to acoustic noise. In addition to this, sparkling takes place at the edge of the brushes, which is a source of radiofrequency interference.
  • Universal collector motors may be controlled by means of a simple and cheap electronic circuit, illustrated in Figure 1.
  • the universal collector motor 2 is connected in series with a triac 3, triggered by the triggering circuit 4.
  • the motor is controlled by means of the aperture angle a.
  • the triggering circuit 4 opens the triac 3.
  • the current from the power grid i ac starts to flow and keeps on flowing until the end of the half period of the power grid voltage u AC -
  • the triac 3 closes when the current passing through the said triac and consequently through the universal collector motor 2 drops to zero.
  • the procedure is repeated every half period of the power grid voltage U ⁇ C -
  • the time diagrams 5 show the case in which the aperture angle a is small, determining, in turn, a small power and speed of the universal collector motor 2.
  • the time diagrams 6 show the case in' which the aperture angle a is large. The highest power and speed are achieved when the aperture angle a is equal to the half period of the power grid voltage u AC .
  • a brushless drive with a brushless permanent magnet motor or a brushless drive with a reluctance motor might be used instead of a drive with a universal collector motor.
  • the current passing through the windings is commutated by the electronics which are an integral part of the brushless drive and are complex and consequently expensive.
  • the elevated price as compared to drives with a universal collector motor curtails the use of the brushless drives in high volume consumer appliances.
  • the brushless drive exhibits no technical limitations that are o present in drives with universal collector motors and arise from the use of brushes and collectors.
  • a lower price would open the possibilities for employing brushless drives in high volume consumer appliances.
  • the price of the drive may be cut down by reducing the number of electronic components utilized, which is to say the number of components of the electronic circuitry.
  • the motor 12 may be a brushless permanent magnet motor having any number of phases, or a reluctance motor having any number of phases.
  • the phase windings of the motor 12 are connected to the power output stage 11, composed of semiconductor switches which commutate the electric current in the phase windings of the motor 12. This rectifying of the current must take place in accordance with the rotational offset of the rotor of the motor 12, as measured by the sensor 15.
  • the said sensor 15 is generally made of Hall sensors. More expensive embodiments of the said sensor 15 comprise optical position transducers.
  • the recent developments in processor semiconductor circuits have made it possible for sensorless brushless drives to be constructed wherein the motor 12 comprises no sensor 15 on the shaft.
  • the motor 12 is mechanically simpler.
  • the required information on the actual rotational offset of the shaft of the motor 12 in sensorless brushless drives is obtained from the measured electrical quantities and the recalculation thereof in processor semiconductor circuits.
  • the information about the actual rotational offset of the shaft is required by the commutation logic 14 which opens the semiconductor switches in the power output stage 11.
  • the power output stage 11 gets the electric power from the intermediate direct current circuit 10.
  • a smoothing capacitor 13 is used to store electric energy.
  • the smoothing capacitor 13 is an electrolytic capacitor. Its capacity depends upon the power of the drive and generally ranges from 100 ⁇ F to several 1000 ⁇ F. Since the smoothing capacitor 13 is large, it constitutes a considerable part of the overall electronics.
  • the smoothing capacitor 13 Before the smoothing capacitor 13 there is a power factor corrector 9 which shapes the electric current from the power grid i AC . If the electronics did not comprise a power factor corrector 9, the smoothing capacitor 13 would only get filled in the proximity of the peak of the power grid voltage U ⁇ C , and the amplitude of the filling current and consequently of the power grid current i ac would be very big, as shown in the time diagrams 20 in Figure 4. The rest of the time the power grid current i ⁇ C would be zero. Given that thus shaped power grid current i AC heavily pollutes the public power grid, the electromagnetic compatibility standards EN61000-3-2 limit the content of higher harmonic components in the electric current drawn by appliances from the public power grid. By means of the power factor corrector 9, the smoothing capacitor 13 is filled in such a way that the current from the power grid i AC contains fewer higher harmonic components and/or that said higher harmonic components are low enough to comply with the standard EN61000-3-2.
  • the power factor corrector 9 may be embodied as a passive filter or as a switching converter.
  • the passive filter requires a large choke coil, the reactance of which greatly reduces the voltage in the intermediate direct current circuit 10. Being large, the choke coil is also heavy and expensive. Because of the reduced voltage and its weight and price, this embodiment of the power factor corrector 9 is less convenient for use in high volume consumer appliances.
  • the power factor corrector 9 with a switching converter is composed of a choke coil, a semiconductor switch, a semiconductor diode, and the controller circuitry which switches on the semiconductor switch. In this embodiment, the choke coil is smaller as compared to the passive filter embodiment, making the whole circuit lighter. In spite of that, the switching converter with all the required elements is still large and costly.
  • the rectifier bridge 8 rectifies the power grid alternating voltage U ⁇ C - In the large majority of cases, a Greatz bridge is employed in the rectifier bridge 8.
  • the radio frequency interference filter 7 filters out the interferences generated in the electronics by the fast switching on and switching off of the currents and voltages.
  • the radio frequency interference filter 7 must be adequately dimensioned in order for the device to comply with the current electromagnetic compatibility standards (EN55014-1) .
  • Figure 3 shows a circuit, composed of a Greatz bridge 16 and a load 17.
  • the Greatz bridge 16 rectifies the power grid voltage u RCr so that a pulsating load voltage u L is obtained on the load 17.
  • This voltage on the load u L is followed by the current i L that flows through the load and is likewise pulsating.
  • a power grid current i AC is obtained having a shape that complies with the electromagnetic compatibility standards (EN61000-3-2) .
  • Such a circuit was employed by C. Larouci, J. P. Ferrieux, L. Gerbaud, J. Roudet, J. P. Keradec, in the paper Optimisation of a PFC Flyback Converter in Discontinuous Conduction Mode, Proceedings PCIM 2002, Nuremberg, May 2002, wherein a flyback switching converter is used in the place of the burden 17.
  • a capacitor is connected in parallel with the switching converter in order to block the radio : frequency interference caused by the switching converter.
  • the circuit of Figure 3 may be seen, with a capacitor 18 added in parallel to the load.
  • the capacitor 18 is kept small, it merely serves to block the radio frequency interference caused by the load, such as a switching converter.
  • the electric quantities vary, as indicated in the time diagrams 19.
  • the voltage on the load u L is pulsating, each half period dropping to virtually zero.
  • the rectified current i D c is the sum of the current through the load i L and the filling current of the capacitor 18.
  • the current i DC flows the greater part of the half period, so that when the current i DC is de-rectified, the shape of the current from the power grid does not differ much from the sinus, which makes it compliant with the electromagnetic compatibility standards (EN61000-3-2) .
  • the voltage on the capacitor 18, which is to say the voltage on the load u L becomes smoother, as indicated in the time diagrams 20.
  • the capacitor 18 is only filled during the peak of the power grid voltage U ⁇ C . Consequently, the current i DC flows in narrow pulses of great amplitude.
  • the current drawn from the power grid i ac by the circuit contains a lot of higher harmonic components, 'hence not complying with the electromagnetic compatibility standards (EN61000-3-2) .
  • the permanent magnet brushless motor requires a comparatively stable voltage in the intermediate direct current circuit 10 to operate.
  • the reason for this is the cutting voltage generated in the motor windings due to the rotation of the rotor.
  • the amplitude of the cutting voltage is equal to the rotating speed multiplied by a constant.
  • the voltage in the intermediate direct current circuit 10 must exceed the amplitude of the cutting voltage, so that the electric current generating the positive torque may flow into the motor 12.
  • the electronics may ensure a stable voltage in the intermediate direct current circuit 10, provided that the smoothing capacitor 13 has a sufficient capacity. Owing to the smoothing capacitor 13 being so big, in turn, a power factor corrector 9 is required in order to ensure that a conveniently shaped electric current from the power grid i AC flows into the electronics .
  • the stator 21 and the rotor 22 of the reluctance motor illustrated in Figure 5 are conveniently shaped so that the magnetic resistance to the magnetic flow, i. e. the inductance L of the phase winding 23, varies depending on the rotational shift p.
  • the inductance L varies periodically with a period 25, and in the case of the motor shown in Figure 5, the said inductance L would' have two periods .
  • the voltage drop 28, which is a consequence of the power being generated on the shaft, is small even if the rotational speed of the motor is high. That is why the voltage in the intermediate direct current circuit of the electronics of the reluctance motor drive may be pulsating, as shown in the time diagrams 19, as opposed to the voltage in the intermediate direct current circuit 10 of prior-art electronics of the permanent-magnet brushless motor drive according to Figure 2, which voltage must be stable.
  • the electronics for controlling the reluctance motor do not require a power factor corrector, provided that the voltage in the intermediate direct current circuit is pulsating.
  • the windings may be the motor windings.
  • the authors do not describe how they carried out the start of the motor or how they regulate the speed and the power of the motor, but only describe the operation of the motor at its full power.
  • the current i F may be limited by applying to the phase winding 23 a pulsating voltage u F of a frequency that is generally above the audible range, that is to say a frequency of over 20 kHz, which is generated by the circuit shown in Figure 6.
  • the said circuit is composed of a Greatz bridge 29, a capacitor 30 of small capacitance, and a half- bridge 34, comprising semiconductor switches Vl and V2 and diodes Dl and D2.
  • the phase winding 23 may be switched on softly, causing the voltages and currents to be shaped as shown in Figure 7. If the phase winding 23 is switched on in a hard manner, the voltages and currents will be shaped as shown in Figure 8.
  • the time axis in the diagrams of Figures 7 and 8 is given in the rotational shift p, for which the rotor 22 revolves at a given speed.
  • semiconductor switches Vi and V 2 are switched on at the moment ti, so that the current i F through the phase winding 23 is increasing.
  • the said current i F is flowing via the path 32 and is, at that particular moment, equal to the currents i L and i DC in Figure 6.
  • the semiconductor switch Vi is switched off, and the current i F starts decreasing.
  • the current i F is being completed via the path 33 within the half-bridge 34.
  • the currents i L and i DC are equal to 0.
  • such interruptions of the current i DC and consequently of the current from the power grid i RC produce huge radio frequency interferences.
  • Prior-art circuits and methods for controlling a reluctance motor in grid-powered drives complying with the regulations on electromagnetic compatibility contain expensive components and are consequently not suitable for being built into comparatively cheap high volume consumer products, or else they generate radio frequency disturbances at certain points of operation, consequently requiring big filters to block radio frequency interference .
  • the object of the present invention is a circuit and a corresponding method for controlling a reluctance motor in a grid-powered drive, which will be compliant with the regulations on electromagnetic compatibility and will be composed of cheaper components, allowing it to be built into comparatively inexpensive high volume consumer products .
  • the said object is achieved through a circuit and a method for controlling a reluctance motor as per the independent patent claims .
  • Figure 1 a prior-art circuit and method for controlling a universal collector motor
  • Figure 2 a prior-art circuit for controlling brushless motors
  • Figure 3 a prior-art rectifier circuit having no smoothing capacitor, and the operation thereof;
  • Figure 4 a prior-art rectifier circuit having a smoothing capacitor, and the operation thereof;
  • Figure 5 an embodiment of a prior-art three-phase reluctance motor
  • Figure 6 the directions of the currents in the half-bridge of a prior-art pulsating feed of a motor phase winding
  • Figure 7 a time diagram of the currents of a prior-art pulsating feed of a motor phase winding
  • Figure 8 a time diagram of the currents of a prior-art pulsating feed of a motor phase winding
  • Figure 9 the circuit for controlling the reluctance motor according to a first embodiment of the invention.
  • Figure 10 the circuit for controlling the reluctance motor according to a second embodiment of the invention.
  • Figure 11 the circuit for controlling the reluctance motor according to a third embodiment of the invention.
  • Figure 12 an embodiment of a power output stage for powering the reluctance motor according to the method of the invention
  • Figure 13 the time diagram of the electric currents in the output stage according to the invention.
  • Figure 14 the time diagram of the electric currents and voltages when the motor is controlled according to the first method of the invention
  • Figure 15 the time diagram of the electric currents and voltages when the motor is controlled according to the second method of the invention.
  • the electronics of the grid-powered drive with a reluctance motor comprise a capacitor 40 of a very small capacitance, so that in each half period the voltage at the said capacitor drops to 25 % of the maximum voltage reached thereat during the same half period, and also comprise a voltage-dependent circuit 41, or alternatively the electronics in the intermediate direct current circuit only comprise a voltage-dependent circuit and no capacitor 40.
  • the voltage-dependent circuit 41 the magnetic energy returning from the motor 39 is transformed into heat.
  • the grid-powered drive with a reluctance motor does not require a power factor corrector.
  • an electric current of a shape that causes fewer radiofrequency interferences flows into the power output stage 38.
  • the current flowing through the windings of the motor 39 is limited by switching on the phase currents of the motor 39 in synchronicity with the power grid alternating voltage u RC . '
  • Circuits for controlling a reluctance motor 39 with two or more phases comprise a radiofrequency interference filter 35, a rectifier bridge 36, an intermediate direct current circuit 37 having a capacitor 40 and a voltage- dependent circuit 41 or alternatively having only a voltage-dependent circuit 41, a power output stage 38, a sensor 44, a commutation logic 43, and a voltage meter 42.
  • the sensor 44 may be substituted by a sensorless algorithm.
  • the expression "voltage meter" 42 refers to an electronic circuit which yields information on the power grid voltage u AC passing through the zero point.
  • each of the phase windings of the motor 39 gets switched on and off only once, exception being made for very low speeds and the starting of the motor when the duration of one period of the inductance variation 25 is longer than the half period of the power grid voltage u AC -
  • the phase winding of the motor 39 might get switched on and off several times during a given period of the inductance variation 25, but still only once during any given half period of the power grid voltage u AC .
  • Figure 12 depicts the circuit of the power output stage 38, to which the phase winding 46, the phase winding 47 and the phase winding 48 of the reluctance motor are connected.
  • the circuit of the power output stage 38 consists of the diodes Di to D 6 and of the semiconductor switches Vi to V ⁇ r which may be bipolar transistors, MOSFETs, or IGBTs.
  • the current ⁇ flows through the phase winding 46
  • the current I 2 flows through the phase winding 47
  • the current I 3 flows through the phase winding 48.
  • the unfolding of the currents I 2 and i 3 is shown in the diagrams of Figure 13, wherein the events taking place within a single revolution are represented, the duration of such a single revolution being substantially shorter than the half period of the grid voltage u AC .
  • the procedure of commutating the current from the phase winding 46 to the phase winding 47 starts with the semiconductor switches V 3 and V 4 i . e. the phase winding 47 switching on.
  • the moment at which the phase winding 47 gets switched on varies depending on the speed of and the load on the motor 39.
  • the current i 2 is increasing and flowing via the path 52.
  • the current i L is now the sum of the currents X 1 and I 2 .
  • the phase winding 46 is switched off by first switching off only the semiconductor switch Vi, so that at the moment t 3 the current ii is being completed via the path 51 through the semiconductor switch V 2 and the diode Di of the half-bridge 34 in the power output stage 38.
  • the inductance of the phase winding 46 must still keep increasing, so that the current i ⁇ in the said phase winding 46 keeps generating torque and consequently keeps decreasing.
  • we could switch off the semiconductor switch V 2 thereby forcing the current i ⁇ to complete through the semiconductor switch V 1 and the diode D 2 .
  • the time during which the current I x is being completed within the half- bridge 34 may be longer than 5 % of the period of the inductance variation 25.
  • the current i 2 becomes bigger than the current ⁇ lr we switch off the semiconductor switch V 2 as well.
  • the current ii is flowing from the half-bridge 34 via the path 49 and is subtracted from the current i 2 flowing via the path 52.
  • the current i 2 is bigger than the current i lr the current i L is greater than zero.
  • the current l ⁇ drops down to zero, the commutation of the current from the phase winding 46 to the phase winding 47 is finished.
  • the current i L did not drop to zero, that is, it did not begin flowing backwards to the intermediate direct current circuit 37. There is accordingly no need of the capacitor 40 during operation.
  • the current i L would start flowing in the reverse direction, that is to say, the energy would begin flowing back from the magnetic field inside the motor 39 to the intermediate direct current circuit 37.
  • the said energy may be stored inside the capacitor 40, or converted into heat on the voltage- dependent element 41.
  • the aperture angle a may be enlarged without resulting in an overly big current flowing through the phase windings of the motor 39.
  • the aperture angle a is equal to IT. In that situation the power output stage 38 commutates the current in the phase windings of the motor 39 without any interruptions.
  • the duration of a single rotational shift 53 of the motor 39 is also indicated, valid in the case of the motor 39 being identical to the motor in Figure 5.
  • the regulation of the power viz. of the speed of the reluctance motor 39 during the start and the operation with the aperture angle a may be accomplished in two different ways.
  • the first way is to make the electronics switch on and off the phase windings of the motor 39 in such a way that the electric currents i lr ⁇ 2 , I 3 in the phases of the motor 39 start to flow at the instant of angle /3 in the proximity of the passage of the power grid voltage U ⁇ C through 0 and then continue flowing only during the aperture angle a, as indicated in Figure 14.
  • the second way is to make the electric currents I 1 , i 2 , 1 3 in the phases of the motor 39 flow only during the aperture angle a, and stop flowing at the instant of angle ⁇ in the proximity of the passage of the power grid voltage U ⁇ C through zero, as indicated in Figure 15.
  • This second way is analog to the method of controlling a universal collector motor 2 with a triac 3, as represented in Figure 1.
  • the duration of the aperture angle a may assume values from zero to half of the period of the power grid voltage
  • the angle ⁇ designates the amount by which the electric currents i ⁇ , I 2 , 1 3 in the phases of the motor 39 precede or follow the moment of passage of the power grid voltage U ⁇ C through zero.
  • the angle /3 is temporally offset from the passage of the power grid voltage U ⁇ C through zero by less than 20 % of the half period of the power grid voltage u A c-
  • the information on the actual value of the power grid voltage u A c viz. the moment of passage of the power grid voltage u RC through zero is forwarded to the commutation logic 43 by the voltage meter 42. Consequently, the commutation logic 43 can control the aperture angle a. in synchronicity with the power grid voltage U ⁇ C - In addition, the commutation logic 43 can take care of the commutation of the currents i ⁇ f ⁇ 2 , 1 3 in dependence of the rotational shift of the rotor of the motor 39. To operate, the commutation logic 43 also requires the information on the desired speed viz. the desired torque.
  • the current flowing through the phase windings of the motor 39 is interrupted in synchronicity with the power grid, thus controlling the aperture angle a with the additional semiconductor switch 45 in the intermediate direct current circuit 37, to which the information on the actual value of the power grid voltage u AC viz. on the moment of passage of the power grid voltage U ⁇ C through zero is forwarded.
  • the semiconductor switch 45 may be placed in the positive or in the negative branch of the intermediate direct current circuit 37.
  • the current flowing through the phase windings of the motor 39 is interrupted in synchronicity with the power grid, thus controlling the aperture angle a already in the rectifier bridge 36, which is equipped with controlled semiconductor switches.
  • the information on the actual value of the power grid voltage u AC viz. on the moment of passage of the power grid voltage u AC through zero is forwarded to the rectifier bridge 36.
  • the power output stage 38 merely directs the current to the appropriate winding of the motor 39, depending on the rotational shift of the rotor.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Electric Motors In General (AREA)

Abstract

L'invention se rapporte à un circuit et à un procédé destinés à réguler un moteur à réluctance alimenté à partir du système public d'émission d'énergie (le réseau de distribution d'énergie) et, en particulier, elle se rapporte à un procédé de fonctionnement qui permet aux circuits électroniques d'attaque de comporter moins de sous-systèmes et d'être en conséquence meilleur marché. Le circuit conforme à l'invention comprend un filtre d'interférences à haute fréquence (35), un pont redresseur (36), un voltmètre (42), un circuit intermédiaire à courant continu (37), un étage de sortie de puissance (38), un capteur (44) destiné à mesurer le décalage en rotation du rotor ou, en variante, un algorithme sans capteur, ainsi qu'une logique de commutation (43). Le circuit est constitué de telle sorte que la tension dans le circuit intermédiaire à courant continu (37) soit pulsé, ce qui rend le courant électrique (iAC) consommé depuis le réseau de distribution d'énergie conforme aux réglementations sur la compatibilité électromagnétique (EN61000-3-2). Les courants électriques (i1, i2, i3) dans les enroulements des phases du moteur (39) doivent être limités afin que l'étage de sortie de puissance (38) ne soit pas calciné. Ceci est obtenu en limitant les tensions dans les enroulements des phases du moteur (39), ce qui est réalisé en ne mettant sous tension les enroulements des phases que lorsque la tension dans le circuit intermédiaire à courant continu (37), c'est-à-dire la tension alternative du réseau de distribution d'énergie (uAC), soit suffisamment faible par rapport à l'état de fonctionnement du moteur (39).
PCT/SI2006/000003 2005-02-21 2006-02-15 Circuit et procede pour la regulation d'un moteur a reluctance Ceased WO2006098703A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
SIP-200500045 2005-02-21
SI200500045A SI21983A (sl) 2005-02-21 2005-02-21 Vezje in postopek za krmiljenje reluktancnega motorja

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Cited By (3)

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Publication number Priority date Publication date Assignee Title
EP1903667A1 (fr) * 2006-09-22 2008-03-26 Switched Reluctance Drives Limited Commande de machines électriques à partir d'une liaison CC
CN109861214A (zh) * 2019-02-28 2019-06-07 中国电力科学研究院有限公司 判断区域电网暂态功角稳定薄弱线路的方法、系统
WO2023115861A1 (fr) * 2021-12-21 2023-06-29 莱克电气股份有限公司 Procédé et appareil de commande de moteur électrique à réluctance commutée, et dispositif de cuisson et support de stockage

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JPH07312826A (ja) * 1994-05-17 1995-11-28 Shibaura Eng Works Co Ltd モータの駆動装置
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US6208113B1 (en) * 1998-09-21 2001-03-27 Ebm Werke Gmbh & Co. System for controlling the rotation of AC motors
GB2396491A (en) * 2002-12-21 2004-06-23 Dyson Ltd Power conversion apparatus

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Publication number Priority date Publication date Assignee Title
JPH07312826A (ja) * 1994-05-17 1995-11-28 Shibaura Eng Works Co Ltd モータの駆動装置
US6208113B1 (en) * 1998-09-21 2001-03-27 Ebm Werke Gmbh & Co. System for controlling the rotation of AC motors
DE29918256U1 (de) * 1999-10-18 2001-03-01 Robert Bosch Gmbh, 70469 Stuttgart Entstörvorrichtung
GB2396491A (en) * 2002-12-21 2004-06-23 Dyson Ltd Power conversion apparatus

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Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1903667A1 (fr) * 2006-09-22 2008-03-26 Switched Reluctance Drives Limited Commande de machines électriques à partir d'une liaison CC
US7737646B2 (en) 2006-09-22 2010-06-15 Switched Reluctance Drives Limited Operating electrical machines from a DC link
US7888896B2 (en) 2006-09-22 2011-02-15 Switched Reluctance Drives Limited Operating electrical machines from a DC link
EP2688194A3 (fr) * 2006-09-22 2014-05-07 Nidec SR Drives Ltd. Commande de machines électriques à partir d'une liaison CC
CN109861214A (zh) * 2019-02-28 2019-06-07 中国电力科学研究院有限公司 判断区域电网暂态功角稳定薄弱线路的方法、系统
WO2023115861A1 (fr) * 2021-12-21 2023-06-29 莱克电气股份有限公司 Procédé et appareil de commande de moteur électrique à réluctance commutée, et dispositif de cuisson et support de stockage

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