WO2008019531A1 - Générateur haute fréquence - Google Patents

Générateur haute fréquence Download PDF

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Publication number
WO2008019531A1
WO2008019531A1 PCT/CN2006/002026 CN2006002026W WO2008019531A1 WO 2008019531 A1 WO2008019531 A1 WO 2008019531A1 CN 2006002026 W CN2006002026 W CN 2006002026W WO 2008019531 A1 WO2008019531 A1 WO 2008019531A1
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WO
WIPO (PCT)
Prior art keywords
voltage
circuit
output
high frequency
converter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2006/002026
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English (en)
Chinese (zh)
Inventor
Waikei Huen
Yun Li
Lock Kee Rocky Poon
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Individual
Original Assignee
Individual
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Individual filed Critical Individual
Priority to PCT/CN2006/002026 priority Critical patent/WO2008019531A1/fr
Publication of WO2008019531A1 publication Critical patent/WO2008019531A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices
    • H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2851—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2853—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal power supply conditions
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps

Definitions

  • the present invention relates to a high frequency generator as a novel power source, and more particularly to a high frequency generator for driving an electrodeless discharge lamp and a radio. Background technique
  • the electrical energy generated by the solar cells or the electrical energy generated by the wind turbine typically needs to be stored in the battery first, and then powered by the battery to the powered device.
  • a low DC voltage such as 12V can be supplied by means of a battery or the like.
  • discharge lamps such as cold cathode fluorescent lamps
  • a low-current DC voltage directly or indirectly supplied by the solar cell is converted by a conversion circuit into a high-frequency high-voltage sine wave output voltage required for a discharge lamp (such as a cold cathode fluorescent lamp) to reduce the circuit. Loss and achieve high luminous efficiency.
  • Prior art conversion circuits typically implement voltage conversion and frequency control in the same stage, which typically includes an output transformer through which voltage is supplied to the powered device.
  • a converter for driving a discharge lamp is disclosed, for example, in U.S. Patent Application Serial No. 2004/0056607, in which an input DC voltage is first converted to a high amplitude ripple voltage by a regulator circuit and then passed through an output transformer.
  • the direct drive circuit converts the ripple voltage into an output voltage.
  • the converter includes Two-stage circuit, but the previous stage circuit generates ripple voltage, which is mainly used to control the output voltage value.
  • the voltage conversion and frequency control are still realized by the latter stage circuit.
  • the output transformer needs to withstand both high frequency and high voltage, the parameters of the output transformer itself are very high. For example, to increase the pressure resistance of a transformer, a larger transformer must be designed. Therefore, due to the use of the output transformer, the conventional conversion circuit is only suitable for outputting a low-frequency low-voltage AC voltage, and has the disadvantages of low efficiency, large loss, and large volume, resulting in great waste of energy.
  • An object of the present invention is to provide a novel high frequency generator which is highly reliable and small in size.
  • a high frequency generator comprising a DC-DC converter for converting an input DC voltage into a high voltage DC voltage, and a high frequency oscillation output device for converting a high voltage DC voltage into a high frequency output
  • the voltage is further characterized by: a protection device that detects a DC voltage input to the DC-DC converter and is coupled to the DC-DC converter, and stops the DC when the value of the input DC voltage is too low - The operation of the DC converter.
  • the protection device further detects an output current of the DC-DC converter, and stops the operation of the DC-DC converter when the value of the output current is too high. .
  • the high frequency oscillation output device uses a high voltage direct current power source as a working power source, and includes two A half-bridge oscillating circuit composed of a CMOS field effect transistor has an LC series resonant circuit connected to the half bridge, and the gates of the two FETs are respectively connected to the same polarity end of the first winding of the transformer (also referred to as the same name end).
  • the third winding of the transformer is connected in the LC series resonant circuit, and once the half-bridge oscillating circuit starts to work under the driving of the oscillating circuit, The half-bridge oscillating circuit maintains its own oscillation.
  • the protection device does not directly detect the high frequency output voltage signal, but detects the DC input voltage and the output current of the DC-DC converter to achieve undervoltage or overcurrent protection. Since the protection device detects the DC signal, it does not cause a problem that the high-frequency signal causes the protection circuit to malfunction, thereby ensuring the operational reliability of the generator.
  • the high-frequency output signal is outputted by the series LC resonant network, and the switching frequency of the two FETs is controlled by the LC series resonant frequency, so that the high-frequency characteristics are good, the high-voltage loss is small, and the nonlinearity is low. Small size, light weight, high reliability, and stable output frequency. Also, since the series LC resonance network is employed, the high frequency oscillation output device can be easily designed to operate at a high frequency of, for example, 2.65 MHz.
  • control transformer Since only the control transformer is used in the high-frequency oscillation output device, the control transformer only needs to withstand a very low voltage during operation, and therefore, it is required to withstand high voltage and operate at high frequency as compared with the prior art. In the case of an output transformer, the volume of the transformer can be greatly reduced, and as a result, a small-sized high-frequency generator can be obtained.
  • Figure 1 is a circuit block diagram of a high frequency generator in accordance with the present invention.
  • FIG. 2 is a circuit diagram of the electromagnetic compatibility filter circuit of Figure 1;
  • Figure 3 is a circuit diagram of the oscillation drive circuit of Figure 1; 4 is a circuit diagram of the boost converter and rectifier circuit of FIG. 1; FIG. 5 is a circuit diagram of the power supply overload and undervoltage protection sampling circuit of FIG. 1; FIG. 6 is a circuit diagram of the high frequency oscillation output circuit of FIG.
  • Figure 7 is a waveform diagram at each node in Figure 2-6. detailed description
  • FIG. 1 shows a circuit block diagram of a high frequency generator according to the present invention, comprising five circuit modules, namely: an electromagnetic compatibility filter circuit 1, an oscillation drive circuit 3, a boost converter and a rectifier circuit 2, a power supply overload and an undervoltage protection.
  • a DC voltage of, for example, 12 V is input to the input terminal of the high frequency generator, and filtered by the electromagnetic compatibility filter circuit 1, the DC voltage is input to the boost converter and rectifier circuit 2.
  • the step-up conversion and rectification circuit 2 is driven by the oscillation drive circuit 3 so that the DC voltage is first boost-converted into a high-voltage sine wave voltage, and then rectified to obtain, for example, a DC high voltage of about 400V.
  • the power overload and undervoltage protection circuit 4 detects the input voltage and the output current of the high frequency generator, and stops controlling the operation of the oscillation driving circuit 3 when the input voltage is too low or the output current is too large, so as to protect the high frequency occurrence of the present invention. Device.
  • the DC high voltage obtained by the rectification is input to the high frequency oscillation output circuit 5, and the high frequency oscillation output circuit operates at a frequency of 2.65 MHz, thereby converting the input DC high voltage into a high frequency sine wave output high voltage.
  • FIG. 2 shows a circuit diagram of the electromagnetic compatibility filter circuit 1.
  • the electromagnetic compatibility filter circuit 1 includes an insulative fuse connected in series on the input line for preventing overcurrent, and further includes capacitors C1, C2, C3, C4 connected in parallel on the input line and a choke line mounted on the input line.
  • Ll select the parameters of each component to filter out clutter and interference signals in the power grid, and suppress the operating frequency of the high-frequency oscillation output circuit, ie 2.65MHz
  • the electromagnetic wave and its higher harmonics thereby eliminating the electromagnetic radiation interference of the circuit of the present invention to the outside, and further comprising a diode D1 connected in parallel to the input line for preventing polarity reversal at the input end due to misoperation Possible damage to the circuit of the present invention.
  • Fig. 3 shows a circuit diagram of the oscillation drive circuit 3.
  • the oscillating drive circuit 3 is a conventional two-way output pulse width modulation (PWM) control circuit.
  • PWM pulse width modulation
  • Fig. 4 an integrated circuit UC3525 from Texas Instruments is used as an example.
  • the integrated circuit U2 includes an externally controllable internal oscillation circuit, the pin 5 is an external capacitor terminal of the internal oscillator, and the pin 6 is an external resistor terminal of the internal oscillator.
  • the pulse width can be adjusted by adjusting capacitor C17 connected in series between pin 5 and ground.
  • the oscillation frequency can be adjusted by adjusting resistor R27 connected in series between pin 6 and ground.
  • An integrated internal voltage regulator is also included in integrated circuit U2, and the resulting reference voltage is output from pin 16.
  • Resistors R29 and R24 form a bias circuit that is connected in series between pin 16 and ground to provide this reference voltage to pin 2.
  • An integrated error amplifier is also included in integrated circuit U2, and pins 1 and 2 are the two inputs of the internal error amplifier.
  • Resistors R23 and R24 form a bias circuit connected in series between the approximately 400V DC voltage output of boost converter and rectifier circuit 2 and ground.
  • Pin 1 is connected to the node between resistors R23 and R24 for detection.
  • External line voltage As described above, the pin 2 receives the reference voltage.
  • the internal error amplifier outputs a signal that activates the PWM latching circuit inside the integrated circuit U2 to stop the output.
  • Pin 8 of integrated circuit U2 is the soft start terminal, and capacitor C16 is connected in series between pin 8 and ground as a soft start capacitor.
  • capacitor C16 begins to discharge. After a certain period of time, the pulse width modulation control circuit is restarted.
  • the soft start time can be changed by adjusting the capacitance of capacitor C16.
  • the pin 10 of the integrated circuit U2 is a closed end and is connected to the following description.
  • the load and undervoltage protection circuit 4 will turn off the pulse width modulation control circuit when the input voltage of the high frequency oscillation generator is too low or the output current is too high.
  • Pins 11 and 14 of integrated circuit U2 are the respective outputs of the two outputs.
  • the waveform signals generated at the nodes h, i are shown in Fig. 7, in which the waveforms of the two output square wave signals of the integrated circuit U2 are the same, and the phases are 180 degrees out of phase.
  • the square wave signals are applied to the control terminals of the switching transistors Q1 and Q2, respectively, such that the switching transistors are alternately turned on or off.
  • Fig. 4 shows a circuit diagram of the boost converter and rectifier circuit 2.
  • the boost converter and rectifier circuit 2 includes a transformer L2 having a center tap on the primary side.
  • the center tap of the primary side of the transformer L2 is connected to the high potential output of the electromagnetic filter circuit 1, the two inputs of the primary side are connected to the current terminals of the switching transistors Q1 and Q2, respectively, and the two outputs of the secondary side are Connect to a full bridge rectifier.
  • the control terminals of the switching transistors Q1 and Q2 are connected to the oscillation drive circuit 3 already explained above to receive the drive control signal.
  • the switching transistors Q1 and Q2 are alternately turned on, so that current flows from the center tap, and then alternately flows out from the two input terminals on the primary side through the corresponding switches.
  • the transistor is grounded to thereby generate an AC output voltage having a frequency of, for example, 50 Hz and a waveform symmetrical with respect to the ground potential due to coupling on the secondary side, and a signal waveform generated at the node b is shown in FIG.
  • the output voltage reaches an amplitude of, for example, about 400 V due to the voltage conversion of the transformer.
  • the AC voltage from the secondary output of transformer L2 is supplied to the full bridge rectifier circuit.
  • a filter network consisting of capacitor C15 and inductor L3 and resistors R10, R11, and R12 is provided.
  • the AC voltage is processed by the full bridge rectifier circuit rectification and filtering network to generate a converted DC high voltage.
  • the oscillation drive circuit 3, the boost converter and the rectifier circuit 2 constitute a DC-DC converter.
  • FIG. 5 shows a circuit diagram of the power supply overload and undervoltage protection sampling circuit 4.
  • Can This circuit is constructed using a conventional two-way operational amplifier, and Texas Instruments' dual operational amplifier integrated circuit LM358 (hereinafter referred to as ⁇ ) is selected as an example.
  • the pins 3, 2, and 1 of the two operational amplifiers U1 are the non-inverting input, the inverting input, and the output of one of the operational amplifiers, respectively, and the pins 5, 6, and 7 are the non-inverting inputs of the other operational amplifier, Inverting input and output.
  • Pin 8 is the power supply and is connected to the 12V supply voltage.
  • a sampling resistor 5 is connected in series to the negative output of the full-bridge rectifier circuit in the boost converter and rectifier circuit 2 of Fig. 3 for detecting current.
  • the in-phase input pin 5 and the inverting input pin 6 of the two operational amplifiers IJ1 are coupled across the sampling resistor R5.
  • the diode D2 is turned on, and the high potential signal is supplied to the integrated circuit U1.
  • the pin 10 causes the integrated circuit U1 to stop the operation of the pulse width modulation control circuit, thereby implementing overload protection.
  • Resistors R19, R18 and variable resistor R17 are connected in series between the input 12V DC voltage and ground, and a voltage stabilizing diode D5 is connected between the node of resistors R19 and R18 and ground.
  • the resistors R19, R18, the variable resistor R17 and the Zener diode D5 form a conventional voltage stabilizing circuit to provide a stable voltage for the non-inverting input terminal 3 as a reference voltage.
  • the inverting input pin 2 is connected to the input of the high frequency generator via a resistor R21 to detect the input 12V DC voltage.
  • Fig. 6 shows a circuit diagram of the high frequency oscillation output circuit 5.
  • Transistors Q5 and Q6 form a start-up circuit.
  • the charging of the capacitor C13 is started, and the base potential of the transistor Q5 rises to be turned on.
  • the current flows through the emitter and collector of the transistor Q5, charges the capacitor C14, and the potential of the control terminal of the transistor Q6 rises to be turned on, thereby turning on the diode D6.
  • the control transformer L5 includes windings N1, ⁇ 2 and ⁇ 3 which are formed on the same core so as to be coupled to each other.
  • the winding ⁇ 2 is connected to the control terminal of the switching transistor Q3, and the winding ⁇ 3 is connected to the control terminal of the switching transistor Q4.
  • the same polarity end of each winding is shown by black dots in Fig. 6.
  • the main part of the high-frequency oscillation output circuit 5 is a half-bridge oscillation circuit including switching transistors Q3 and Q4, inductors L4 and L5, and a capacitor C10.
  • Inductor L4 and capacitor C10 form a series LC resonant network connected between the midpoint of the half bridge (ie, the node between switching transistors Q3 and Q4) and the same polarity end of winding N1 of transformer L5, the non-homopolar of winding N1 The ground is grounded.
  • the half-bridge oscillating circuit starts operating under the driving of the oscillating circuit.
  • the switching transistor Q3 When the switching transistor Q3 is turned on, a 400 V DC voltage is applied to the point g through the two current terminals of the switching transistor Q3, and the capacitor C10 is charged via the inductor L4.
  • the current iL reaches a maximum value.
  • the left side and the right side of the inductor L4 are positive potential and negative potential, respectively, and the left side and the right side of the capacitor C10 are also positive potential and negative potential, respectively, and the winding N1 of the transformer L5 reaches the highest polarity end. Potential. Due to the coupling relationship, the winding N2 of the transformer L5 and the same polarity end of the winding N3 (the black point in Fig. 6) also reach the highest potential, so that the e point potential is low and the f point potential is high, so that the switching transistor Q3 is turned off and the switching transistor is turned off. Q4 is turned on.
  • the switching transistor Q3 When the switching transistor Q3 is turned off and Q4 is turned on, the g point passes through the two current terminals of the switching transistor Q4 to the ground, so that the potential of the point is lowered.
  • the current in the inductor L4 cannot be abruptly changed, so that an induced electromotive force of opposite polarity is generated in the inductor L4, that is, the left side and the right side of the inductor L4 are a negative potential and a positive potential, respectively.
  • the voltage across capacitor C10 cannot be abrupt, so that current iL is reversed, flowing through the two current terminals of switching transistor Q4 to ground, thereby discharging the electrical energy stored by inductor L4 and capacitor C10.
  • the potential is lowered at the respective polarity ends of the windings N1, N2 and the winding N3 of the transformer L5, causing the potential at the point e to be high and the potential at the point f to be low, so that the switching transistor Q3 is turned on and the switching transistor Q4 is turned off, so that the half The bridge oscillating circuit maintains its own oscillation.
  • a square wave signal having a phase difference of 180 degrees is generated at points e and f, respectively, acting on the control terminal of Q4 of the switching transistor Q3, so that the switching transistors Q3 and Q4 are alternately turned on and off, and output at the point g.
  • the signal waveform is shown in Figure 7.
  • Diodes D8 and D9 are connected in series between the control terminal and the current terminal of the switching transistor Q3 to protect the switching transistor Q3 from breakdown due to the back electromotive force of the winding N2.
  • Resistor R15 and capacitor C11 are connected in parallel between the control terminal and the current terminal of the switching transistor Q3, and the resonance frequency is set at about 2.65 MHz to ensure an accurate output frequency.
  • diodes D10 and D11 are connected in series between the control terminal and the current terminal of switching transistor Q4 to protect switching transistor Q4 from breakdown due to the back EMF of winding N3.
  • the resistor R16 and the capacitor C12 are connected in parallel between the control terminal and the current terminal of the switching transistor Q3, and the resonance frequency is set at about 2.65 MHz to ensure an accurate output frequency.
  • the resistor R13, the capacitor C8 and the diode D7 constitute a protection circuit.
  • the voltage across capacitor C8 cannot be abrupt, thereby protecting switching transistor Q3.
  • the resistor R13 and the diode D7 are divided to The switching transistor Q3 is protected.
  • the output signal is taken from the node between the inductor L4 and the capacitor C10 in the series LC resonant network.
  • the output signal is corrected by the parallel capacitor C9 and resistor R14 to smooth the rising and falling edges of the output signal. See Figure 7. An approximate sine wave is obtained at point d.
  • the output signal is an approximately sinusoidal voltage having a frequency of 2.65 MHz and an amplitude of approximately 400V.
  • the invention can be used in conjunction with a solar cell for generating a high frequency and high voltage output voltage to drive electrical equipment, such as an electrodeless discharge lamp.
  • electrical equipment such as an electrodeless discharge lamp.
  • the use of the high frequency generator of the present invention for driving a discharge lamp achieves optimum luminous efficiency.

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  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente invention concerne un générateur haute fréquence, qui comprend une unité de conversion continu-continu destinée à convertir une tension continue d'entrée en un courant continu haute tension, et une unité de sortie à oscillation haute fréquence destinée à convertir la tension continue convertie en une tension de sortie haute fréquence. Le générateur haute fréquence selon l'invention comprend également un protecteur, qui détecte la tension continue qui est entrée dans l'unité de conversion continu-continu. Le protecteur se couple à l'unité de conversion continu-continu et interrompt le fonctionnement de cette dernière lorsque la tension continue d'entrée est trop basse.
PCT/CN2006/002026 2006-08-10 2006-08-10 Générateur haute fréquence Ceased WO2008019531A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
PCT/CN2006/002026 WO2008019531A1 (fr) 2006-08-10 2006-08-10 Générateur haute fréquence

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2006/002026 WO2008019531A1 (fr) 2006-08-10 2006-08-10 Générateur haute fréquence

Publications (1)

Publication Number Publication Date
WO2008019531A1 true WO2008019531A1 (fr) 2008-02-21

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PCT/CN2006/002026 Ceased WO2008019531A1 (fr) 2006-08-10 2006-08-10 Générateur haute fréquence

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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113759436A (zh) * 2021-08-30 2021-12-07 航宇救生装备有限公司 一种带自加热功能的入水检测传感器
CN113824435A (zh) * 2021-08-19 2021-12-21 松翰科技(深圳)有限公司 一种雾化器追频软件

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1098242A (zh) * 1993-04-23 1995-02-01 菲利浦电子有限公司 电路装置
JPH11283770A (ja) * 1998-03-31 1999-10-15 Toshiba Lighting & Technology Corp 多灯用放電ランプ点灯装置および照明装置
CN2590267Y (zh) * 2002-12-02 2003-12-03 南昌智圣电力电子设备厂 直流－直流变换器

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1098242A (zh) * 1993-04-23 1995-02-01 菲利浦电子有限公司 电路装置
JPH11283770A (ja) * 1998-03-31 1999-10-15 Toshiba Lighting & Technology Corp 多灯用放電ランプ点灯装置および照明装置
CN2590267Y (zh) * 2002-12-02 2003-12-03 南昌智圣电力电子设备厂 直流－直流变换器

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113824435A (zh) * 2021-08-19 2021-12-21 松翰科技(深圳)有限公司 一种雾化器追频软件
CN113824435B (zh) * 2021-08-19 2024-04-19 松翰科技(深圳)有限公司 一种雾化器追频电路
CN113759436A (zh) * 2021-08-30 2021-12-07 航宇救生装备有限公司 一种带自加热功能的入水检测传感器
CN113759436B (zh) * 2021-08-30 2023-10-24 航宇救生装备有限公司 一种带自加热功能的入水检测传感器

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