WO2020104597A1 - Convertisseur de puissance cc-cc isolé à rapport de tours réglable - Google Patents

Convertisseur de puissance cc-cc isolé à rapport de tours réglable

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Publication number
WO2020104597A1
WO2020104597A1 PCT/EP2019/082108 EP2019082108W WO2020104597A1 WO 2020104597 A1 WO2020104597 A1 WO 2020104597A1 EP 2019082108 W EP2019082108 W EP 2019082108W WO 2020104597 A1 WO2020104597 A1 WO 2020104597A1
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WO
WIPO (PCT)
Prior art keywords
power converter
isolated
controllable
switch
stages
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/EP2019/082108
Other languages
English (en)
Inventor
Bin Zhao
Ziwei OUYANG
Michael Andreas Esbern ANDERSEN
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Danmarks Tekniske Universitet
Original Assignee
Danmarks Tekniske Universitet
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Danmarks Tekniske Universitet filed Critical Danmarks Tekniske Universitet
Publication of WO2020104597A1 publication Critical patent/WO2020104597A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33538—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H02M1/342—Active non-dissipative snubbers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • a first aspect of the invention relates to an isolated DC-DC power converter which comprises at least one transformer which comprises a primary side winding and a secondary side winding wound on a common magnetic core.
  • the isolated DC-DC power converter comprising a plurality of stages, each stage comprising a controllable switch and a winding inductor.
  • the winding inductors of each two adjacent stages are connected via a controllable coupling switch so as to serially connect or disconnect these winding inductors to form the primary side winding with an adjustable number of turns.
  • the isolated DC-DC power converter comprises a shared active clamp circuit for the controllable switches.
  • DC-DC power converters implemented for example as switched mode power supplies (SMPS).
  • SMPS switched mode power supplies
  • Advantageous DC-DC power converters are of a compact design with a high power density, use the electric input power in a highly efficient manner for generating the output power with small power losses in the conversion process, and are furthermore flexible with respect to their DC input voltage range and load current characteristics.
  • DC-DC power converters implemented in forward topology or flyback topology are well-known and have the further advantage of providing electric isolation between a primary side and a secondary side of the converter circuit via a transformer.
  • the transformer of the forward converter as well as of the flyback converter also has disadvantageous effects.
  • a turns ratio between primary and secondary windings of the transformer is generally fixed. In case of a wide DC input voltage range, the fixed turns ratio of the transformer results in a large duty cycle variation of a pulse width modulation (PWM) control signal in order to maintain a target output voltage level at an output of the DC-DC power converter.
  • PWM pulse width modulation
  • a large input voltage range is a typical use scenario for a DC-DC power converter which has to operate with rectified mains voltages ranging from below 1 10 V to above 230 V.
  • the large duty cycle variation is disadvantageous as a high time resolution of a PWM control signal for controlling a switch of the DC-DC converter is necessary in order to cope with the large input voltage range.
  • a very small duty cycle such as 0.02 or a high duty cycle, for example 0.98, result in an undesired decrease in conversion efficiency because it induces large peak currents through the DC-DC power converter.
  • the large peak currents lead to increased power loss and current stress in active and/or passive circuit components, such as semiconductor switches, of the DC-DC power converter.
  • Patent application CN 10 1 171797 proposes an isolated power converter with two alternative turns ratios of an isolation transformer being available by selecting different number of windings of a primary winding of the isolation transformer and thereby adjusting the turns ratio of the isolation transformer in order to improve efficiency of the isolation transformer.
  • the isolated power converter may operate over a wide input voltage range and for varying DC output voltages with an appropriate PWM duty cycle and a favourable high efficiency.
  • the proposed isolated power converter includes a demagnetizing circuit using a separate demagnetizing winding N a to discharge magnetic energy stored in the primary side winding of the isolation transformer.
  • Leakage energy which stored in a leakage inductance of the isolation transformer of a DC-DC power converter is generally dissipated in the active main or modulating switch during each off period of the switching cycle of the active main switch.
  • the use of a shared active clamp circuit on the primary side circuit of the isolated DC-DC power converter allows recycling a large portion of this leakage energy, as well as providing soft switching, or so-called ZVS or and ZCS operation, of the active main controllable switches.
  • the present isolated DC-DC power converter allows ZVS operation of the active main switches for both low and high transformer turns ratio cases. Thereby, reducing switching losses and improving energy efficiency and power density of the converter in a manner that is particularly well- suited for high frequency operation of the applicant’s isolated DC-DC power converter.
  • the switching frequency of the applicant’s isolated DC-DC power converter may for example be higher than 1 MHz such as higher than 3 MHz or even higher than 10 MHz.
  • the present isolated DC-DC power converters provides improved power efficiency under a large DC input voltage range with high energy efficiency and a relatively low component count even when using a relatively large number of individual winding segments or winding Inductors, e.g. more than 3 or 4 separate winding inductors, on the primary side winding of the isolation transformer.
  • the isolated DC-DC power converter according to independent claim 1 solves the technical problem in a first aspect of the invention.
  • the dependent claims define further advantageous embodiments of the .
  • a DC-DC power converter comprises an isolation transformer with an adjustable turns ratio.
  • the adjustability of the turns ratio is achieved by adjusting or selecting the number of individual stages of the primary side circuit of the DD-DC power converter.
  • Each of the stages of the power converter comprises a controllable switch and an inductor or winding segment.
  • the converter comprises a further controllable coupling switch arranged in-between each pair of adjacent stages.
  • the DC-DC power converter further comprises a shared active clamped circuit for the controllable switches of the plurality of stages.
  • the isolated DC-DC power converter with the shared active clamp circuit and the adjustable turns ratio resulting from the further coupling switches interposed between the adjacent stages achieve improved soft switching characteristics and an advantageous recycling of leakage energy of the transformer over the switching cycle of the converter.
  • the coupling switches it is possible to electrically disconnect those stages which are unrequired to establish a desired or target turns ratio of the transformer. Due to providing a shared active clamp circuit for all switches of the plurality of stages, the beneficial soft switching characteristics are achieved at only a comparatively small number of additional components, required space and costs for the shared active clamp circuit.
  • the driving circuit for the active clamp circuit typically is high side type driver which is particular costly to implement.
  • a single additional third switch of the shared active clamp circuit increases the driving loss only disproportionally although the electric characteristics of the soft switching, particularly the recycling of leakage energy of the transformer and therefore driving losses are improved.
  • the reduced driving loss is in particular advantageous for low power, high frequency applications.
  • the shared active clamp circuit will improve the electric characteristics without any major decrease of the power density of the DC-DC power converter as only space for one single shared active clamp circuit is required although the overall switching behaviour of the DC-DC power converter is improved.
  • the DC-DC power converter according to a preferred embodiment comprises one single shared active clamp, or clamped, circuit for all the controllable switches of the plurality of stages.
  • a single active clamp circuit for all switches optimizes the advantageous characteristics of the advantageous DC-DC power converter.
  • the DC-DC power converter comprises a control circuit configured to control the adjustable (variable) turns ratio of the at least one isolation transformer with respective control signals for the switches of the stages and respective control signals for coupling switches interposed between the stages.
  • these signals are low side drive signals.
  • the shared active clamp circuit comprises a separate controllable switch such as a MOSFET, IGBT switch, GaNFET switch etc. driven by a third control signal.
  • the control circuit is configured to drive or control the separate controllable switch of the active clamp circuit with a high side drive signal.
  • the controllable coupling switches of the isolated DC-DC power converter are controlled such that according to a desired turns ratio, individual stages are successively connected or disconnected, by closing or opening the respective coupling switch starting from a first stage which typically is permanently connected to an input side of the isolated DC-DC power converter until the desired turns ratio is achieved.
  • respective winding inductors of the plurality of stages can be combined so as to form a single inductor, coil or primary side winding of the isolation transformer.
  • controllable switches of the stages and the controllable coupling switches are MOSFET or GaNFET switches.
  • FET Field effect transistors
  • the isolated DC-DC power converter may for example comprise a flyback converter or forward converter.
  • FIG. 1 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a forward topology in a hard switching configuration to illustrate the background of the present invention
  • FIG. 2 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a flyback topology in a hard switching configuration to illustrate the background of the present invention
  • FIG. 3 depicts switching states and a time versus voltage chart of the flyback converter of FIG. 2 with a low transformer turns ratio
  • FIG. 4 depicts switching states and a time versus voltage chart of the flyback converter of FIG. 2 with a high transformer turns ratio
  • FIG. 5 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a flyback topology comprising a shared active clamp circuit in accordance with a first exemplary embodiment of the invention
  • FIG. 6 shows a time chart of the isolated DC-DC power converter in a
  • FIG. 7 shows switching states corresponding to the time chart of FIG. 6 of the isolated DC-DC power converter in a flyback topology with the shared active clamp circuit of FIG. 5 with a low transformer turns ratio
  • FIG. 8 shows a time chart of the isolated DC-DC power converter in a
  • FIG. 9 shows switching states corresponding to the time chart of FIG. 8 of the isolated DC-DC power converter in a flyback topology with the shared active clamp circuit of FIG. 5 with a high transformer turns ratio
  • FIG. 10 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a flyback topology with N stages with a shared active clamp circuit in accordance with a second exemplary embodiment of the invention
  • Fig. 1 1 A provides simulation results for an isolated DC-DC power converter in a flyback topology according to FIG. 5 with switch Si acting as a main switch; and Fig. 1 1 B provides simulation results for an isolated DC-DC power converter in a flyback topology according to FIG. 5 with switch S 2 acting as the main switch.
  • An example of a forward DC-DC power converter comprises an isolation transformer with a fixed turns ratio of the isolation transformer.
  • a DC input voltage V which is inputted or applied to the isolated DC-DC power converter can vary over a wide voltage range a large change in a pulse width modulation (PWM) duty cycle of a control signal controlling a main switch arranged at a primary side of the isolation transformer will occur.
  • PWM pulse width modulation
  • the DC-DC power converter may be adapted to
  • FIG. 1 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a forward topology in a hard switching configuration.
  • the turns ratio of the isolation transformer of the DC-DC power converter in FIG. 1 can be adjusted (varied) by appropriately controlling the controllable switches Si , S 2 and S ai - Controlling of the switches Si , S 2 and S ai can be performed according to the available DC input voltage V, and/or a desired DC output voltage V 0 .
  • the isolated DC-DC power converter can therefore operate always with an appropriate PWM duty cycle, i.e. avoiding extreme duty cycle ranges like below 0.05 and above 0.95.
  • the illustrated embodiment of a DC-DC power converter comprises a first stage and a second stage.
  • Each of these stages comprises a winding inductor or winding segment P1 and P2 of the primary side winding of the isolation transformer, and a switch Si and S 2 respectively.
  • the stages can be electrically connected to each other by a further, or coupling, switch S a1 . Closing this coupling switch S a1 leads to electrically connecting winding inductor P1 of the first stage and winding inductor P2 of the second stage. Thereby, the winding inductors P1 and P2 are serially connected to form the primary side winding (coil).
  • Further stages may of course be included in the isolated DC-DC power converter as needed, wherein each of these additional stages is connected to the previously already connected stages via a further coupling switch in order to achieve a desired turns ratio of the isolation transformer.
  • the number of windings (turns) of the primary side winding is adjusted or adapted by controlling the coupling switches S ai , interposed between successive stages, to be in their open or closed states, i.e. either ON/conducting or OFF/non-conducting.
  • FIG. 2 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a flyback topology.
  • DC-DC power converters in forward topology are generally well known in the art.
  • FIG. 2 When comparing the forward DC-DC power converter in FIG.
  • both converter topologies differ merely with respect to the electric circuitry on the secondary side of the isolation transformer.
  • the electric circuitry on the primary side of the isolation transformer of the DC-DC power converter in forward topology corresponds to the electric circuitry on the primary side of the isolation transformer of the DC-DC power converter in flyback topology.
  • the isolation transformer again comprises a primary winding formed by a first winding inductor or inductance P1 of the isolation transformer and a second winding inductor or inductance P2 of the isolation transformer, wherein the primary winding has a number of windings either according to the number of windings of the first winding inductor P1 only, or the number of windings of the first winding inductor P1 plus the number of windings of the second winding inductor P2 depending of the state of the controllable coupling switch S Ai -
  • the isolation transformer further comprises a secondary winding S on its secondary side.
  • the winding inductors P1 , P2 and the secondary winding S are preferably wound around a common magnetic core of the isolation transformer.
  • the two winding inductors P1 , P2 and the secondary winding S are inversely wound on the magnetic core to implement the reverse electrical coupling of a typical flyback converter configuration.
  • each of the first winding inductor P1 and the second winding inductor P2 may comprise for example between 10 and 15 windings on the common magnetic core and the secondary winding S may comprise 2 windings on the common magnetic core.
  • the controllable switches S 1 ; S 2 , S a1 of the primary side circuit of the converter are arranged on the primary side of the isolation transformer and each of the
  • controllable switches S 1 ; S 2 , S a1 is preferably a semiconductor switch.
  • the controllable switches S 1 ; S 2 , S a1 can be semiconductor devices in MOSFET or GaN- FET technology. Due to a high mobility of charge carriers, GaN-FETs are
  • Ci is an input capacitor connected across the input terminals of the converter for receipt of the DC input voltage V, on the primary side of the isolated DC-DC power converter.
  • D is a diode rectifier circuit element on the secondary side of the isolation
  • the diode D can be replaced by an active switch such as a MOSFET or GaNFET for a synchronous active type of rectifier in a specific embodiment of the DC-DC power converter.
  • C o is an output capacitor arranged on the secondary side of the isolation transformer of the DC-DC power converter in order to suppress ripple voltages and smoothen the DC output voltage V 0 provided between output terminals of the DC-DC power converter.
  • a schematically illustrated load circuit R n is coupled to the DC output voltage V 0 of the DC-DC power converter.
  • DC-DC power converter may comprise three, four or even more, in general terms N serially connectable individual stages with respective winding inductors P1 , P2, P3, ..., PN of the primary side winding of the isolation transformer and corresponding semiconductor switches Si , S ai , S 2 , ..., S a(N -i ) , SN-
  • N serially connectable individual stages with respective winding inductors P1 , P2, P3, ..., PN of the primary side winding of the isolation transformer and corresponding semiconductor switches Si , S ai , S 2 , ..., S a(N -i ) , SN-
  • These additional input stages up to input stage N are arranged in series with each other beginning with the first stage being permanently connected with the input side of the DC-DC power converter followed by the second stage shown on the primary side of the isolation transformer in FIGS. 1 and 2.
  • FIG. 3 depicts switching states and a time chart of control signals used for controlling the open/closed state of the controllable switches of the flyback converter of FIG. 2 operating with a low transformer turns ratio n being selected.
  • the exemplary embodiment is a flyback DC-DC power converter with a first stage and a second stage.
  • the flyback DC-DC converter operates in a continuous-conduction mode (CCM).
  • CCM continuous-conduction mode
  • a low transformer turns ratio n such less than 8 or 5.5, may apply in a phone adaptor application when the DC input voltage V, is relatively low, for example.
  • controllable switch Si of the first stage works as a main modulating switch for example as a PWM switch.
  • the further controllable switch S a1 and the switch S 2 of the second stage are in a non-conducting state (off state) during the entire switching period of the main switch, thus, all the time.
  • the first stage and the windings of the first winding inductor P1 of the isolation transformer are active when the switch Si of the first stage is alternately switched between On and Off states.
  • the controllable switch Si is in a conducting state.
  • the diode D on the secondary side of the isolation transformer is reverse biased.
  • the input voltage V crosses an isolation barrier implemented by the isolation transformer from the first inductor P1 to the secondary winding S.
  • the switch Si of the first stage is in non-conducting state (off-state).
  • the diode D on the secondary side of the isolation transformer is forward biased, while the controllable switch Si is non conducting.
  • a voltage transfer function of the DC-DC power converter can be derived by evaluating the voltage balance over the inductive component
  • the voltage transfer function is a
  • FIG. 4 depicts switching states of the flyback converter of FIG. 2 with a high transformer turns ratio n, in a time chart.
  • the exemplary embodiment is a flyback DC-DC power converter with a first stage and a second stage.
  • the flyback DC-DC converter operates in a continuous-conduction-mode (CCM).
  • a high transformer turns ratio n may apply in a phone adaptor application when the DC input voltage V, is high.
  • the first stage 1 and the second stage 2 on the primary side circuit of the converter are connected in series which specifically means that the winding inductors P1 and P2 of the first stage and the second stage, respectively, are connected in series.
  • the controllable coupling switch S ai is switched to its conducting state by the controller over the entire switching period T, thus, all the time.
  • the controllable switch S 2 of the second stage now acts as a main PWM switch and the controllable switch Si of the first stage is switched to a non-conducting state by the controller during the entire switching period of the main switch S 2 , thus, all the time.
  • both the first stage 1 and the second stage 2 are active their winding inductors P1 and P2 commonly form the primary side winding of the isolation transformer.
  • a power transfer from the primary side of the isolation transformer to the secondary side of the isolation transformer is achieved via first and second winding inductors P1 , P2, which are now connected in series to the secondary winding S, thereby establishing a turns ratio different from the one of FIG. 2, where the turns ratio is defined only by the number of windings of the first winding inductor P1 and the number of turns of the inductor on the secondary side.
  • first inductor P1 and second inductorP2 comprise both n turns and the secondary winding is assumed to include one turn. Then, only half of the input voltage V, crosses the isolation barrier implemented by the isolation transformer from the first inductor P1 and the second inductor P2 on the one hand to the secondary winding S on the other hand.
  • the main switch S 2 is in non-conducting state.
  • a voltage transfer function of the DC-DC power converter can be derived by evaluating the voltage balance over the inductive component
  • the voltage transfer function is a
  • Fig. 5 is a simplified electrical circuit diagram of an isolated DC-DC power converter in a flyback topology with a shared active clamp circuit 2 in accordance with a first exemplary embodiment of the of the isolated DC-DC power converter.
  • the first and second stages of the DC-DC power converter depicted in FIGS. 3 and 4 show hard switching characteristics, in particular due to the leakage inductance of the winding inductors P1 and P2 in the isolation transformer.
  • the first and second stage on the primary side circuit of the isolated DC-DC power converter commonly comprise one shared active clamp circuit 2.
  • the shared active clamp circuit 2 is arranged in series with the first stage with its first winding inductor P1 and the second stage with its second winding inductor P2 each as shown in FIG. 5.
  • the shared active clamp circuit 2 of the first embodiment comprises a clamp capacitor C c in series with a controllable clamp switch S c
  • This controllable switch S c of the shared active clamp circuit 2 is shown with its parasitic switch capacitor and parasitic pn diode.
  • FIG. 6 shows a time domain plot or chart of the isolated DC-DC power converter in a flyback topology with the shared active clamp circuit 2 of FIG. 5 in an application with a low transformer turns ratio.
  • a low transformer turns ratio n may apply in a phone adaptor application when the DC input voltage V, is low.
  • FIG. 7 shows the switching states corresponding to the time chart of FIG. 6 of the isolated DC-DC power converter in a flyback topology with the shared active clamp circuit of FIG. 5 with a low transformer turns ratio.
  • the first stage only works together with the shared active clamp circuit 2. Therefore, the controllable switch Si of the first stage functions as the main PWM switch.
  • the controllable switch S 2 is constantly in a non conducting state (off state).
  • the controllable coupling switch S ai connecting the first inductor P1 and the second inductor P2, and controllable switch S c of the shared active clamp circuit have a common control signal scheme to function as the active clamp switches.
  • the low turns ratio may be 5.5 and for example selected by the controller, e.g. programmable microcontroller or microprocessor, of the isolated DC- DC power converter in response to the DC input voltage V, lies between 60 V and 150 V, while the high turns ratio may be larger than 10 or 1 1 and selected by the microcontroller in response to the DC input voltage V, exceeds 150 V.
  • the controllable switch Si is in a conducting state.
  • the other controllable switches S a1 , S 2 , and S c are all switched to their respective non-conducting states.
  • the diode D on the secondary side of the isolation transformer is reverse biased.
  • the DC input voltage V is applied solely across the first winding inductor P1 during the first time interval.
  • the output capacitor C 0 arranged on the secondary side of the isolation transformer begins to accumulate charge and accordingly the output voltage across the capacitor C 0 begins to rise.
  • both the controllable coupling switch S a1 and controllable clamp switch S c are placed in their respective conducting states.
  • the fifth time interval represents a second dead zone (second dead time interval), in which all controllable switches Si , S ai , S 2 and S c are switched into their respective non-conducting states.
  • the energy stored in the output capacitor of Si releases to maintain the current still flowing in the reverse direction.
  • the output voltage V 0 starts to drop while D is still forward biased.
  • the controllable switch Si of the first stage is switched back into its conducting state.
  • the next switching cycle of the present flyback converter starts accordingly with a smooth zero voltage switching (ZVS) in a continuous conduction mode CCM of operation.
  • ZVS smooth zero voltage switching
  • the voltage transfer function of the first embodiment of the DC-DC power converter with soft switching due to the shared active clamped stage corresponds to the voltage transfer function as discussed with respect to FIG. 5 for hard switching and is cited in equation (2).
  • the first and second dead time intervals result in achieving an advantageous ZVS behavior for the main switch of the DC-DC power converter.
  • FIG. 8 shows a time chart of the isolated DC-DC power converter in a flyback topology with the shared active clamp circuit of FIG. 5 with a high transformer turns ratio.
  • FIG. 9 shows the respective switching states corresponding to the time chart of FIG. 8 of the isolated DC-DC power converter in a flyback topology with the shared active clamp circuit 2 of FIG. 5 with a high transformer turns ratio.
  • the embodiment is a flyback DC-DC power converter with a first stage and a second stage and a shared active clamp circuit 2 arranged in series to the first stage and the second stage.
  • the flyback DC-DC converter operates in a continuous- conduction-mode (CCM).
  • a high transformer turns ratio n may apply in a phone adaptor application when the DC input voltage V, is high.
  • the further controllable switch S ai is set to a conducting state during the entire switching period or cycle of the main switch of the flyback converter.
  • the winding inductor P1 of the first stage and the winding inductor P2 of the second stage are electrically connected to each other through the coupling switch such that they commonly form the primary side winding with a large number of windings when compared to the number of windings of the first inductor P1 only. Consequently, also the turns ratio of the transformer of the inventive power converter is adapted.
  • the controllable modulating switch S 2 of the second stage which in the illustrated embodiment is of course the last added stage, functions as the main switch for controlling the modulation of the DC input voltage for example using PWM modulation.
  • the controllable switch Si is in a non conducting state during the switching cycle so that the combination of the first winding inductor P1 and the second winding inductor P2 commonly can act as one single primary side winding of the isolation transformer.
  • the controllable clamp switch Sc functions as active clamp switch of the shared active clamp circuit 2.
  • the controllable modulating switch S 2 of the second stage and the coupling switch S ai connecting the first stage and the second stage are in placed in respective conducting states.
  • the other controllable switches Si and S c are in a non-conducting state.
  • the diode D is reverse biased. Across the first winding inductor P1 one-half of the DC input voltage applies when the first winding inductor P1 equals the second inductor P2 with respect to the number of turns or windings.
  • the output capacitor C 0 arranged on the secondary side circuit of the converter, and of the isolation transformer, begins charging. Therefore, the voltage across the capacitor C o begins to increase or rise.
  • controllable coupling switch S a1 and the clamp switch S c are in a conducting state. Now, energy stored in a leakage inductance of the isolation transformer begins to discharge into the clamp capacitor C c .
  • the diode D is now forward biased.
  • the third time interval ends when the current through the first and second inductors P1 and P2 into the clamp capacitor C c reaches zero.
  • the controllable coupling switch S ai and the clamp switch S c are still in respective conducting states.
  • the leakage inductance energy has been fully discharged or released in the preceding third time interval.
  • the clamp capacitor C c begins to discharge and the current through the first and second inductors P1 , P2 is reversed.
  • the diode D on the secondary side of the isolation transformer is still forward biased.
  • the fifth time interval is the second dead zone, in which the controllable switches Si , S 2 and S c are switched to their respective non-conducting states.
  • the energy stored in the output capacitor of Si releases or discharges to maintain the current still in the reversed direction.
  • the voltage V 0 starts to drop while diode D on the secondary side of the isolation transformer is still forward biased.
  • the controllable switch S 2 is switched to the conducting state.
  • the next switching cycle of the flyback converter starts accordingly with a smooth zero voltage switching (ZVS) in a continuous conduction mode CCM.
  • ZVS smooth zero voltage switching
  • the preceding sections discuss an embodiment of the invention with reference to a flyback converter in CCM mode of operation.
  • the DC-DC power converter with further switches connecting and disconnecting inductors of additional stages and with a shared active clamp circuit invention is also applicable in a discontinuous mode of operation (DCM).
  • FIG. 10 is a simplified electrical circuit diagram of an isolated DC-DC power converter 5 in a flyback topology or forward topology with N stages with a shared active clamp circuit 2 in accordance with a second exemplary embodiment of the invention.
  • the second embodiment may correspond to the isolated DC-DC power converter in a flyback topology with N stages with a shared active clamp circuit 2 of the first embodiment.
  • the skilled person will appreciate that merely the position of the shared active clamp circuit 2 in the primary side circuit is changed in the circuitry according to FIG. 10.
  • the advantageous characteristics and benefits of the isolated DC-DC power converter according to FIG. 10 correspond to those characteristics and benefits of the isolated DC-DC power converter according to FIG. 5 and reference to the above discussion of FIG. 5 is considered sufficient for sake of conciseness.
  • the only difference that occurs is that the active clamp circuit 2 is connected to the last available stage of the primary side circuit and all intermediate stages between the first stage on the primary side or input side and the last stage need to be connected while switch S c is closed.
  • FIG. 1 1 A provides simulation results for an isolated DC-DC power converter in a flyback topology according to FIG. 5 with the controllable switch Si of the first stage acting as a main or modulating switch of the converter It is evident from the plot in FIG. 1 1 A that for the DC-DC power converter with the shared active clamp circuit 2, before the controllable switch Si of the first stage is closed, a drain-source voltage V ds1 (t) across switch Si has reached zero. As a result, when the controllable switch Si is switched to a conducting state, a zero-voltage-switching (ZWS) of the controllable switch Si is achieved.
  • ZWS zero-voltage-switching
  • FIG. 1 1 B provides simulation results for an isolated DC-DC power converter in a flyback topology according to FIG. 5 with the controllable switch S 2 acting as the main or modulating switch. Similar to FIG. 1 1 A, FIG. 1 1 B demonstrates that with the shared active clamp circuit 2, before the switch S 2 is closed, a voltage V ds2 (t) over the switch S 2 has decreased to a value of zero. As a result, when the switch S 2 is closed (switched into a conducting state), zero-voltage-switching of the controllable switch S 2 of the second stage is achieved.
  • the voltage versus time plots in FIGS. 1 1 A and 1 1 B depict simulations, which validate the performance and properties for a DC-DC power converter with the shared active clamp circuit 2.
  • the DC-DC power converter with the shared active clamp circuit 2 enables high power efficiency and high power density. This results from a decreased volume of the passive components by increasing the switching frequency.
  • the inventive DC-DC power converters achieve high efficiency and high power density by reducing the switching losses and recycling the leakage energy of the primary side winding inductors or winding segments by using the shared active clamp circuit.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

Un premier aspect de l'invention concerne un convertisseur de puissance CC-CC isolé qui comprend au moins un transformateur qui comprend un enroulement côté primaire et un enroulement côté secondaire enroulés sur un noyau magnétique commun. Le convertisseur de puissance CC-CC isolé comprend une pluralité d'étages, chaque étage comprenant un commutateur pouvant être commandé et une bobine d'induction d'enroulement. Les bobines d'induction d'enroulement de tous les deux étages adjacents sont connectées par l'intermédiaire d'un commutateur de couplage pouvant être commandé de manière à connecter ou déconnecter en série ces bobines d'induction d'enroulement pour former l'enroulement côté primaire avec un nombre réglable de tours. Le convertisseur de puissance CC-CC isolé comprend une bride de serrage active partagée pour les commutateurs pouvant être commandés.
PCT/EP2019/082108 2018-11-22 2019-11-21 Convertisseur de puissance cc-cc isolé à rapport de tours réglable Ceased WO2020104597A1 (fr)

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EP18207859.2 2018-11-22
EP18207859 2018-11-22

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WO2020104597A1 true WO2020104597A1 (fr) 2020-05-28

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Citations (6)

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US5808879A (en) * 1996-12-26 1998-09-15 Philips Electronics North America Corporatin Half-bridge zero-voltage-switched PWM flyback DC/DC converter
CN101171797A (zh) 2005-03-10 2008-04-30 高通股份有限公司 在易出错的无线广播信道上进行多路复用的方法
CN101174797A (zh) * 2007-08-14 2008-05-07 伊博电源（杭州）有限公司 可变匝比的同步整流变换器
WO2012155325A1 (fr) * 2011-05-16 2012-11-22 Intersil Americas Inc. Convertisseur de puissance cc/cc à large plage de tension d'entrée
US20130279208A1 (en) * 2012-04-23 2013-10-24 Delta Electronics, Inc. Power converter and controlling method
US20160087541A1 (en) * 2014-09-23 2016-03-24 Analog Devices Global Minimum duty cycle control for active snubber

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Publication number Priority date Publication date Assignee Title
US5808879A (en) * 1996-12-26 1998-09-15 Philips Electronics North America Corporatin Half-bridge zero-voltage-switched PWM flyback DC/DC converter
CN101171797A (zh) 2005-03-10 2008-04-30 高通股份有限公司 在易出错的无线广播信道上进行多路复用的方法
CN101174797A (zh) * 2007-08-14 2008-05-07 伊博电源（杭州）有限公司 可变匝比的同步整流变换器
WO2012155325A1 (fr) * 2011-05-16 2012-11-22 Intersil Americas Inc. Convertisseur de puissance cc/cc à large plage de tension d'entrée
US20130279208A1 (en) * 2012-04-23 2013-10-24 Delta Electronics, Inc. Power converter and controlling method
US20160087541A1 (en) * 2014-09-23 2016-03-24 Analog Devices Global Minimum duty cycle control for active snubber

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Title
KI-BUM PARK ET AL: "Series-Input Series-Rectifier Interleaved Forward Converter With a Common Transformer Reset Circuit for High-Input-Voltage Applications", IEEE TRANSACTIONS ON POWER ELECTRONICS, INSTITUTE OF ELECTRICAL AND ELECTRONICS ENGINEERS, USA, vol. 26, no. 11, 1 November 2011 (2011-11-01), pages 3242 - 3253, XP011369868, ISSN: 0885-8993, DOI: 10.1109/TPEL.2011.2148126 *

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