WO2024254763A1 - 确定通感探测结果的方法、装置及存储介质 - Google Patents

确定通感探测结果的方法、装置及存储介质 Download PDF

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Publication number
WO2024254763A1
WO2024254763A1 PCT/CN2023/099979 CN2023099979W WO2024254763A1 WO 2024254763 A1 WO2024254763 A1 WO 2024254763A1 CN 2023099979 W CN2023099979 W CN 2023099979W WO 2024254763 A1 WO2024254763 A1 WO 2024254763A1
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Prior art keywords
frequency domain
synaesthesia
signal
echo
sub
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English (en)
French (fr)
Inventor
张振宇
吴昱民
赵群
黄驿轩
叶启彬
胡泽林
胡苏�
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Beijing Xiaomi Mobile Software Co Ltd
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Beijing Xiaomi Mobile Software Co Ltd
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Priority to CN202380009690.4A priority Critical patent/CN116964993A/zh
Priority to EP23941001.2A priority patent/EP4730722A1/en
Priority to PCT/CN2023/099979 priority patent/WO2024254763A1/zh
Publication of WO2024254763A1 publication Critical patent/WO2024254763A1/zh
Anticipated expiration legal-status Critical
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/003—Transmission of data between radar, sonar or lidar systems and remote stations
    • G01S7/006—Transmission of data between radar, sonar or lidar systems and remote stations using shared front-end circuitry, e.g. antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines

Definitions

  • the present disclosure relates to the field of communication technology, and in particular to a method, an apparatus, a communication device and a computer-readable storage medium for determining a synaesthesia detection result.
  • synaesthesia detection technology also known as communication radar integration technology
  • the multipath effect that is prevalent in various wireless communication scenarios inevitably causes multipath interference in the detection results, resulting in more false targets in the synaesthesia detection and increasing the difficulty of radar detection.
  • the embodiments of the present disclosure provide a method for determining synaesthesia detection results, device communication, and computer-readable storage medium, which can solve the above-mentioned problems of the prior art.
  • the technical solution is as follows:
  • a method for determining a synaesthesia detection result comprising:
  • an operation cycle includes an up phase and a down phase
  • the synaesthesia frequency domain reception signal is determined by demodulating the echo signal, and the echo signal is a signal reflected by the terminal from the integrated signal sent by the network device in the downlink phase;
  • the integrated signal is determined by modulating the synaesthesia frequency domain transmission signal.
  • a device for determining a synaesthesia detection result comprising:
  • a processing module used to determine an uplink channel estimation result in an uplink phase and a synaesthesia frequency domain transmission signal and a synaesthesia frequency domain reception signal in a downlink phase in at least one operation cycle;
  • the processing module is further used to determine the synaesthesia detection result according to the uplink channel estimation result, the synaesthesia frequency domain transmission signal and the synaesthesia frequency domain reception signal of at least one operation cycle;
  • an operation cycle includes an up phase and a down phase
  • the synaesthesia frequency domain reception signal is determined by demodulating the echo signal, and the echo signal is a signal reflected by the terminal from the integrated signal sent by the device in the downlink phase;
  • the integrated signal is determined by modulating the synaesthesia frequency domain transmission signal.
  • a communication device includes a memory, a processor, and a computer program stored in the memory.
  • the processor executes the computer program to implement the method for determining synaesthesia detection results provided in the above aspect.
  • a computer-readable storage medium on which a computer program is stored.
  • the computer program is executed by a processor, the method for determining the synaesthesia detection result provided in the above aspect is implemented.
  • each operation cycle into two stages, the uplink and downlink stages.
  • the channel estimation of each operation cycle is obtained by receiving the uplink signal in the uplink stage.
  • FIG1 is a schematic diagram of the architecture of a communication system provided by an embodiment of the present disclosure.
  • FIG2a is a schematic flow chart of a method for determining a synaesthesia detection result provided by an embodiment of the present disclosure
  • FIG2b is a schematic diagram of an operation cycle provided by an embodiment of the present disclosure.
  • FIG2c is a schematic diagram of a process of sending an integrated signal, receiving an echo, and performing radar processing through a transmitting end (Tx) of a network device provided in an embodiment of the present disclosure
  • FIG3a is a schematic diagram of a radar image obtained by a method for determining a synaesthesia detection result provided by the related art
  • FIG3 b is a schematic diagram of a radar image obtained by a method for determining a synaesthesia detection result provided by an embodiment of the present disclosure
  • FIG4 is a schematic diagram of the structure of a device for determining synaesthesia detection results provided by an embodiment of the present disclosure
  • FIG5 is a schematic diagram of the structure of a communication device provided in an embodiment of the present disclosure.
  • connection or “coupling” used herein may include wireless connection or wireless coupling.
  • connection or “coupling” used herein may include wireless connection or wireless coupling.
  • connection or “coupling” used herein may include wireless connection or wireless coupling.
  • and/or indicates at least one of the items defined by the term, for example, “A and/or B” can be implemented as “A”, or as “B”, or as “A and B”.
  • Wired channels include open wires, symmetrical cables, coaxial cables and optical cables; wireless channels include ground wave propagation, shortwave ionospheric reflection, ultra-short wave or microwave line-of-sight relay, artificial satellite relay and various scattering channels.
  • Signals propagate in wireless channels, and the received signal is not only obtained through a single direct path, but also includes reflections, diffractions and data signals arriving through different paths. This phenomenon is called multipath propagation, and the channel is called a multipath channel.
  • Orthogonal Frequency Division Multiplexing realizes parallel transmission of high-speed serial data through frequency division multiplexing. It has good resistance to multipath fading and can support multi-user access.
  • the cyclic prefix is formed by copying the signal at the end of the OFDM symbol to the head.
  • CP There are two main lengths of CP, namely Normal Cyclic Prefix and Extended Cyclic Prefix.
  • the cyclic prefix can be associated with other multipath component information to obtain complete information.
  • the cyclic prefix can realize time estimation and frequency synchronization.
  • Discrete Fourier Transform is a Fourier transform in discrete form in both time and frequency domains, which transforms the time domain sampling of the signal into the frequency domain sampling of its DTFT.
  • the sequences at both ends of the transform are of finite length, but in fact both sets of sequences should be considered as the main value sequences of discrete periodic signals. Even if DFT is performed on a discrete signal of finite length, it should be considered as a transformation of its periodic extension. In practical applications, fast Fourier transform is usually used to calculate DFT.
  • the method for determining synaesthesia detection results, device communication, and computer-readable storage medium provided in the present disclosure are intended to solve the above technical problems in the prior art.
  • FIG1 is a schematic diagram of the architecture of a communication system provided in an embodiment of the present disclosure.
  • the communication system 100 includes a terminal 101 and a network device 102 .
  • the terminal 101 includes, for example, a mobile phone, a wearable device, an Internet of Things device, a car with communication function, a smart car, a tablet computer (Pad), a computer with wireless transceiver function, a virtual reality (VR) terminal device, an augmented reality (AR) terminal device, a wireless terminal device in industrial control, a wireless terminal device in self-driving, a wireless terminal device in remote medical surgery, a wireless terminal device in a smart grid, a wireless terminal device in transportation safety, a wireless terminal device in a smart city, and at least one of a wireless terminal device in a smart home, but is not limited to these.
  • a mobile phone a wearable device, an Internet of Things device, a car with communication function, a smart car, a tablet computer (Pad), a computer with wireless transceiver function, a virtual reality (VR) terminal device, an augmented reality (AR) terminal device, a wireless terminal device in industrial control, a wireless terminal device in self-driving, a wireless terminal device
  • network device 102 may include an access network device.
  • the access network device is, for example, a node or device that accesses a terminal to a wireless network, and may include an evolved NodeB (eNB), a next generation evolved NodeB (ng-eNB), a next generation NodeB (gNB), a node B (NB), a home node B (HNB), a home evolved nodeB (HeNB), a wireless backhaul device, a radio network controller (RNC), a base station controller (BSC), a base transceiver station (BTS), a base band unit (BBU), a mobile switching center, a base station in a 6G communication system, an open base station (Open RAN), a cloud base station (Cloud RAN), and other communication systems. At least one of a base station in a wireless fidelity (WiFi) system, but not limited thereto.
  • WiFi wireless fidelity
  • the technical solutions of the embodiments of the present disclosure may be applicable to the Open RAN architecture.
  • the interfaces between or within network devices involved in the embodiments of the present disclosure may become internal interfaces of Open RAN, and the processes and information interactions between these internal interfaces may be implemented through software or programs.
  • the access network device may be composed of a centralized unit (central unit, CU) and a distributed unit (distributed unit, DU), wherein the CU may also be called a control unit (control unit).
  • the CU-DU structure may be used to split the protocol layer of the network device, with some functions of the protocol layer being centrally controlled by the CU, and the remaining part or all of the functions of the protocol layer being distributed in the DU, and the DU being centrally controlled by the CU, but not limited to this.
  • the communication system described in the embodiment of the present disclosure is for the purpose of more clearly illustrating the technical solution of the embodiment of the present disclosure, and does not constitute a limitation on the technical solution proposed in the embodiment of the present disclosure.
  • a person of ordinary skill in the art can know that with the evolution of the system architecture and the emergence of new business scenarios, the technical solution proposed in the embodiment of the present disclosure is also applicable to similar technical problems.
  • the following embodiments of the present disclosure may be applied to the communication system 100 shown in FIG1 , or part of the subject, but are not limited thereto.
  • the subjects shown in FIG1 are examples, and the communication system may include all or part of the subjects in FIG1 , or may include other subjects other than FIG1 , and the number and form of the subjects are arbitrary, and the connection relationship between the subjects is an example, and the subjects may be connected or disconnected, and the connection may be in any manner, which may be a direct connection or an indirect connection, and may be a wired connection or a wireless connection.
  • LTE Long Term Evolution
  • LTE-A LTE-Advanced
  • LTE-B LTE-Beyond
  • SUPER 3G IMT-Advanced
  • fourth generation mobile communication system (4G) fifth generation mobile communication system
  • 5G 5G new radio
  • NR future radio access
  • FX new radio access technology
  • GSM Global System for Mobile communications
  • CDMA2000 Ultra Mobile Broadband
  • UMB Ultra Mobile Broadband
  • IEEE 802.11 Wi-Fi (registered trademark)
  • IEEE 802.16 WiMAX (registered trademark)
  • IEEE 802.20 Ultra-WideBand (UWB), Bluetooth (registered trademark), Public Land Mobile Network (PLMN) network
  • D2D Device-to-Device
  • M2M Machine-to-Machine
  • IoT Vehicle-to-Everything
  • V2X Vehicle-to-Everything
  • a method for determining a synaesthesia detection result is provided, which is applied to a network device. As shown in FIG2a , the method includes:
  • the number of operating cycles is the number of radar processing estimate symbols N f .
  • Each operation cycle of the embodiment of the present disclosure is further divided into an uplink phase and a downlink phase.
  • the terminal sends an uplink signal containing a training sequence or a pilot to the network device.
  • the network device sends a downlink communication radar integrated signal (also referred to as an integrated signal) to the terminal and receives an echo signal reflected by the integrated signal from the terminal.
  • a downlink communication radar integrated signal also referred to as an integrated signal
  • the duration of the uplink phase and the downlink phase in each operation cycle are consistent.
  • the total number of OFDM subcarriers is N
  • the basic symbol period is T
  • the cyclic prefix period is T CP
  • the symbol period is T sym
  • T sym T+T CP
  • the cyclic prefix length N CP NT CP /T
  • FIG. 2b exemplarily shows a schematic diagram of an operation cycle provided by an embodiment of the present disclosure.
  • the duration of the uplink phase and the downlink phase of the embodiment of the present disclosure is T sym .
  • the terminal sends an uplink signal including a training sequence or a pilot to the network device.
  • the network equipment performs uplink channel estimation and communication reception.
  • the network equipment sends an integrated signal to the terminal, receives the echo signal and performs radar processing.
  • the uplink signal sent by the terminal is an OFDM symbol including a pilot or training, so that the network device performs uplink channel estimation through an existing channel estimation method.
  • the uplink channel estimation result obtained by the network device is a channel time domain response of one-way propagation in the corresponding uplink stage.
  • the one-way propagation channel is a Rician channel.
  • one-way transmission refers to the transmission of signals from the first communication device to the second communication device
  • two-way transmission refers to the transmission of signals from the first communication device to the second communication device and then back to the first communication device.
  • first communication device refers to the terminal
  • second communication device refers to the network device
  • first communication device refers to the network device
  • second communication device refers to the terminal
  • one-way transmission in the uplink phase refers to the transmission of signals from the terminal to the network device.
  • the network device of the embodiment of the present disclosure sends a downlink integrated signal to the terminal and receives an echo signal in each downlink phase.
  • FIG. 2c is a schematic diagram of a flow chart of sending an integrated signal, receiving an echo signal and performing radar processing through a transmitting end (Tx) of a network device provided by an embodiment of the present disclosure. As shown in the figure, for the ⁇ th operation cycle, it includes:
  • the binary data is converted into RadCom frequency domain symbols (also called RadCom frequency domain symbols) through quadrature amplitude modulation (QAM) or phase amplitude modulation (PAM). It can be understood that X ⁇ [k] is the synaesthesia frequency domain symbol of the k-th subcarrier of the ⁇ -th operating cycle transmitted;
  • the synaesthesia frequency domain symbol is subjected to serial/parallel conversion (S/P) to obtain a first synaesthesia frequency domain symbol vector (i.e., synaesthesia frequency domain transmission signal)
  • X ⁇ [X ⁇ [0], X ⁇ [1], ..., X ⁇ [N-1]] T , wherein the superscript T represents a transposition budget;
  • IDFT Inverse Discrete Fourier Transform
  • the ⁇ th synaesthesia time domain transmission signal of the synaesthesia time domain symbol vector (also called the time domain sampling of the ⁇ th downlink OFDM symbol) is expressed as:
  • Nf is the number of operating cycles.
  • the signal obtained by modulating the synaesthesia time domain transmission signal is sent to the channel as an integrated signal, thereby completing the process of sending the downlink integrated signal.
  • the modulation includes performing parallel-to-serial (P/S) conversion on the synaesthesia time domain transmission signal, adding a cyclic prefix CP, performing digital-to-analog conversion (D/A), and the like.
  • P/S parallel-to-serial
  • D/A digital-to-analog conversion
  • the network device After sending the integrated signal to the terminal, the network device further receives the arriving signal (i.e., the echo signal of the integrated signal transmitted by the terminal) after being acted upon by the channel;
  • the arriving signal i.e., the echo signal of the integrated signal transmitted by the terminal
  • the received echo signal is demodulated to obtain the second synaesthesia frequency domain symbol vector (i.e., synaesthesia frequency domain received signal) Y ⁇ [k] represents the echo frequency domain term of the k-th subcarrier received in the ⁇ -th operation cycle;
  • demodulation includes performing analog-to-digital conversion (A/D) on the echo signal, removing the CP, and then mapping it to the frequency domain through discrete Fourier transform DFT through S/P.
  • A/D analog-to-digital conversion
  • the received signal in the synaesthesia frequency domain is also divided into two paths, one for radar processing and the other for channel equalization to compensate for channel distortion;
  • the equalization may use a minimum mean-squared error (MMSE) or zero forcing (ZF) equalizer;
  • MMSE minimum mean-squared error
  • ZF zero forcing
  • the MMSE equalization coefficient is:
  • the ZF balance coefficient is:
  • H * [k] represents the conjugate operation of H[k]
  • ⁇ b and N0 are the power spectral density of the signal energy per bit and the additive white Gaussian noise AWGN (Additive White Gaussian Noise), respectively;
  • the equalized signal can be expressed as the IDFT result of multiplying the received signal in the frequency domain by the equalization coefficient:
  • S202 Determine a synaesthesia detection result according to an uplink channel estimation result of at least one operation cycle, a synaesthesia frequency domain transmission signal, and a synaesthesia frequency domain reception signal.
  • the embodiment of the present disclosure can determine the uplink channel estimation result of the operation cycle based on the received uplink signal of the operation cycle.
  • the uplink phase and the downlink phase are within the coherence time, it can be considered that the channel information in the uplink phase and the downlink phase has not changed. Due to the reciprocity of the channel, the integrated signal undergoes two approximately identical channel propagations in the uplink phase and the adjacent downlink phase in the same operation cycle.
  • the embodiment of the present disclosure performs uplink channel estimation based on the received uplink signal to obtain a one-way uplink channel estimation result, and obtains a channel estimation result of the echo signal after two-way propagation, so as to use the two-way channel estimation results and the integrated signal to process the echo signal, thereby effectively eliminating the inherent radar multipath interference of the terminal.
  • the disclosed embodiment analyzes the generation logic and transmission process of the echo signal, and determines that on the basis of the existing integrated signal, further processing the echo signal in combination with the propagation channel estimation can effectively eliminate the radar multipath interference inherent in the terminal.
  • the disclosed embodiment subdivides each operation cycle into two stages, the uplink and downlink stages. By receiving the uplink signal in the uplink stage and analyzing the uplink signal, the uplink channel estimation result of each operation cycle is obtained.
  • determining the synaesthesia detection result according to the uplink channel estimation result, the synaesthesia frequency domain transmission signal and the synaesthesia frequency domain reception signal of at least one operation cycle includes:
  • the synaesthesia detection result is determined according to the echo channel frequency domain response, the synaesthesia frequency domain transmission signal and the synaesthesia frequency domain reception signal of at least one operation cycle.
  • the frequency domain transmission signal refers to the OFDM frequency domain symbol in the transmitted integrated signal.
  • the frequency domain received signal refers to a frequency domain symbol in the received echo signal.
  • OFDM frequency domain symbols refer to frequency domain samples of OFDM symbols.
  • the echo channel frequency domain response is a channel frequency domain response of an echo signal after two-pass propagation.
  • the frequency domain response of a channel refers to the frequency domain sampling of a channel impulse response.
  • the time domain response of a channel refers to the time domain sampling of a channel impulse response.
  • the embodiment of the present disclosure will retain one synaesthesia frequency domain transmission signal, and in the process of receiving the echo signal, it will also retain one synaesthesia frequency domain reception signal, thereby determining the synaesthesia detection results of the terminal in multiple operating cycles based on the echo channel frequency domain response, synaesthesia frequency domain transmission signal and synaesthesia frequency domain reception signal of each operating cycle.
  • the uplink channel estimation result includes a channel time domain response of one-way propagation.
  • the echo channel frequency domain response of the operation period is determined, including:
  • the echo channel frequency domain response of the operation period is determined according to the channel frequency domain response of the one-way propagation of the operation period.
  • the uplink signal of the present disclosure may include a training sequence or a pilot, so that the channel estimation is performed based on the training sequence or the pilot through the existing channel estimation method to determine the channel time domain response of the one-way propagation of the operation period.
  • h ⁇ [n] represents the channel time domain response coefficient of the nth channel in the ⁇ th operation cycle
  • the network device since the network device needs to detect the terminal in the downlink phase, its signal undergoes two-pass propagation. In order to ensure the radar ranging performance, the total time of the two-pass propagation cannot be longer than the cyclic prefix duration of the OFDM symbol, that is, the multipath channel length Nch in the embodiment of the present disclosure satisfies Nch ⁇ Ncp /2. Maximum transmission delay
  • the channel frequency domain response of one-way propagation can be obtained by mapping it to the frequency domain through DFT (which can be expressed as ).
  • the channel frequency domain response coefficient of the kth subcarrier of the echo channel frequency domain response can be determined according to two one-way channel frequency domain responses of the subcarrier in the downlink phase.
  • the echo channel frequency domain response of the operation cycle may be obtained by performing a linear convolution operation on the two channel time domain responses.
  • the echo channel frequency domain response of the operation period is determined, including:
  • the echo channel frequency domain response H r, ⁇ [k] of the operation period is determined.
  • each synaesthesia frequency domain transmission signal includes OFDM frequency domain symbols of all subcarriers in the corresponding downlink phase.
  • the OFDM frequency domain symbol of the kth subcarrier in the ⁇ th downlink phase can be represented as X ⁇ [k].
  • each echo channel frequency domain response includes channel frequency domain response coefficients of all subcarriers in the corresponding downlink stage.
  • the echo channel frequency domain response of the ⁇ th downlink stage can be expressed as H r, ⁇
  • the channel frequency domain response coefficient of the kth subcarrier of the echo channel frequency domain response can be expressed as H r, ⁇ [k].
  • each synaesthesia frequency domain received signal includes an echo frequency domain item Y ⁇ of all subcarriers in the corresponding downlink phase
  • each echo frequency domain item includes a first sub-item related to the OFDM frequency domain symbol of the corresponding subcarrier, a second sub-item related to the channel frequency domain response coefficient of the corresponding subcarrier, and a third sub-item related to the synaesthesia detection result of the terminal.
  • ⁇ ⁇ [n] represents additive white Gaussian noise (AWGN)
  • h ⁇ [n] represents the time domain response coefficient of the nth subcarrier in the ⁇ th downlink phase
  • * represents a linear convolution operation
  • x ⁇ ,echo [n] represents the reflected echo term of the time domain sample x ⁇ [n] of the OFDM frequency domain symbol of the nth subcarrier in the ⁇ th downlink phase, which can be expressed by the following formula:
  • f c is the carrier frequency, c is the speed of light;
  • R and v are the distance and relative speed between the terminal and the subject of the present disclosure, respectively, and are parameters to be determined;
  • PRI is the pulse repetition interval
  • PRI 2T sym .
  • determining the synaesthesia detection results of the terminal in multiple operation cycles according to the echo channel frequency domain response, the synaesthesia frequency domain transmission signal and the synaesthesia frequency domain reception signal of at least one operation cycle includes:
  • the synaesthesia detection result is determined according to the third sub-item corresponding to each sub-carrier in at least one downlink phase.
  • each echo frequency domain term in the embodiment of the present disclosure includes three sub-terms, wherein the first sub-term is X ⁇ [k], the second sub-term is (H ⁇ [k]) 2 , and the third sub-term is
  • the distance factor is related to the subcarrier k and the echo delay L of the terminal
  • the speed factor is related to the operating period ⁇ and the Doppler frequency deviation f D of the terminal.
  • the embodiment of the present disclosure can establish a quotient matrix, in which the divisor of each element in the quotient matrix is the product of the OFDM frequency domain symbol of the subcarrier in the synesthesia frequency domain transmission signal of a subcarrier in a downlink phase and the channel frequency domain response coefficient of the subcarrier in the echo channel frequency domain response, and the dividend is the echo frequency domain item of the subcarrier in the downlink phase, thereby converting the echo frequency domain item in the echo frequency domain item into the product of the OFDM frequency domain symbol of the subcarrier in the synesthesia frequency domain transmission signal of a subcarrier in a downlink phase.
  • the first sub-item and the second sub-item are eliminated to obtain the third sub-item of the echo frequency domain item of the subcarrier in the downlink phase;
  • each complete OFDM frequency domain symbol is arranged in a matrix form as one column, that is, the following matrix is obtained:
  • the element values of the above quotient matrix can also be determined. By combining all the element values of the quotient matrix, the distance information and relative speed information can be obtained.
  • determining the synaesthesia detection result of the terminal according to the third sub-item corresponding to each subcarrier in each downlink phase includes:
  • DFT discrete Fourier transform
  • a synaesthesia detection result is determined according to a fifth sub-item corresponding to at least one subcarrier in at least one downlink phase.
  • the embodiment of the present disclosure can perform an IDFT operation of N elements on each column of the above-mentioned quotient matrix M D , so that the elements in the quotient matrix M D are updated to the fourth sub-item corresponding to the subcarrier to extract the distance information of the terminal, and then perform a DFT operation of N f elements on each row of the matrix after the IDFT operation, so that the elements in the matrix are further updated to the fifth sub-item corresponding to the subcarrier to extract the speed information of the terminal.
  • the absolute values of the elements of the matrix obtained by the DFT operation can obtain a three-dimensional radar display image, and then obtain the synaesthesia detection result.
  • the distance resolution of this method is c/(2N ⁇ f) and the speed resolution is c/(4N f f c T sym ).
  • the uplink channel estimation result adopts the ideal channel estimation result, and the simulation parameters are: the number of subcarriers is 1620, the number of accumulated symbols is 560, the carrier frequency is 5GHz, the subcarrier spacing is 60kHz, the CP period is 1.2 ⁇ s, the bandwidth is 97.2MHz, the maximum effective range is 179.9m, the maximum detection speed is ⁇ 419.5m/s, the distance resolution is 1.54m, and the speed resolution is 1.5m/s.
  • Figures 3a and 3b are schematic diagrams of the range-speed radar images obtained by the related art and the present disclosure respectively.
  • the integrated echo signal presents multiple multipath false target peaks on the range axis in the range-speed radar image after radar processing.
  • the multipath interference elimination processing proposed in the present disclosure the multipath false target peaks in the radar image are eliminated, and only the required communication target detection peak value remains, and its distance and relative speed are accurate. It can be seen that the embodiment of the present disclosure can effectively eliminate the radar multipath interference of the communication target user in the radar image.
  • the present disclosure provides a device for determining a synaesthesia detection result.
  • the device may include: a processing module 401 for determining an uplink phase in at least one operation cycle; Uplink channel estimation results and downlink phase synaesthesia frequency domain transmission signal and synaesthesia frequency domain reception signal;
  • the processing module 401 is further used to determine the synaesthesia detection result according to the uplink channel estimation result, the synaesthesia frequency domain transmission signal and the synaesthesia frequency domain reception signal of at least one operation cycle;
  • an operation cycle includes an up phase and a down phase
  • the synaesthesia frequency domain receiving signal is determined by demodulating the echo signal, and the echo signal is the signal reflected by the terminal from the integrated signal sent by the device in the downlink stage;
  • the integrated signal is determined by modulating the signal sent in the synaesthesia frequency domain.
  • the device of the embodiments of the present disclosure can execute the method provided by the embodiments of the present disclosure, and the implementation principles are similar.
  • the actions performed by each module in the device of each embodiment of the present disclosure correspond to the steps in the method of each embodiment of the present disclosure.
  • a communication device including a memory, a processor and a computer program stored in the memory.
  • the processor executes the above-mentioned computer program to implement the steps of a method for determining a synaesthesia detection result.
  • it can be achieved: by analyzing the generation logic and transmission process of the echo signal, it is determined that on the basis of the existing integrated signal, the echo signal is further processed in combination with the propagation channel estimation, which can effectively eliminate the terminal's inherent radar multipath interference.
  • the embodiment of the present disclosure subdivides each operating cycle into two stages, an uplink stage and a downlink stage. By receiving the uplink signal in the uplink stage and parsing the uplink signal, the channel estimation of each operating cycle is obtained.
  • a communication device is provided, as shown in FIG5 , and the communication device 4000 shown in FIG5 includes: a processor 4001 and a memory 4003.
  • the processor 4001 and the memory 4003 are connected, such as through a bus 4002.
  • the communication device 4000 may also include a transceiver 4004, which may be used for data interaction between the communication device and other communication devices, such as data transmission and/or data reception.
  • the transceiver 4004 is not limited to one, and the structure of the communication device 4000 does not constitute a limitation on the embodiments of the present disclosure.
  • Processor 4001 may be a CPU (Central Processing Unit), a general-purpose processor, a DSP (Digital Signal Processor), an ASIC (Application Specific Integrated Circuit), an FPGA (Field Programmable Gate Array) or other programmable logic devices, transistor logic devices, hardware components or any combination thereof. It may implement or execute various exemplary logic blocks, modules and circuits described in conjunction with the disclosure of the present invention. Processor 4001 may also be a combination that implements computing functions, such as a combination of one or more microprocessors, a combination of a DSP and a microprocessor, etc.
  • the bus 4002 may include a path for transmitting information between the above components.
  • the bus 4002 may be a PCI (Peripheral Component Interconnect) bus or an EISA (Extended Industry Standard Architecture) bus.
  • the bus 4002 may be divided into an address bus, a data bus, a control bus, etc.
  • FIG5 is represented by only one thick line, but it does not mean that there is only one bus or one type of bus.
  • the memory 4003 can be a ROM (Read Only Memory) or other types of static storage devices that can store static information and instructions, a RAM (Random Access Memory) or other types of dynamic storage devices that can store information and instructions, or it can be an EEPROM (Electrically Erasable Programmable Read Only Memory), a CD-ROM (Compact Disc Read Only Memory) or other optical disk storage, optical disk storage (including compressed optical disk, laser disk, optical disk, digital versatile disk, Blu-ray disk, etc.), magnetic disk storage media, other magnetic storage devices, or any other medium that can be used to carry or store computer programs and can be read by a computer, without limitation herein.
  • ROM Read Only Memory
  • RAM Random Access Memory
  • EEPROM Electrically Erasable Programmable Read Only Memory
  • CD-ROM Compact Disc Read Only Memory
  • optical disk storage including compressed optical disk, laser disk, optical disk, digital versatile disk, Blu-ray disk, etc.
  • magnetic disk storage media other magnetic storage devices, or any other medium that can be used to carry or store computer programs
  • the memory 4003 is used to store the computer program for executing the embodiment of the present disclosure, and the execution is controlled by the processor 4001.
  • the processor 4001 is used to execute the computer program stored in the memory 4003 to implement the steps shown in the above method embodiment.
  • An embodiment of the present disclosure provides a computer-readable storage medium, on which a computer program is stored.
  • the computer program is executed by a processor, the steps and corresponding contents of the aforementioned method embodiment can be implemented.
  • the embodiments of the present disclosure also provide a computer program product, including a computer program, which can implement the steps and corresponding contents of the aforementioned method embodiments when executed by a processor.
  • the flowchart of the embodiment of the present disclosure indicates each operation step by arrows
  • the implementation order of these steps is not limited to the order indicated by the arrows.
  • the implementation steps in each flowchart can be executed in other orders according to demand.
  • some or all of the steps in each flowchart may include multiple sub-steps or multiple stages based on the actual implementation scenario. Some or all of these sub-steps or stages can be executed at the same time, and each sub-step or stage in these sub-steps or stages can also be executed at different times. In scenarios with different execution times, the execution order of these sub-steps or stages can be flexibly configured according to demand, and the embodiment of the present disclosure does not limit this.

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Abstract

本公开实施例提供了一种确定通感探测结果的方法、装置、通信设备及存储介质，涉及通信领域。该方法包括：确定至少一个运行周期中上行阶段的上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号；根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果；一个运行周期包括上行阶段和下行阶段；通感频域接收信号是对回波信号进行解调确定的，回波信号为网络设备在下行阶段发送的一体化信号经终端反射的信号；一体化信号是对通感频域发送信号进行调制确定的。本公开实施例可以有效消除终端固有的雷达多径干扰。

Description

确定通感探测结果的方法、装置及存储介质 技术领域
本公开涉及通信技术领域，具体而言，本公开涉及一种确定通感探测结果的方法、装置、通信设备及计算机可读存储介质。
背景技术
随着通信信息技术的快速发展，在6G、车联网、无人机组网以及军事应用等领域中，为了实现通信类与感知类业务的深度融合，需对通感探测技术(也称为通信雷达一体化技术)进行深入研究。
在无线通信各种场景中普遍存在的多径效应，不可避免的在探测结果中出现多径干扰，使得通感探测出现较多虚假目标，增加雷达检测难度。
相关技术，例如雷达杂波处理方案、虚假目标消除方案都无法有效消除环境目标固有的雷达多径干扰，此难题对通感探测技术的发展与推广造成了阻碍。
发明内容
本公开实施例提供了一种确定通感探测结果的方法、装置通信及计算机可读存储介质，可以解决现有技术的上述问题。所述技术方案如下：
根据本公开实施例的一个方面，提供了一种确定通感探测结果的方法，该方法包括：
确定至少一个运行周期中上行阶段的上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号；
根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果；
其中，一个运行周期包括上行阶段和下行阶段；
所述通感频域接收信号是对回波信号进行解调确定的，所述回波信号为所述网络设备在下行阶段发送的一体化信号经终端反射的信号；
所述一体化信号是对所述通感频域发送信号进行调制确定的。
根据本公开实施例的另一个方面，提供了一种确定通感探测结果的装置，该装置包括：
处理模块，用于确定至少一个运行周期中上行阶段的上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号；
处理模块，还用于根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果；
其中，一个运行周期包括上行阶段和下行阶段；
所述通感频域接收信号是对回波信号进行解调确定的，所述回波信号为装置在下行阶段发送的一体化信号经终端反射的信号；
所述一体化信号是对所述通感频域发送信号进行调制确定的。
根据本公开实施例的另一个方面，提供了一种通信设备，该通信设备包括存储器、处理器及存储在存储器上的计算机程序，处理器执行计算机程序以实现上述方面提供的确定通感探测结果的方法。
根据本公开实施例的再一个方面，提供了一种计算机可读存储介质，其上存储有计算机程序，计算机程序被处理器执行时实现上述方面提供的确定通感探测结果的方法。
本公开实施例提供的技术方案带来的有益效果是：
通过对回波信号的生成逻辑和传输过程进行分析，确定在现有的一体化信号的基础上，进一步结合传播的信道估计对回波信号进行处理，可以有效消除环境目标固有的雷达多径干扰，为了获得单程传播的信道估计，本公开实施例将每个运行周期细分为了上、下行两个阶段，通过在上行阶段接收上行信号获得每个运行周期的信道估计。
附图说明
为了更清楚地说明本公开实施例中的技术方案，下面将对本公开实施例描述中所需要使用的附图作简单地介绍。
图1为本公开实施例提供的通信系统的架构示意图；
图2a为本公开实施例提供的一种确定通感探测结果的方法的流程示意图；
图2b为本公开实施例提供的运行周期的示意图；
图2c为本公开实施例提供的通过网络设备的发送端(Tx)发送一体化信号、接收回波并进行雷达处理的流程示意图；
图3a为相关技术提供的一种确定通感探测结果的方法获得的雷达图像示意图；
图3b为本公开实施例提供的一种确定通感探测结果的方法获得的雷达图像示意图；
图4为本公开实施例提供的一种确定通感探测结果的装置的结构示意图；
图5为本公开实施例提供的一种通信设备的结构示意图。
具体实施方式
下面结合本公开中的附图描述本公开的实施例。应理解，下面结合附图所阐述的实施方式，是用于解释本公开实施例的技术方案的示例性描述，对本公开实施例的技术方案不构成限制。
本技术领域技术人员可以理解，除非特意声明，这里使用的单数形式“一”、“一个”和“该”也可包括复数形式。应该进一步理解的是，本公开实施例所使用的术语“包括”以及“包含”是指相应特征可以实现为所呈现的特征、信息、数据、步骤、操作、元件和/或组件，但不排除实现为本技术领域所支持其他特征、信息、数据、步骤、操作、元件、组件和/或它们的组合等。应该理解，当我们称一个元件被“连接”或“耦接”到另一元件时，该一个元件可以直接连接或耦接到另一元件，也可以 指该一个元件和另一元件通过中间元件建立连接关系。此外，这里使用的“连接”或“耦接”可以包括无线连接或无线耦接。这里使用的术语“和/或”指示该术语所限定的项目中的至少一个，例如“A和/或B”可以实现为“A”，或者实现为“B”，或者实现为“A和B”。
为使本公开的目的、技术方案和优点更加清楚，下面将结合附图对本公开实施方式作进一步地详细描述。
首先对本公开涉及的几个名词进行介绍和解释：
信道(channel)是信号的传输媒质，可分为有线信道和无线信道两类。有线信道包括明线、对称电缆、同轴电缆及光缆等；无线信道有地波传播、短波电离层反射、超短波或微波视距中继、人造卫星中继以及各种散射信道等。信号在无线信道中传播，接收信号不仅是通过单一直射路径得到，还包括不同路径到达的反射、衍射和数据信号，这种现象称为多径传播，该信道称为多径信道(Multi-path channel)。
正交频分复用(Orthogonal Frequency Division Multiplexing，OFDM)技术，通过频分复用实现高速串行数据的并行传输,它具有较好的抗多径衰落的能力，能够支持多用户接入。
循环前缀(Cyclic Prefix，CP)是将OFDM符号尾部的信号复制到头部构成的。CP的长度主要有两种，分别为常规循环前缀(Normal Cyclic Prefix)和扩展循环前缀(Extended Cyclic Prefix)。循环前缀可以与其他多径分量信息相关联，得到完整的信息。此外循环前缀可以实现时间的预估计和频率同步。
离散傅里叶变换(Discrete Fourier Transform，DFT)，是傅里叶变换在时域和频域上都呈离散的形式，将信号的时域采样变换为其DTFT的频域采样。在形式上，变换两端(时域和频域上)的序列是有限长的，而实际上这两组序列都应当被认为是离散周期信号的主值序列。即使对有限长的离散信号作DFT，也应当将其看作其周期延拓的变换。在实际应用中通常采用快速傅里叶变换计算DFT。
本公开提供的确定通感探测结果的方法、装置通信以及计算机可读存储介质，旨在解决现有技术的如上技术问题。
下面通过对几个示例性实施方式的描述，对本公开实施例的技术方案以及本公开的技术方案产生的技术效果进行说明。需要指出的是，下述实施方式之间可以相互参考、借鉴或结合，对于不同实施方式中相同的术语、相似的特征以及相似的实施步骤等，不再重复描述。
图1为本公开实施例提供的通信系统的架构示意图，通信系统100包括终端(terminal)101和网络设备102。
在一些实施例中，终端101例如包括手机(mobile phone)、可穿戴设备、物联网设备、具备通信功能的汽车、智能汽车、平板电脑(Pad)、带无线收发功能的电脑、虚拟现实(virtual reality，VR)终端设备、增强现实(augmented reality，AR)终端设备、工业控制(industrial control)中的无线终端设备、无人驾驶(self-driving)中的无线终端设备、远程手术(remote medical surgery)中的无线终端设备、智能电网(smart grid)中的无线终端设备、运输安全(transportation safety)中的无线终端设备、智慧城市(smart city)中的无线终端设备、智慧家庭(smart home)中的无线终端设备中的至少一者，但不限于此。
在一些实施例中，网络设备102可以包括接入网设备。
在一些实施例中，接入网设备例如是将终端接入到无线网络的节点或设备，可以包括5G通信系统中的演进节点B(evolved NodeB，eNB)、下一代演进节点B(next generation eNB，ng-eNB)、下一代节点B(next generation NodeB，gNB)、节点B(node B，NB)、家庭节点B(home node B，HNB)、家庭演进节点B(home evolved nodeB，HeNB)、无线回传设备、无线网络控制器(radio network controller，RNC)、基站控制器(base station controller，BSC)、基站收发台(base transceiver station，BTS)、基带单元(base band unit，BBU)、移动交换中心、6G通信系统中的基站、开放型基站(Open RAN)、云基站(Cloud RAN)、其他通信系统 中的基站、无线保真(wireless fidelity，WiFi)系统中的接入节点中的至少一者，但不限于此。
在一些实施例中，本公开实施例的技术方案可适用于Open RAN架构，此时，本公开实施例所涉及的网络设备间或者网络设备内的接口可变为Open RAN的内部接口，这些内部接口之间的流程和信息交互可以通过软件或者程序实现。
在一些实施例中，接入网设备可以由集中单元(central unit，CU)与分布式单元(distributed unit，DU)组成的，其中，CU也可以称为控制单元(control unit)，采用CU-DU的结构可以将网络设备的协议层拆分开，部分协议层的功能放在CU集中控制，剩下部分或全部协议层的功能分布在DU中，由CU集中控制DU，但不限于此。
可以理解的是，本公开实施例描述的通信系统是为了更加清楚的说明本公开实施例的技术方案，并不构成对于本公开实施例提出的技术方案的限定，本领域普通技术人员可知，随着系统架构的演变和新业务场景的出现，本公开实施例提出的技术方案对于类似的技术问题同样适用。
下述本公开实施例可以应用于图1所示的通信系统100、或部分主体，但不限于此。图1所示的各主体是例示，通信系统可以包括图1中的全部或部分主体，也可以包括图1以外的其他主体，各主体数量和形态为任意，各主体之间的连接关系是例示，各主体之间可以不连接也可以连接，其连接可以是任意方式，可以是直接连接也可以是间接连接，可以是有线连接也可以是无线连接。
本公开实施例各实施例可以应用于长期演进(Long Term Evolution，LTE)、LTE-Advanced(LTE-A)、LTE-Beyond(LTE-B)、SUPER 3G、IMT-Advanced、第四代移动通信系统(4th generation mobile communication system，4G)、)、第五代移动通信系统(5th generation mobile communication system，5G)、5G新空口(new radio，NR)、未来无线接入(Future Radio Access，FRA)、新无线接入技术(New-Radio Access Technology，RAT)、新无线(New Radio，NR)、新无线接入(New radio access，NX)、未 来一代无线接入(Future generation radio access，FX)、Global System for Mobile communications(GSM(注册商标))、CDMA2000、超移动宽带(Ultra Mobile Broadband，UMB)、IEEE 802.11(Wi-Fi(注册商标))、IEEE 802.16(WiMAX(注册商标))、IEEE 802.20、超宽带(Ultra-WideBand，UWB)、蓝牙(Bluetooth(注册商标))、陆上公用移动通信网(Public Land Mobile Network，PLMN)网络、设备到设备(Device-to-Device，D2D)系统、机器到机器(Machine to Machine，M2M)系统、物联网(Internet of Things，IoT)系统、车联网(Vehicle-to-Everything，V2X)、利用其他通信方法的系统、基于它们而扩展的下一代系统等。此外，也可以将多个系统组合(例如，LTE或者LTE-A与5G的组合等)应用。
本申请实施例中提供了一种确定通感探测结果的方法，应用于网络设备，如图2a所示，该方法包括：
S201、确定至少一个运行周期中上行阶段的上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号。
在一些实施例中，运行周期的数量为雷达处理估计符号数Nf。
本公开实施例的每个运行周期进一步分为了上行阶段和下行阶段，在上行阶段，终端向网络设备发送包含训练序列或者导频的上行信号，在下行阶段，网络设备向终端发送下行的通信雷达一体化信号(也称之为一体化信号)并接收一体化信号经终端反射的回波信号。
在一些实施例中，每个运行周期内的上行阶段和下行阶段的时长一致。
在一些实施例中，OFDM的子载波总数为N，基础符号周期为T、循环前缀周期为TCP，符号周期分别为Tsym，且Tsym＝T+TCP，循环前缀长度NCP＝NTCP/T，子载波间距为Δf＝1/T。
请参见图2b，其示例性地示出了本公开实施例提供的运行周期的示意图，如图所示，本公开实施例的上行阶段和下行阶段的持续时间都为Tsym，在上行阶段，终端向网络设备发送包含训练序列或导频的上行信号， 网络设备进行上行信道估计与通信接收，在下行阶段，网络设备向终端发送一体化信号、接收回波信号并进行雷达处理。
在一个实施例中，终端发送的上行信号为包含导频或训练的OFDM符号，从而，网络设备通过已有的信道估计方式进行上行信道估计。
在一些实施例中，网络设备获得的上行信道估计结果为相应上行阶段的单程传播的信道时域响应。
在一个实施例中，单程的传播信道为莱斯信道(Rician信道)。
应当理解的是，单程传播是指从信号从第一通信设备传播至第二通信设备，而双程传播是指信号从第一通信设备传播至第二通信设备，再返回第一通信设备，可以理解的是，当第一通信设备指终端时，第二通信设备指网络设备，当第一通信设备指网络设备时，第二通信设备指终端。相应地，上行阶段的单程传播，是指由信号由终端向网络设备传播。
需要注意的是，为了方便推导和理解，本公开实施例对上行信道进行了理想估计。
本公开实施例的网络设备在每个下行阶段向终端发送下行的一体化信号并接收回波信号。
请参见图2c，其示例性地本公开实施例提供的通过网络设备的发送端(Tx)发送一体化信号、接收回波信号并进行雷达处理的流程示意图，如图所示，对于第μ个运行周期，包括：
将二进制数据通过正交幅度调制(Quadrature Amplitude Modulation，QAM)或者相位幅度调制(phase amplitude modulation，PAM)为通感频域符号(也称之为RadCom频域符号)可以理解的是，Xμ[k]为发送的第μ个运行周期的第k个子载波的通感频域符号；
将通感频域符号经过串并转换(serial/parallel conversion，S/P)，得到第一通感频域符号矢量(也即通感频域发送信号)Xμ＝[Xμ[0],Xμ[1],…,Xμ[N-1]]T，其中，上标T表示转置预算；
一路通感频域发送信号被用于通感探测结果的获得，另一路通感频域发送信号则经过离散傅里叶逆变换IDFT(Inverse Discrete Fourier  Transform)映射到时域，可以理解的是，对应的通感时域符号矢量为x＝IDFT(X)，公式中IDFT即标识IDFT运算；
通感时域符号矢量的第μ个通感时域发射信号(也成为第μ个下行OFDM符号的时域采样)表示为：
其中，Nf为运行周期数。
对通感时域发射信号通过调制所得信号作为一体化信号发送至信道中，即完成发送下行的一体化信号的流程。
在一些实施例中，调制包括对通感时域发射信号进行并串转换(P/S)后，添加循环前缀CP，并进行数模转化(D/A)等等。
网络设备在向终端发送一体化信号后，进一步对经过信道作用的到达信号(即该一体化信号经终端发射的回波信号)进行接收；
接收的回波信号通过解调得到第二通感频域符号矢量(也即通感频域接收信号)Yμ[k]表示为接收的第μ个运行周期的第k个子载波的回波频域项；
在一个实施例中，解调包括对回波信号进行模数转换(A/D)后，去除CP，然后通过S/P，由离散傅里叶变换DFT映射到频域。
获得的通感频域接收信号同样被分为两路，一路用于雷达处理，另一路进行信道均衡，以补充信道失真；
在一个实施例中，均衡可以采用最小均分误差(Minimum Mean-Squared Error，MMSE)或迫零(Zero Forcing，ZF)均衡器；
MMSE均衡系数为：
ZF均衡系数为：
其中，表示单程传播的第k个子载波的信道频域响应系数，H*[k]表示对H[k]进行共轭运算，εb和N0分别为信号每比特能量与加性高斯白噪声AWGN(Additive White Gaussian Noise)的功率谱密度；
均衡后的信号可表示为通感频域接收信号与均衡系数相乘的IDFT结果：
S202、根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果。
本公开实施例对于每个运行周期，可以根据接收的该运行周期的上行信号，可以确定该运行周期的上行信道估计结果，当上行阶段和下行阶段在相干时间内时，可以认为上行阶段和下行阶段内的信道信息未发生改变，由于信道的互易性，上行阶段在同一运行周期内相邻的下行阶段中，一体化信号经历了两次近似相同的信道传播，基于此，本公开实施例根据接收的上行信号进行上行信道估计得到的单程的上行信道估计结果，得出回波信号经过两程传播的信道估计结果，从而利用两程的信道估计结果以及一体化信号，对回波信号进行处理，有效消除终端固有的雷达多径干扰。
本公开实施例通过对回波信号的生成逻辑和传输过程进行分析，确定在现有的一体化信号的基础上，进一步结合传播的信道估计对回波信号进行处理，可以有效消除终端固有的雷达多径干扰，为了获得传播的信道估计，本公开实施例将每个运行周期细分为了上、下行两个阶段，通过在上行阶段接收上行信号，对上行信号进行解析，获得每个运行周期的上行信道估计结果。
在上述各实施例的基础上，作为一种可选实施例，根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果，包括：
根据运行周期的上行信道估计结果，确定运行周期的回波信道频域响应；
根据至少一个运行周期的回波信道频域响应、通感频域发射信号和通感频域接收信号，确定所述通感探测结果。
在一些实施例中，通感频域发射信号，是指发送的一体化信号中的OFDM频域符号。
在一些实施例中，通感频域接收信号，是指接收的回波信号中的频域符号。
在一些实施例中，OFDM频域符号，是指OFDM符号的频域采样。
在一些实施例中，回波信道频域响应为回波信号经过两程传播的信道频域响应。
在一些实施例中，信道频域响应，是指信道冲击响应的频域采样，同理，信道时域响应，是指信道冲击响应的时域采样。
由上述图2c可知，本公开实施例在每个运行周期的下行阶段发送一体化信号的过程中，会保留一路通感频域发送信号，同时在接收回波信号的过程，也会保留一路通感频域接收信号，从而具体基于各个运行周期的回波信道频域响应、通感频域发射信号和通感频域接收信号，确定终端在多个运行周期内的通感探测结果。
在上述各实施例的基础上，作为一种可选实施例，上行信道估计结果包括单程传播的信道时域响应。
根据运行周期的上行信道估计结果，确定运行周期的回波信道频域响应，包括：
对运行周期的单程传播的信道时域响应进行DFT操作，获得运行周期的单程传播的信道频域响应；
根据运行周期的单程传播的信道频域响应，确定运行周期的回波信道频域响应。
需要说明的是，本公开的上行信号可以包括训练序列或导频，从而通过现有的信道估计方法，基于训练序列或者导频进行信道估计，确定运行周期的单程传播的信道时域响应其中，hμ[n]表示第μ个运行周期的第n个信道的信道时域响应系数；
值得注意的是，由于网络设备在下行阶段中要对终端进行探测，其信号经历了两程传播，为了保证雷达测距性能，两程传播总时间不能长于OFDM符号的循环前缀持续时间，也即本公开实施例的多径信道长度Nch满足Nch＜Ncp/2，最大传输时延
在获得单程传播的信道时域响应后，由DFT映射到频域，即可得到单程传播的信道频域响应(可表示为)。
由于回波信号进行了两程传播，因此该回波信道频域响应的第k个子载波的信道频域响应系数，可根据该下行阶段的该子载波的两个单程的信道频域响应确定。
在一些实施例中，通过对两个信道时域响应进行线性卷积运算，即可获得该运行周期的回波信道频域响应。
本公开实施例的第μ个运行周期的回波信道频域响应中的第k个子载波的信道频域响应系数Hr,μ[k]可以表示为：
Hr,μ[k]＝DFT{hμ[n]*hμ[n]}＝(Hμ[k])2，k＝0,1，…，N-1
也即，根据运行周期的单程传播的信道时域响应，确定运行周期的回波信道频域响应，包括：
对运行周期的单程传播的信道时域响应进行DFT操作，获得运行周期的单程传播的信道频域响应Hμ[k]；
根据运行周期的单程传播的信道频域响应Hμ[k]，确定运行周期的回波信道频域响应Hr,μ[k]。
在一些实施例中，每个通感频域发射信号包括相应下行阶段的所有子载波的OFDM频域符号。第μ个下行阶段的第k个子载波的OFDM频域符号可表示为Xμ[k]。
在一些实施例中，每个回波信道频域响应包括相应下行阶段的所有子载波的信道频域响应系数。第μ个下行阶段的回波信道频域响应可以表示为Hr,μ，相应地，该回波信道频域响应的第k个子载波的信道频域响应系数可表示为Hr,μ[k]。
在一些实施例中，每个通感频域接收信号包括相应下行阶段的所有子载波的回波频域项Yμ，每个回波频域项包括与相应子载波的OFDM频域符号相关的第一子项、与相应子载波的信道频域响应系数相关的第二子项以及与终端的通感探测结果相关的第三子项。
具体地，当上下行周期在相干时间内时，可认为上下行周期内信道信息未发生改变。由于信道的互易性，相邻的下行阶段中，一体化信号经历了两次近似相同的信道传播，则第μ个下行阶段的第n个子载波的OFDM频域符号对应的通感频域接收信号可表示为：
yμ[n]＝xμ,echo[n]*hμ[n]*hμ[n]+ημ[n]，
n＝0,1,…,N-1；μ＝0,1,…,Nf-1；
其中，ημ[n]表示加性高斯白噪声(White Gaussian Noise，AWGN)，hμ[n]表示第μ个下行阶段的第n个子载波的时域响应系数，*表示线性卷积运算。
xμ,echo[n]表示第μ个下行阶段的第n个子载波的OFDM频域符号的时域采样xμ[n]的反射回波项，可用以下公式表示：
其中，L和fD为探测终端的回波延迟和多普勒频偏；

fD＝2vfc/c；
fc为载波频率，c为光速；
R和v分别为终端与本公开执行主体间的距离与相对速度，属于待求的参数；
PRI为脉冲重复间隔。
在一个实施例中，PRI＝2Tsym。
在上述各实施例的基础上，作为一种可选实施例，根据至少一个运行周期的回波信道频域响应、通感频域发射信号和通感频域接收信号，确定终端在多个运行周期内的通感探测结果，包括：
根据下行阶段的通感频域发射信号中子载波的OFDM频域符号和回波信道频域响应中相应子载波的信道频域响应系数，对相应子载波的回波频域项的第一子项和第二子项进行消除，获得下行阶段的相应子载波的回波频域项的第三子项；
根据至少一个下行阶段的各子载波各自对应的第三子项，确定通感探测结果。
通过将上述xμ,echo[n]的表达式带入回波接收信号的表达式中，同时，结合上述信道频域响应系数Hr,μ[k]的表达式，可获得第μ下行阶段的第k个子载波的回波频域项的表达式Yμ[k]：
由上述表达式可以看出，本公开实施例的每个回波频域项包括3个子项，其中，第一子项为Xμ[k]，第二子项为(Hμ[k])2，第三子项为
进一步分析每个回波频域项的第三子项可知，第三子项包括距离因子和速度因子
可以看出，距离因子与子载波k和终端的回波延迟L相关；
速度因子与运行周期μ和终端的多普勒频偏fD相关。
因此，本公开实施例可以建立一个商矩阵，该商矩阵中的每个元素中的除数一个下行阶段的一个子载波的通感频域发射信号中子载波的OFDM频域符号和回波信道频域响应中子载波的信道频域响应系数的乘积，被除数为该下行阶段的该子载波的回波频域项，从而将回波频域项中 的第一子项和第二子项消除，获得下行阶段的子载波的回波频域项的第三子项；
具体地，本公开实施例按照每个完整的OFDM频域符号为一列的方式排成矩阵形式，即得到如下的矩阵：


为了预防畸变，将MX中的所有为0的元素更新为1，再进行矩阵元素的除法操作，得到商矩阵MD＝MY/(MX·MH)，其中(·)表示矩阵元素级乘法运算，该商矩阵的元素可以表示为：
由于每个运行周期的每个子载波的OFDM频域符号、信道频域响应系数以及回波频域项都是可以确定的，因此，上述商矩阵的元素值也是可以确定的，通过联立商矩阵的所有元素值，即可获得距离信息和相对速度信息。
在上述各实施例的基础上，作为一种可选实施例，根据各下行阶段的各子载波各自对应的第三子项，确定终端的通感探测结果，包括：
对下行阶段的各子载波各自对应的第三子项，进行离散傅里叶逆变换IDFT操作，获得下行阶段的各子载波各自对应的第四子项；
对子载波在各下行阶段各自对应的第四子项进行离散傅里叶变换DFT操作，获得各下行阶段的子载波各自对应的第五子项；
根据至少一个下行阶段的至少一个子载波对应的第五子项，确定通感探测结果。
具体地，本公开实施例可以对上述商矩阵MD的每一列进行N个元素的IDFT操作，从而商矩阵MD中的元素被更新为子载波对应的第四子项，以提取终端的距离信息，再对经过IDFT操作后的矩阵的每一行进行Nf个元素的DFT操作，从而矩阵中的元素进一步更新为子载波对应的第五子项，以提取终端的速度信息，由经过DFT操作得到矩阵的元素的绝对值，即可得到三维雷达显示图像，进而获得通感探测结果。
本公开采用的确定通感探测结果的方法可探测的目标最大距离为rmax＝Tc/2，最大相对速度为vmax＝±c/(8fcTsym)，其中，c与fc分别为光速与载波频率，且此方法的距离分辨率为c/(2NΔf)，速度分辨率为c/(4NffcTsym)。
假设环境中存在距离为20m、相对速度为5m/s的单通信目标用户，其上行信道估计结果采用理想信道估计结果，其仿真参数为：子载波数为1620，累积符号数为560，载波频率为5GHz，子载波间隔为60kHz，CP周期为1.2μs，带宽97.2MHz，最大作用距离为179.9m，最大探测速度为±419.5m/s，距离分辨率为1.54m，速度分辨率为1.5m/s，图3a和图3b分别为相关技术与本公开各自获得的距离-速度雷达图像的示意图，由图3a可看出，经历双程的多径信道后，一体化回波信号在雷达处理之后的距离-速度雷达图像中呈现出多个距离轴上的多径虚假目标峰。而由图3b可知，经过本公开所提的多径干扰消除处理，其雷达图像中的多径虚假目标峰被清除，仅剩所需的通信目标探测峰值，其距离与相对速度准确无误，可以看出，本公开实施例可有效消除雷达图像中的通信目标用户的雷达多径干扰。
本公开实施例提供了一种确定通感探测结果的装置，如图4所示，该装置可以包括：处理模块401，用于确定至少一个运行周期中上行阶段的 上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号；
处理模块401还用于根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果；
其中，一个运行周期包括上行阶段和下行阶段；
通感频域接收信号是对回波信号进行解调确定的，回波信号为装置在下行阶段发送的一体化信号经终端反射的信号；
一体化信号是对通感频域发送信号进行调制确定的。
本公开实施例的装置可执行本公开实施例所提供的方法，其实现原理相类似，本公开各实施例的装置中的各模块所执行的动作是与本公开各实施例的方法中的步骤相对应的，对于装置的各模块的详细功能描述具体可以参见前文中所示的对应方法中的描述，此处不再赘述。
本公开实施例中提供了一种通信设备，包括存储器、处理器及存储在存储器上的计算机程序，该处理器执行上述计算机程序以实现确定通感探测结果的方法的步骤，与相关技术相比可实现：通过对回波信号的生成逻辑和传输过程进行分析，确定在现有的一体化信号的基础上，进一步结合传播的信道估计对回波信号进行处理，可以有效消除终端固有的雷达多径干扰，为了获得传播的信道估计，本公开实施例将每个运行周期细分为了上、下行两个阶段，通过在上行阶段接收上行信号，对上行信号进行解析，获得每个运行周期的信道估计。
在一个可选实施例中提供了一种通信设备，如图5所示，图5所示的通信设备4000包括：处理器4001和存储器4003。其中，处理器4001和存储器4003相连，如通过总线4002相连。可选地，通信设备4000还可以包括收发器4004，收发器4004可以用于该通信设备与其他通信设备之间的数据交互，如数据的发送和/或数据的接收等。需要说明的是，实际应用中收发器4004不限于一个，该通信设备4000的结构并不构成对本公开实施例的限定。
处理器4001可以是CPU(Central Processing Unit，中央处理器)，通用处理器，DSP(Digital Signal Processor，数据信号处理器)，ASIC(Application Specific Integrated Circuit，专用集成电路)，FPGA(Field Programmable Gate Array，现场可编程门阵列)或者其他可编程逻辑器件、晶体管逻辑器件、硬件部件或者其任意组合。其可以实现或执行结合本公开公开内容所描述的各种示例性的逻辑方框，模块和电路。处理器4001也可以是实现计算功能的组合，例如包含一个或多个微处理器组合，DSP和微处理器的组合等。
总线4002可包括一通路，在上述组件之间传送信息。总线4002可以是PCI(Peripheral Component Interconnect，外设部件互连标准)总线或EISA(Extended Industry Standard Architecture，扩展工业标准结构)总线等。总线4002可以分为地址总线、数据总线、控制总线等。为便于表示，图5中仅用一条粗线表示，但并不表示仅有一根总线或一种类型的总线。
存储器4003可以是ROM(Read Only Memory，只读存储器)或可存储静态信息和指令的其他类型的静态存储设备，RAM(Random Access Memory，随机存取存储器)或者可存储信息和指令的其他类型的动态存储设备，也可以是EEPROM(Electrically Erasable Programmable Read Only Memory，电可擦可编程只读存储器)、CD-ROM(Compact Disc Read Only Memory，只读光盘)或其他光盘存储、光碟存储(包括压缩光碟、激光碟、光碟、数字通用光碟、蓝光光碟等)、磁盘存储介质、其他磁存储设备、或者能够用于携带或存储计算机程序并能够由计算机读取的任何其他介质，在此不做限定。
存储器4003用于存储执行本公开实施例的计算机程序，并由处理器4001来控制执行。处理器4001用于执行存储器4003中存储的计算机程序，以实现前述方法实施例所示的步骤。
本公开实施例提供了一种计算机可读存储介质，该计算机可读存储介质上存储有计算机程序，计算机程序被处理器执行时可实现前述方法实施例的步骤及相应内容。
本公开实施例还提供了一种计算机程序产品，包括计算机程序，计算机程序被处理器执行时可实现前述方法实施例的步骤及相应内容。
本公开的说明书和权利要求书及上述附图中的术语“第一”、“第二”、“第三”、“第四”、“1”、“2”等(如果存在)是用于区别类似的对象，而不必用于描述特定的顺序或先后次序。应该理解这样使用的数据在适当情况下可以互换，以便这里描述的本公开的实施例能够以除图示或文字描述以外的顺序实施。
应该理解的是，虽然本公开实施例的流程图中通过箭头指示各个操作步骤，但是这些步骤的实施顺序并不受限于箭头所指示的顺序。除非本文中有明确的说明，否则在本公开实施例的一些实施场景中，各流程图中的实施步骤可以按照需求以其他的顺序执行。此外，各流程图中的部分或全部步骤基于实际的实施场景，可以包括多个子步骤或者多个阶段。这些子步骤或者阶段中的部分或全部可以在同一时刻被执行，这些子步骤或者阶段中的每个子步骤或者阶段也可以分别在不同的时刻被执行。在执行时刻不同的场景下，这些子步骤或者阶段的执行顺序可以根据需求灵活配置，本公开实施例对此不限制。
以上仅是本公开部分实施场景的可选实施方式，应当指出，对于本技术领域的普通技术人员来说，在不脱离本公开的方案技术构思的前提下，采用基于本公开技术思想的其他类似实施手段，同样属于本公开实施例的保护范畴。

Claims (13)

  1. 一种确定通感探测结果方法，所述方法由网络设备执行，其特征在于，包括：
    确定至少一个运行周期中上行阶段的上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号；
    根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果；
    其中，一个运行周期包括上行阶段和下行阶段；
    所述通感频域接收信号是对回波信号进行解调确定的，所述回波信号为所述网络设备在下行阶段发送的一体化信号经终端反射的信号；
    所述一体化信号是对所述通感频域发送信号进行调制确定的。
  2. 根据权利要求1所述的方法，其特征在于，所述根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果，包括：
    根据运行周期的上行信道估计结果，确定所述运行周期的回波信道频域响应，所述回波信道频域响应为所述回波信号经过两程传播的信道频域响应；
    根据至少一个运行周期的回波信道频域响应、通感频域发射信号和通感频域接收信号，确定所述通感探测结果。
  3. 根据权利要求2所述的方法，其特征在于，所述通感频域接收信号包括相应下行阶段的所有子载波的回波频域项；
    所述回波频域项包括：
    与相应子载波的正交频分复用OFDM频域符号相关的第一子项；
    与相应子载波的信道频域响应系数相关的第二子项，以及
    与所述终端的通感探测结果相关的第三子项。
  4. 根据权利要求3所述的方法，其特征在于，所述通感频域发射信号包括相应下行阶段的所有子载波的OFDM频域符号；
    所述回波信道频域响应包括相应下行阶段的所有子载波的信道频域响应系数；
    所述根据至少一个运行周期的回波信道频域响应、通感频域发射信号和通感频域接收信号，确定通感探测结果，包括：
    根据所述下行阶段的通感频域发射信号中子载波的OFDM频域符号和回波信道频域响应中相应子载波的信道频域响应系数，对相应子载波的回波频域项的第一子项和第二子项进行消除，获得所述下行阶段的相应子载波的回波频域项的第三子项；
    根据至少一个下行阶段的各子载波各自对应的第三子项，确定通感探测结果。
  5. 根据权利要求4所述的方法，其特征在于，所述根据各下行阶段的各子载波各自对应的第三子项，确定通感探测结果，包括：
    对下行阶段的各子载波各自对应的第三子项，进行离散傅里叶逆变换IDFT操作，获得所述下行阶段的各子载波各自对应的第四子项；
    对子载波在各下行阶段各自对应的第四子项进行离散傅里叶变换DFT操作，获得各下行阶段的所述子载波各自对应的第五子项；
    根据至少一个下行阶段的至少一个子载波对应的第五子项，确定通感探测结果。
  6. 根据权利要求3-5任意一项所述的方法，其特征在于，所述回波频域项的第三子项包括距离因子和速度因子；
    其中，所述距离因子与子载波和终端的回波延迟相关；
    所述速度因子与运行周期和终端的多普勒频偏相关。
  7. 根据权利要求2所述的方法，其特征在于，所述上行信道估计结果包括单程传播的信道时域响应。
  8. 根据权利要求7所述的方法，其特征在于，所述根据运行周期的上行信道估计结果，确定所述运行周期的回波信道频域响应，包括：
    对所述运行周期的单程传播的信道时域响应进行DFT操作，获得所述运行周期的单程传播的信道频域响应；
    根据所述运行周期的单程传播的信道频域响应，确定所述运行周期的回波信道频域响应。
  9. 根据权利要求8所述的方法，其特征在于，所述信道时域响应包括多径信道长度的信道时域响应系数；所述多径信道长度不超过循环前缀长度的一半。
  10. 根据权利要求1-8任意一项所述的方法，其特征在于，所述上行阶段和下行阶段的持续时间均为符号周期的持续时长。
  11. 一种确定通感探测结果的装置，其特征在于，包括：
    处理模块，用于确定至少一个运行周期中上行阶段的上行信道估计结果以及下行阶段的通感频域发送信号和通感频域接收信号；
    所述处理模块，还用于根据至少一个运行周期的上行信道估计结果、通感频域发送信号和通感频域接收信号，确定通感探测结果；
    其中，一个运行周期包括上行阶段和下行阶段；
    所述通感频域接收信号是对回波信号进行解调确定的，所述回波信号为所述装置在下行阶段发送的一体化信号经终端反射的信号；
    所述一体化信号是对所述通感频域发送信号进行调制确定的。
  12. 一种通信设备，包括存储器、处理器及存储在存储器上的计算机程序，其特征在于，所述处理器执行所述计算机程序以实现权利要求1-10任一项所述方法的步骤。
  13. 一种计算机可读存储介质，其上存储有计算机程序，其特征在于，所述计算机程序被处理器执行时实现权利要求1-10任一项所述方法的步骤。
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