EP0125722A1 - Schaltungsanordnung zur kombinierten adaptativen Entzerrung und Demodulation - Google Patents

Schaltungsanordnung zur kombinierten adaptativen Entzerrung und Demodulation Download PDF

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Publication number
EP0125722A1
EP0125722A1 EP84200647A EP84200647A EP0125722A1 EP 0125722 A1 EP0125722 A1 EP 0125722A1 EP 84200647 A EP84200647 A EP 84200647A EP 84200647 A EP84200647 A EP 84200647A EP 0125722 A1 EP0125722 A1 EP 0125722A1
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EP
European Patent Office
Prior art keywords
channel
branches
output
phase
circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP84200647A
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English (en)
French (fr)
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EP0125722B1 (de
Inventor
Lydie Société Civile S.P.I.D. Desperben
Hikmet Société Civile S.P.I.D. Sari
Said Société Civile S.P.I.D. Moridi
Georges Société Civile S.P.I.D. Bonnerot
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Laboratoires dElectronique Philips SAS
Koninklijke Philips NV
Original Assignee
Laboratoires dElectronique et de Physique Appliquee
Philips Gloeilampenfabrieken NV
Koninklijke Philips Electronics NV
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Publication of EP0125722A1 publication Critical patent/EP0125722A1/de
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Publication of EP0125722B1 publication Critical patent/EP0125722B1/de
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/01—Equalisers

Definitions

  • the present invention relates to an adaptive equalization device for a digital transmission system, and in particular for high speed systems in which the transmission channel is not known in advance and / or is liable to vary over time. It is therefore applicable to digital radio-relay systems, to data transmission over the switched telephone network, to digital transmission over cable (special networks of the Transpac type, etc.).
  • the introduction of adaptive equalizers in high speed digital transmission systems to compensate for channel amplitude and phase distortions has been going on for several years. After their introduction into data transmission systems on the switched telephone network, Adaptive equalizers will soon be used in Digital radio-relay systems.
  • the equalizers used and used in practice generally have one of the following two structures: (a) non-recursive transversal filter, (b) transversal filter having a recursive part whose inputs are the symbols previously decided.
  • the adaptation of the equalizer to the channel and to its possible variations in time is generally done by the method of the stochastic gradient of the mean square error.
  • the two equalizer structures mentioned above and their adaptation have been described in numerous articles including: C. Macchi et al., "Adaptive receivers for high speed data transmission", Annales des Telecommunicationcom., Tome 30, n ° 9-10, Sept.-Oct. 1975.
  • the equalizers are often in baseband, and therefore operate on demodulated signals.
  • systems with high spectral efficiency use modulations of two carriers in quadrature.
  • the equalizer In these systems, to compensate for the intersymbol interference in the phase and quadrature channels and the interference between these two channels, the equalizer must have four branches, each of which consists of a transverse filter; if there is one, the recursive part also has four transversal filters.
  • the carrier recovery loop contains an additional delay which is the propagation time of the signals in the equalizer and which, if the equalizer is very long (which is the case in data transmission over cable), tends to make the carrier recovery loop unstable.
  • the loop will then not be able to follow large frequency deviations (as shown for example by L'articLe by RW Chang and R. Srinivasagopalan, "Carrier recovery for data communication systems with adaptative equalization", published in IEEE Transactions on Communication, volume COM-28, n ° 8, August 1980, pages 1142 to 1153).
  • the same problem is encountered in digital equalizers, even if they do not have many coefficients, since the propagation time is not negligible.
  • IF intermediate frequency equalizers have been introduced (DD Falconer, "Jointly Adaptative Equalization and Carrier Recovery in Two-Dimensional DigitaL Communication Systems", BSTJ, vol. 55, n ° 3, March 1976, pp. 317-334).
  • carrier recovery is robust because there is then the double advantage of using equalized signals and avoiding the delay of the equalizer in servo control of the carrier.
  • Falconer's FI equalizer like Bottom Band EQs, uses the criterion of mean square error to adapt.
  • the object of the invention is therefore to propose an adaptive equalization device operating on the intermediate frequency signal not sampled but having at the same time the function of a demodulator and the output of which is therefore in baseband.
  • the device thus proposed has, in one or the other of the two embodiments, the following advantages: simplicity of a two-channel structure instead of four in the band equalizer base or Falconer's intermediate frequency equalizer, enslavement of the carrier recovery loop by equalized signals, compensation for most of the delay of the equalizer with therefore, for the carrier recovery loop, the possibility to pursue larger frequency deviations without reaching the instability threshold, absence of sampling of signals at intermediate frequency or re-modulation of decisions. More briefly, this device therefore offers the advantages of less sensitivity to sampling errors compared to the intermediate frequency equalizer, better performance (less delay in the loop) compared to the baseband equalizer, and greater simplicity of implementation compared to one and the other.
  • the signal received is of the form: where A (t) and B (t) are low frequency signals before The frequency of the two carriers sin ⁇ o t and cos ⁇ o ⁇ .
  • a (t) and B (t) are low frequency signals before The frequency of the two carriers sin ⁇ o t and cos ⁇ o ⁇ .
  • These signals are linked to the symbols emitted by relations of the type: in which h '(t) and h "(t) are respectively the real and imaginary parts of the complex impulse response of the transmission channel, and in which the terms a k and the terms b k are the symbol trains modulating at the frequency 1 / T
  • the two carriers sin ⁇ o t and cos ⁇ o ⁇ respectively (T period of the symbols).
  • the equalization device has a non-recursive transverse filter structure in which, more precisely, the signal R (t) output from the transmission channel, which constitutes the input signal of the equalization device, is supplied on the one hand to a phase channel 100 and on the other hand to a quadrature channel 200 each comprising a non-recursive transversal filter, with n branches and (n-1) delay circuits 101 1 to 101 n-1 and 2011 to 201 n-1 between the inputs of these branches.
  • the delay provided by these circuits is here equal to T, the intersymbol interval, but could have a lower value, for example T / 2, without the invention being limited thereto.
  • This signal is supplied to a mixer 102, which receives on a different input a sin demodulation signal ( ⁇ o ⁇ + ⁇ + ⁇ m ) supplied by a control channel described later, then to a low-pass filter 103, whose output signal is given by:
  • This signal is in turn supplied to a multiplier 104 delivering a signal: which is sent to one of the n inputs of an adder 105, the output of which is provided the output signal of the transversal filter of the in-phase channel 100 (as this path has n branches, are provided of course n mixers 102 o to 102 n-1 n low-pass filters 103 o to 103 n-1 and n multipliers 104 o to 104 n-1
  • This output signal from the adder 105 and the filter: is then sampled at rate 1 / T in a sampling circuit 106, and The samples thus formed are compared with thresholds in a comparison circuit 107 to decide on the symbols â k sent on the channel in phase 100.
  • the signal at the input of the (m + 1) th branch passes through a mixer 202 and, after demodulation by the signal cos ( ⁇ o ⁇ + ⁇ + ⁇ m ) also supplied by said servo channel, a low-pass filter 203 and a multiplier 204,
  • the output of circuits 203 and 204 therefore being:
  • An adder 205 groups the outputs of the n branches by delivering a signal: which is sampled at the same rate 1 / T in a circuit 206, the samples delivered by this circuit being compared with thresholds in a circuit 207 to decide on the symbols b ⁇ k transmitted on the quadrature channel 200 (the quadrature channel also comprising n branches, the remark made above with regard to the number of circuits applies here identically).
  • the demodulation signal is supplied to each of these channels in phase and in quadrature 100 and 200 by a servo channel 300 which includes a voltage-controlled oscillator 301, 2n phase shifters 310 o to 310 n-1 -and 320 o at 320 n-1 , and a control circuit for this oscillator, these 2n phase shifters and the 2n multipliers 104 o to 104 n-1 and 204 o to 204 n-1 .
  • n phase shifters 310 o to 310 n-1 of the channel in phase 100 are supplied in parallel directly by the oscillator 301 and their output is connected to the second input of the corresponding mixer 102, while the n phase shifters 320 o to 320 n -1 of the quadrature channel 200, also supplied in parallel by the oscillator 301 but after crossing a phase shifter 302 by ⁇ / 2, have their output connected to the second input corresponding mixers 202 o to 202 n-1 ; these phase shifters are here either capacitive circuits, or, more simply, delay circuits that can be controlled.
  • the enslavement of oscillator 301 is obtained by using as criteria The search for the minimum of the mean square error J, given by: the symbol E designating the mathematical expectation and the terms e ' k and e " k being given by: where, t o being The sampling instant, we use the notations:
  • ⁇ n-1 at the n branches of channel 200 are made according to the following two relations (in which m always varies from 0 to n-1), which give the expressions of the signals received respectively by these multipliers and phase shifters (these signals being identical for the branches of the same rank of tracks 100 and 200): where ⁇ and ⁇ are positive constants representing the step of the algorithm and which are sufficiently weak to guarantee the stability of this one.
  • a simplified command of oscillator 301 can be obtained by replacing expression (20) by:
  • This variant embodiment is, concretely, obtained from FIG. 1b by placing, just before the inputs of the two multiplication circuits 351 and 352, 2n multiplication circuits 361, 362 and 2n multiplication circuits 381, 382, zero comparators (not shown here).
  • the servo circuit 350 as described is of the analog type, but a digital variant can be envisaged, which modifies, in FIG. 1b, the parts of the circuit situated at the output of the multipliers 364, 374, 384, 394.
  • the 2n multipliers 104 o to 104 n-1 and 20 o to 204 n-1 are replaced (see Figure 2) by as many series circuits comprising an amplifier 404 and a digitally controlled attenuator 405 whose inputs parallel are connected to the outputs (in equal number) of a down-counter 406 game controlled by a zero comparator 407, this comparator being provided at the output of multipliers 364 and 384.
  • phase shift function provided by the 2n phase shifters 310 o to 310 n-1 and 320 o to 320 n-1 can be assigned to n oscillators 501 o to 501 n-1 with voltage control, directly controlling the mixers 102 o to 102 n-1 of the channel in phase 100 and through phase shifters 502 o to 502 n-1 of ⁇ / 2
  • multipliers 104 chosen in FIG. 1a is not the only possible, these multipliers can be placed at the head of the n branches of the filter instead of preceding the adders 105 and 205.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
  • Filters That Use Time-Delay Elements (AREA)
  • Stereo-Broadcasting Methods (AREA)
  • Transmission Systems Not Characterized By The Medium Used For Transmission (AREA)
EP84200647A 1983-05-11 1984-05-08 Schaltungsanordnung zur kombinierten adaptativen Entzerrung und Demodulation Expired EP0125722B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR8307910 1983-05-11
FR8307910A FR2546008B1 (fr) 1983-05-11 1983-05-11 Circuit d'egalisation adaptative et de demodulation conjointes

Publications (2)

Publication Number Publication Date
EP0125722A1 true EP0125722A1 (de) 1984-11-21
EP0125722B1 EP0125722B1 (de) 1987-01-07

Family

ID=9288812

Family Applications (1)

Application Number Title Priority Date Filing Date
EP84200647A Expired EP0125722B1 (de) 1983-05-11 1984-05-08 Schaltungsanordnung zur kombinierten adaptativen Entzerrung und Demodulation

Country Status (9)

Country Link
US (1) US4594725A (de)
EP (1) EP0125722B1 (de)
JP (1) JPS59211337A (de)
AU (1) AU563907B2 (de)
CA (1) CA1211515A (de)
DE (1) DE3461977D1 (de)
FI (1) FI76655C (de)
FR (1) FR2546008B1 (de)
NO (1) NO163929C (de)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0379375A3 (de) * 1989-01-19 1991-10-30 Nec Corporation Parallel arbeitender adaptiver Transversalentzerrer für digitales Hochgeschwindigkeitsübertragungssystem
GB2282030A (en) * 1993-09-14 1995-03-22 Plessey Semiconductors Ltd Direct conversion receivers
ES2101639A1 (es) * 1994-10-21 1997-07-01 Alcatel Standard Electrica Ecualizador adaptativo.

Families Citing this family (35)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB8406846D0 (en) * 1984-03-16 1984-04-18 British Telecomm Digital filters
GB2181008B (en) * 1985-09-25 1989-09-20 Sony Corp Infinite impulse response filters
US4716577A (en) * 1986-07-07 1987-12-29 Rockwell International Corporation Autoequalizer
FR2627032A1 (fr) * 1988-02-09 1989-08-11 Alcatel Thomson Faisceaux Filtre transverse
US4989170A (en) * 1988-06-09 1991-01-29 National Semiconductor Corporation Hybrid stochastic gradient for convergence of adaptive filter
SE462943B (sv) * 1989-01-26 1990-09-17 Ericsson Telefon Ab L M Saett och anordning foer frekvensstyrning av en koherent radiomottagare
SE462942B (sv) * 1989-01-26 1990-09-17 Ericsson Telefon Ab L M Saett och anordning foer snabb frekvensstyrning av en koherent radiomottagare
FR2644638B1 (de) * 1989-03-14 1991-05-31 Labo Electronique Physique
US4947408A (en) * 1989-05-12 1990-08-07 The United States Of America As Represented By The Administrator Of The National Aeronautics And Space Administration Digital carrier demodulator employing components working beyond normal limits
US5067140A (en) * 1989-08-16 1991-11-19 Titan Linkabit Corporation Conversion of analog signal into i and q digital signals with enhanced image rejection
CN1082301C (zh) * 1994-09-10 2002-04-03 三星电子株式会社 数字无线电收发机
US7245671B1 (en) * 2001-04-27 2007-07-17 The Directv Group, Inc. Preprocessing signal layers in a layered modulation digital signal system to use legacy receivers
US7471735B2 (en) * 2001-04-27 2008-12-30 The Directv Group, Inc. Maximizing power and spectral efficiencies for layered and conventional modulations
US7173981B1 (en) 2001-04-27 2007-02-06 The Directv Group, Inc. Dual layer signal processing in a layered modulation digital signal system
US7423987B2 (en) * 2001-04-27 2008-09-09 The Directv Group, Inc. Feeder link configurations to support layered modulation for digital signals
US8005035B2 (en) * 2001-04-27 2011-08-23 The Directv Group, Inc. Online output multiplexer filter measurement
US7184473B2 (en) * 2001-04-27 2007-02-27 The Directv Group, Inc. Equalizers for layered modulated and other signals
US7209524B2 (en) * 2001-04-27 2007-04-24 The Directv Group, Inc. Layered modulation for digital signals
US7483505B2 (en) * 2001-04-27 2009-01-27 The Directv Group, Inc. Unblind equalizer architecture for digital communication systems
US7184489B2 (en) * 2001-04-27 2007-02-27 The Directv Group, Inc. Optimization technique for layered modulation
US7512189B2 (en) 2001-04-27 2009-03-31 The Directv Group, Inc. Lower complexity layered modulation signal processor
US7639759B2 (en) * 2001-04-27 2009-12-29 The Directv Group, Inc. Carrier to noise ratio estimations from a received signal
US7502430B2 (en) * 2001-04-27 2009-03-10 The Directv Group, Inc. Coherent averaging for measuring traveling wave tube amplifier nonlinearity
US7151807B2 (en) * 2001-04-27 2006-12-19 The Directv Group, Inc. Fast acquisition of timing and carrier frequency from received signal
US7822154B2 (en) * 2001-04-27 2010-10-26 The Directv Group, Inc. Signal, interference and noise power measurement
US7583728B2 (en) * 2002-10-25 2009-09-01 The Directv Group, Inc. Equalizers for layered modulated and other signals
WO2004004193A2 (en) 2002-07-01 2004-01-08 The Directv Group, Inc. Improving hierarchical 8psk performance
ES2604453T3 (es) * 2002-07-03 2017-03-07 The Directv Group, Inc. Método y aparato para modulación en capas
US7463676B2 (en) * 2002-10-25 2008-12-09 The Directv Group, Inc. On-line phase noise measurement for layered modulation
US7230480B2 (en) * 2002-10-25 2007-06-12 The Directv Group, Inc. Estimating the operating point on a non-linear traveling wave tube amplifier
US7529312B2 (en) * 2002-10-25 2009-05-05 The Directv Group, Inc. Layered modulation for terrestrial ATSC applications
US7474710B2 (en) * 2002-10-25 2009-01-06 The Directv Group, Inc. Amplitude and phase matching for layered modulation reception
AU2003282854A1 (en) * 2002-10-25 2004-05-25 The Directv Group, Inc. Method and apparatus for tailoring carrier power requirements according to availability in layered modulation systems
US7502429B2 (en) * 2003-10-10 2009-03-10 The Directv Group, Inc. Equalization for traveling wave tube amplifier nonlinearity measurements
US9148162B2 (en) * 2014-01-15 2015-09-29 Guzik Technical Enterprises Digital down converter with equalization

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FR2167441A1 (de) * 1972-01-10 1973-08-24 Ibm France

Family Cites Families (2)

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FR2216715B1 (de) * 1973-01-31 1976-06-11 Ibm France
US4475211A (en) * 1982-09-13 1984-10-02 Communications Satellite Corporation Digitally controlled transversal equalizer

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2167441A1 (de) * 1972-01-10 1973-08-24 Ibm France

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0379375A3 (de) * 1989-01-19 1991-10-30 Nec Corporation Parallel arbeitender adaptiver Transversalentzerrer für digitales Hochgeschwindigkeitsübertragungssystem
GB2282030A (en) * 1993-09-14 1995-03-22 Plessey Semiconductors Ltd Direct conversion receivers
US5451899A (en) * 1993-09-14 1995-09-19 Plessey Semiconductors Limited Direct conversion FSK receiver using frequency tracking filters
GB2282030B (en) * 1993-09-14 1997-09-24 Plessey Semiconductors Ltd Direct conversion receiver
ES2101639A1 (es) * 1994-10-21 1997-07-01 Alcatel Standard Electrica Ecualizador adaptativo.

Also Published As

Publication number Publication date
FR2546008A1 (fr) 1984-11-16
FI76655C (fi) 1988-11-10
NO841836L (no) 1984-11-12
AU563907B2 (en) 1987-07-23
FI76655B (fi) 1988-07-29
JPH0342735B2 (de) 1991-06-28
FR2546008B1 (fr) 1985-07-12
JPS59211337A (ja) 1984-11-30
EP0125722B1 (de) 1987-01-07
CA1211515A (en) 1986-09-16
DE3461977D1 (en) 1987-02-12
NO163929C (no) 1990-08-08
FI841834A7 (fi) 1984-11-12
AU2787884A (en) 1984-11-15
NO163929B (no) 1990-04-30
FI841834A0 (fi) 1984-05-08
US4594725A (en) 1986-06-10

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