EP1406349A2 - Antenne active de réception large bande avec régulation du niveau de réception - Google Patents

Antenne active de réception large bande avec régulation du niveau de réception Download PDF

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Publication number
EP1406349A2
EP1406349A2 EP03019899A EP03019899A EP1406349A2 EP 1406349 A2 EP1406349 A2 EP 1406349A2 EP 03019899 A EP03019899 A EP 03019899A EP 03019899 A EP03019899 A EP 03019899A EP 1406349 A2 EP1406349 A2 EP 1406349A2
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EP
European Patent Office
Prior art keywords
frequency
active
antenna
input
transmission
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP03019899A
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German (de)
English (en)
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EP1406349B1 (fr
EP1406349A3 (fr
Inventor
Heinz Lindenmeier
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Delphi Delco Electronics Europe GmbH
Original Assignee
Fuba Automotive GmbH and Co KG
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Application filed by Fuba Automotive GmbH and Co KG filed Critical Fuba Automotive GmbH and Co KG
Publication of EP1406349A2 publication Critical patent/EP1406349A2/fr
Publication of EP1406349A3 publication Critical patent/EP1406349A3/fr
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Publication of EP1406349B1 publication Critical patent/EP1406349B1/fr
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/27—Adaptation for use in or on movable bodies
    • H01Q1/32—Adaptation for use in or on road or rail vehicles
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q23/00—Antennas with active circuits or circuit elements integrated within them or attached to them

Definitions

  • the invention relates to an active broadband reception antenna, consisting of a passive antenna part 1 with a frequency-dependent effective length l e , the output connections of which are connected to the input connections of an amplifier circuit 21 at a high frequency.
  • Electrically long antennas or antennas that are in direct coupling with large electrical bodies have a frequency-dependent open circuit voltage when excited with an electrical field strength that is kept constant over frequency, which is expressed by the effective length l e (f).
  • the antenna noise temperature T A in terrestrial surroundings - coming from low frequencies - has dropped to such an extent that a source impedance near the optimum impedance Z opt for the transistor is required for the bipolar transistors on the part of the passive antenna part, in order not to suffer any significant loss of sensitivity due to the transistor noise.
  • the basic form of an active antenna of this type is shown in FIG. 2b and is known, for example, from DT-AS 23 10 616, DT-AS 15 91 300 and AS 1919749.
  • the high electrical field strengths near the transmitter can e.g. also by on-board transmitters, by intermodulation and limitation effects in the electronic amplifiers of the active receiving antenna cause strong reception interference, since this in terms of high sensitivity and in terms of broadband compliance the electrical properties are dimensioned.
  • the technique used is usually very complex, the effort with increasing demands on the intermodulation strength increases rapidly.
  • active receiving antennas that determine a signal level Use rectifier circuit with control circuit, but can use cheaper amplifiers be used because they are able to exceed a predetermined reception level to lower the internal gain of the active receiving antenna to act on it Interference and limiting effects in the amplifier and to avoid in the advanced circuit.
  • DE 43 23 014 describes an active broadband antenna in which the one to be measured Antenna impedance into the optimum using a low-loss transformation network Source impedance of the subsequent electronic amplifier to achieve an optimal signal-to-noise ratio is transformed. To protect the following reception system against Nonlinear effects from level overload is often a reduction in the internal gain the active antenna. In DE 43 23 014 the exceeding of a predetermined one Received level determined using a rectifier circuit and using a Control amplifier, the internal gain of the active antenna is lowered.
  • the basic form of active antennas with a transformation network at the amplifier input is shown in FIG. 2b and is known, for example, from DT-AS 23 10 616 and DT-AS DT-AS 15 91 300.
  • Active antennas according to this state of the art are installed, for example, to a large extent above the high-frequency range with antenna arrangements in a motor vehicle window pane together with a heating field for the window heating, as for example in EP 0 396 033, EP 0 346 591 and in EP 0 269 723 described.
  • the structures of the heating fields used as passive antenna part 1 are vehicle parts which were not originally intended for use as an antenna and which can be changed only slightly due to their function for heating.
  • an active antenna according to the state of the art is implemented on such an antenna element as in FIG. 2b
  • the impedance present at the heating field is to be transformed into the vicinity of the impedance Z opt for noise adaptation with the aid of a primary matching circuit and the frequency response of the active antenna is to be transformed Smoothing using an output-side adaptation network.
  • This procedure necessitates the relatively cumbersome dimensioning of two filter circuits, which for an advantageous overall behavior of the active antenna cannot take place separately for each filter due to the mutual dependence on one another.
  • the amplifier circuit cannot be designed as a simple amplifying element as in FIG. 2b to achieve sufficient linearity properties, as a result of which the creative freedom of the two matching networks is significantly restricted.
  • the design of two filters involves increased effort.
  • an active antenna of this type is the load on the matching circuit connected to the heating field with a downstream amplifier if several active antennas are designed from the same heating field to form an antenna diversity system or a group antenna with special directional properties or other purposes.
  • This disadvantageous situation is present in all antenna arrangements, the passive antenna parts of which are in appreciable electromagnetic radiation coupling to one another.
  • switching diodes are attached to the connection points for the antenna amplifiers formed on the heating field, which in each case only switch on the matching circuit with amplifier whose signal is switched through to the receiver and which the other connection points unlock. In such systems, this leads to a considerable outlay and to the additional requirement of switching the diodes precisely in synchronism with the antenna selection.
  • the object of the invention is therefore an active broadband receiving antenna according to the preamble of claim 1 so that with a given passive antenna part with assurance a high sensitivity to noise and a high linearity largely independent on the frequency dependence of the effective length and the impedance of the passive Freely selectable frequency dependence of the reception power is achieved and that an effective device for lowering the internal gain of the active antenna Given a given reception level to protect against non-linear effects is.
  • the advantages that can be achieved with the invention are in particular the reduction of the economic Effort and simplicity to achieve a signal to noise ratio and optimal reception signal with regard to the risk of nonlinear effects.
  • the high linearity of the three-pole achievable through the features of the main claim reinforcing element 2 allow lowering the internal reinforcement of the active Antenna at the exit of this element in connection with an increase achieved at the same time to design the linearizing negative feedback. Due to the loss of a primary matching network in connection with the high impedance of the amplifier circuit on the input side there is an extremely advantageous freedom in the design of complicated multi-antenna systems, whose passive antenna parts are radially coupled to one another.
  • Fig. 1 an antenna according to the basic form of the invention is shown.
  • the passive antenna part 1 cannot be designed in such a way that it has particular desired properties with regard to its use as an antenna in the meter and decimeter wave range and thus has a shape corresponding to its geometric structure and the metallic border of the window has a random frequency dependence of both the effective length l e and its impedance.
  • the essence of the present invention consists in realizing an active antenna, which allows this randomness of the frequency dependency of the given passive antenna part 1 to be compensated for with the aid of an active antenna which is not complex, easy to determine and easy to implement, and with regard to self-noise, linearity and Freely design frequency response and to achieve a predetermined frequency response between the incident wave with the electric field strength E and the high-frequency received signal 8.
  • the reception voltage present at a connection point 18 is fed to the amplifier circuit 21, which contains at the input a three-pole amplifying element 2, preferably an element with the character of a field effect transistor 2, which is coupled in its source line to the input admittance 7 of a low-loss filter circuit 3, which is terminated at its output with an effective resistance 5.
  • the input admittance 7 can be designed according to the invention, for example, in such a way that the strong frequency dependency, which the received open circuit voltage, expressed by the effective length l e of the passive antenna part 1 designed in this way, is largely compensated for in the high-frequency received signal 8.
  • an adjustable longitudinal element 30 is present in the adjustable transmission element 34, which acts as a through-connection in the area of low reception levels.
  • the longitudinal element 30 is set to be high-resistance in the region of a reception level that is too high, on the one hand it causes the lowering of the high-frequency reception signal 8 and an increase in the impedance, which has negative feedback in the source line of the transistor, or a reduction in the admittance 7 ′ present there.
  • the field effect transistor 2 is thus linearized by the measure and the further circuit is protected against excessive reception levels.
  • FIGS. 2a and 5 The mode of operation and the design principle of an antenna according to the invention are explained using the electrical equivalent circuit diagrams of FIGS. 2a and 5:
  • the suitability of a given passive antenna part 1 for the design of a sufficiently noise-sensitive active antenna can be estimated on the basis of the antenna temperature prevailing in the transmission frequency range.
  • Field effect transistors have i r usually an extremely small parallel noise current source so that their contribution i r * Z A at negligibly small gate-source and gate-drain capacitances C 2 and C 1 and the antenna impedances occurring in practice Z A in comparison to the series noise voltage source u r of the field effect transistor, expressed by its equivalent noise resistance R äF, is always negligibly small.
  • the sufficient sensitivity criterion with negligibly small capacitances C 1 , C 2 is therefore simply the requirement that is easy to test R A > R AEF * T 0 / T A to fulfill.
  • Modern gallium arsenide transistors have negligible capacitances C 1 and C 2 in comparison to the rest of the wiring and a negligible effect of i r with regard to the intended application as the cause of the extremely low noise temperature T N0 when such transistors are adapted to noise.
  • the equivalent noise resistance depends on the quiescent current and can be applied over 30 MHz broadband with 30 ohms and less.
  • an antenna for the FM frequency range and an prevailing antenna temperature of approx. 1000 K with regard to the noise sensitivity for the real part of the complex antenna impedance, which represents the radiation resistance in the case of low-loss field effect transistor 2
  • the criterion according to the invention for the exemplary design of a necessary and frequency-independent reception power within the transmission frequency range is explained for the terrestrial broadcast reception of an active vehicle antenna with regard to the reception power in the downstream reception arrangement with reference to FIG. 5.
  • the largely frequency-independent reception behavior must be demanded in order not to significantly reduce the sensitivity of the overall system due to the noise contribution of the reception system downstream of the active antenna and on the other hand to avoid non-linear effects due to amplification increases as a result of the frequency-dependent reception behavior within a transmission frequency range.
  • G (f) denotes the frequency-dependent real part of the input admittance 7 of the low-loss filter circuit 3. This noise contribution is insignificant then applies against the inevitable received sound of the rushing with T A R A when: G ( f ) ⁇ ( F V -1) ⁇ T 0 4 ⁇ T A , 1 R A ( f )
  • the frequency dependence of the real part G (f) of the input admittance 7 of the low-loss filter circuit 3 is to be selected reciprocally to the frequency response of the real part R A (f) of the complex antenna impedance.
  • G (f) ⁇ 1 / (3 * R A (f)) would therefore have to be selected.
  • the invention is associated with the great advantage that the frequency response for G (f) given from R A (f) can be easily fulfilled because neither the source impedance of the low-loss filter circuit 3 which drives the input side, which is given with 1 / g m of the field effect transistor 2 is, the effective resistance 5 at the output of the low-loss filter circuit 3 still have unavoidable essential reactive components.
  • the frequency-dependent radiator impedance Z s (f) is compulsorily and inseparably present as the source impedance of the primary-side transformation network. Their frequency behavior limits the achievable bandwidth of the impedance transformed into the vicinity of Z opt and thus the bandwidth of the signal-to-noise ratio at the output of the active circuit.
  • the receiving system downstream of the active antenna which is represented in FIG. 5 by the amplifier unit 11, is generally related to the line impedance Z L of the high-frequency line system.
  • connection points 18a and 18b exemplify antenna configurations of possible passive antenna parts 1 of active antennas according to the invention.
  • the impedance profiles Z A (f) shown in the complex impedance plane in FIG. 18c are present as a function of the frequency.
  • the diagram shows convincingly the advantage of an active antenna according to the invention over an active antenna according to FIG.
  • equation (6) can be assigned a maximum tolerable azimuthal mean value l em with a known azimuthal directional factor D am (f), a maximum tolerable active component R Amax .
  • the range of values with R A > R Amax which is not permissible for dimensioning is also hatched in FIGS. 18c and 18d.
  • the radiation resistances R A of the impedance values of particularly favorable structures for use as a passive antenna part 1 are therefore outside the hatched value range with R amin ⁇ R A ⁇ R Amax .
  • a predetermined antenna structure is supplemented by using a low-loss transformer with the transmission ratio ü, as indicated in FIG. 17, which forms the passive antenna part 1 together with the antenna structure, for example a heating field on the window pane.
  • the broadband transmission ratio is advantageously chosen such that the impedance that can be measured at the output of the transmitter is placed with its real part in the value range with R Amin ⁇ R A ⁇ R Amax . It is advantageous to make the primary inductance sufficiently high-resistance.
  • the linearity requirement is determined by a sufficiently large negative feedback, through which in the Source line located input admittance 7 fulfilled.
  • This requires one in the transmission area comparatively low negative feedback, which according to the gain requirement e.g. is dimensioned according to equation (8), but so outside the transmission range is as large as possible.
  • such low-loss filter circuits 3 preferably T-half filter or T-filter or chain circuits such filters used.
  • Such filters are shown in their basic structure in the figures.
  • the individual elements can be used to correspond to a more complicated frequency response of G (f) can be supplemented by additional blind elements.
  • the amplifier unit 11 as the active output stage of the amplifier circuit 21.
  • This can be provided with an output resistance equal to the characteristic impedance Z L of conventional coaxial lines.
  • the effective resistance 5 is formed by the input impedance of the amplifier unit 11.
  • G (f) is to be designed analogously according to the above statements with the aid of a low-loss filter circuit 3 terminated with this impedance.
  • a medium resistance value should be selected, which for intermodulating received signals at frequencies with a large real part of the Antenna impedances too small and at frequencies with a small real part of the antenna impedances is too big. This involves the risk of intermodulating receive signals at frequencies with a large real part of the antenna impedances due to the smaller negative feedback effect there cause excessive intermodulation disturbances and, on the other hand, the remaining Gain at frequencies with a small real part of the antenna impedances is too small and the arrangement is too insensitive at these frequencies.
  • such forms are therefore adjustable Proposed transmission elements 34, which are set at low reception levels Reduce admittances 7 by a suitable factor regardless of frequency.
  • This makes the internal gain of the active antenna frequency-independent by a desired one Reduced factor and the above-mentioned frequency-dependent intermodulation effect does not occur. According to the invention, this is achieved, for example, by a transformer arrangement as in Fig. 4 and in Fig. 6 reached.
  • the frequency-independent gear ratio of the Transformer with the help of divided windings and the switching diodes 36 shown as adjustable electronic elements 32 designed adjustable in stages.
  • the quiescent current in this element is in FIG. 6 provided the quiescent current in this element along with the lowering of the internal gain the active antenna.
  • the adjustable longitudinal element 30 is designed as a frequency-dependent two-pole 47 for frequency-independent lowering of the high-frequency received signals 8. This is achieved with a two-pole admittance 46 similar to the input admittance 7 of the low-loss filter circuit 3, but essentially with a frequency-independent factor t-1 smaller than the input admittance 7 of the transmission network 31 at low reception levels.
  • the transmission network 31 is included 8 as a low-loss filter circuit 3 with fixed blind elements 20 designed.
  • Switchable blind elements 20a are used here, which with the help adjustable electronic elements 32 are switched on and off in such a way that when they fall below a desired reception level the desired frequency dependence of the larger Active conductance G (f) of the input admittance 7 effective at the source connection 24 for higher ones internal gain of the active antenna is given on the one hand.
  • the desired frequency dependency accordingly the reduced conductance G '(f) with the same frequency dependence of the am Source connection 24 effective input admittance 7 'for reduced internal amplification of the active antenna.
  • the passive antenna part 1 is configured with a connection point 18, the two connections of which lie high against the mass.
  • Each of the two connections has a control connection 15a and 15b of a three-pole reinforcing element 2 connected.
  • the source terminals 24a and 24b are connected to the primary side of a transformer 38 designed as an isolating transformer, whose secondary side has different outputs to design different gear ratios t owns.
  • the adjustable transmission element 34 thus becomes the transmitter and the switching diodes 36 are formed.
  • the drain terminals 53a and 53b of the three-pole reinforcing Elements 2a and 2b are connected to ground 0.
  • the three-pole reinforcing element 2 as in Fig. 9a, designed as an expanded three-pole reinforcing element.
  • the extended element from an input field effect transistor 13, from the source of which the bipolar transistor 14 in emitter follower circuit is controlled and through the emitter terminal 12, the source electrode of the extended three-pole reinforcing element 2 is formed, combined.
  • the three-pole reinforcing element is 2 in Fig. 9b as an expanded three-pole amplifying element from an input bipolar transistor 49 and a further bipolar transistor 50 combined in an emitter follower circuit.
  • the emitter connection 12 of the bipolar transistor 50 forms the source terminal 24 of the three-pole amplifying Elements 2.
  • the three-pole reinforcing element 2 is an expanded three-pole reinforcing element Element made from an input bipolar transistor 49 or input field-effect transistor 13, whose collector connection or drain connection with the source or. Emitter connection of a additional transistor 51 is connected and its base or gate connection to the Emitter or source connection of the input bipolar transistor 49 or input field effect transistor 13 is connected. Through this connection, the source connection 24 of the three-pole reinforcing element 2 formed.
  • An expanded three-pin reinforcing element of this Shape is prevented by voltage tracking at the drain or collector connection of the input transistor the disruptive influence of a voltage-dependent capacitance between the control electrode and the drain or collector electrode.
  • the three-pole reinforcing element 2 is designed as an expanded three-pole reinforcing element, in which an electronically controllable quiescent current source I S0 or / and an electronically controllable quiescent voltage source U D0 is present.
  • an electronically controllable quiescent current source I S0 or / and an electronically controllable quiescent voltage source U D0 is present.
  • the quiescent current I S0 and / or the quiescent voltage U D0 in the input bipolar transistor 49 or input field-effect transistor 13 are increased when large reception levels occur in connection with the reduction in the internal gain of the active antenna according to the invention due to the reception level being too high.
  • the base electrodes are to the source electrode of a common input transistor 13 or to the source connection an extended three-pole reinforcing element according to Figures 9a to 9d connected.
  • the bipolar transistors 14, 14 ' are each in the emitter follower circuit with the Input of a low-loss filter circuit 3, 3 'to form separate transmission paths for the relevant frequency bands connected.
  • each of the transmission paths an adjustable transmission element 34, 34 'and a control amplifier 33, 33', each of which only the frequency band assigned to the relevant transmission path via filter measures is supplied from the high-frequency received signal 8.
  • the control signal 42, 42 ' is in each case the assigned adjustable transmission element 34, 34 '.
  • the control signals 42, 42 'by selection means and control amplifiers 33, 33' in Receiver 44 derived from the output signal of the active antenna and the active antenna supplied via control lines 41.
  • the present active antenna is used several times in an antenna system, the passive antenna parts 1 of which have frequency-dependent and with respect to incident waves according to the amount and or only in phase, different directional diagrams of the effective lengths l e , which, however, are electromagnetic Radiation coupling to each other and together form a passive antenna arrangement 27 with a plurality of connection points 18a, b, c.
  • each is connected to an amplifier circuit 21 according to the invention and supplemented to form an active antenna according to the invention. Due to the high impedance of the amplifier inputs, there is no noticeable mutual influence of the received voltages due to the decoupling of the high-frequency received signals 8 at the passive antenna parts 1.
  • Such an antenna arrangement is shown in general in FIG. 13.
  • the received signals 8 present at the output of the amplifier circuit 21 are superimposed weighted in terms of magnitude and phase in an antenna combiner 22 provided for this purpose in order to design a group antenna arrangement with predetermined reception properties with regard to directivity and antenna gain without having an effect on the high-frequency received signals applied to the passive antenna parts 1.
  • a common control amplifier 33 whose control signals 42a, b, c are fed to the transmission networks 31a, b, c in the active antennas for lowering the summed high-frequency received signal 8, can advantageously carry out level monitoring.
  • the level monitoring and attenuation takes place separately in each active antenna with the aid of a control amplifier 33 which is accommodated there in each case.
  • the amplifier circuit 21 When using an antenna according to the invention as an active window antenna it is advantageously possible for the amplifier circuit 21 in the very narrow edge area the vehicle window invisible. Therefore it is desirable to use the one at the junction 18 parts to be miniaturized and only functional there install necessary parts of the amplifier circuit 21.
  • the other parts of the low loss Filter circuit 3 are placed separately and switched on via the high-frequency line 10.
  • the active antenna is designed as a multi-range antenna for several frequency ranges.
  • the basic frequency characteristics of reactive resistors X 1 , X 3 and the reactive conductance B 2 of a T-filter arrangement of the low-loss filter circuit 3 shown in FIG. 19 b are given as examples for the frequency ranges VHF radio broadcasting and VHF and UHF television broadcasting .
  • the T-filter configuration ensures the high-impedance of the low-loss filter circuit 3 on the input side in order to achieve a sufficiently large negative feedback of the field effect transistor 2 in the blocking regions.
  • the low-loss filter circuit 3 is designed as a T-half filter or T-filter or as a chain connection of such filters, the series or parallel branch of which is formed in each case from a combination of reactances in such a way that both the absolute value of a reactance in the series branch 28 and also the absolute value of a reactive conductance in the parallel branch 29 is sufficiently small within a transmission frequency range and sufficiently large outside such and the high-frequency received signal 8 is fed to the control amplifier 33 at the output and the adjustable transmission element 34 is controlled by the control signal 42 thereof.
  • the amplifier circuit 21 is in another advantageous embodiment of the invention in addition to the field effect transistor 2, a further field effect transistor 2 used with the same electrical properties.
  • a balun in the low loss filter circuit 3 is used to resymmetrize the high-frequency received signals 8.
  • Circuit can also advantageously be connected to a connection point 18 with two against ground voltage leading connections can be connected.
  • the efficiency of antenna diversity systems is shaped by the number of available, mutually independent antenna signals. This independence is expressed in the correlation factor between the received voltages occurring in a Rayleigh wave field while driving.
  • a plurality of active reception antennas according to the invention are used in an antenna diversity system for vehicles, the passive antenna parts 1 being selected such that their reception signals E * l e present in idle mode at the connection points 18 in a Rayleigh reception field are as independent as possible.
  • Systems of this type, in which the connection points 18 are selected from this point of view and taking into account vehicle-technical aspects, are shown by way of example in FIGS. 15 and 16. Because of the electromagnetic radiation coupling existing between the connection points 18, this independence then only applies to the connection points 18 operated in idle mode.
  • connection points 18 By connecting the connection points 18 with the amplifier circuits 21 according to the invention, due to their negligibly small capacitive input conductance, the high-frequency received signals 8 are tapped without feedback at the antenna outputs.
  • the diversity-independent independence of the received signals at the connection points 18 is thus advantageously not influenced by this measure, and this independence consequently exists in the same way for the received signals 8 at the antenna outputs.
  • independent reception signals 8 are available at the antenna outputs for selection in a scanning diversity system or for further processing in one of the other known diversity methods.
  • This is the relationship for a passive antenna part 1 with two connection points 18 explained in more detail:
  • the level of the selected signal can be fed to a common control amplifier 33 in the electronic changeover switch 25, in which a control signal 42 is formed and to the transmission networks 31 in the amplifier circuits 21 of the active reception antennas for lowering the selected high-frequency reception signal 8 is supplied.
  • the amplifier circuits 21 of the active antennas can each be assigned a separate control amplifier 33 for monitoring the high-frequency received signal 8 at the relevant antenna output.

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  • Input Circuits Of Receivers And Coupling Of Receivers And Audio Equipment (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
EP03019899A 2002-10-01 2003-09-02 Antenne active de réception large bande avec régulation du niveau de réception Expired - Lifetime EP1406349B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10245813A DE10245813A1 (de) 2002-10-01 2002-10-01 Aktive Breitbandempfangsantenne mit Empfangspegelregelung
DE10245813 2002-10-01

Publications (3)

Publication Number Publication Date
EP1406349A2 true EP1406349A2 (fr) 2004-04-07
EP1406349A3 EP1406349A3 (fr) 2006-03-29
EP1406349B1 EP1406349B1 (fr) 2008-05-28

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US (1) US6888508B2 (fr)
EP (1) EP1406349B1 (fr)
KR (1) KR100596126B1 (fr)
CN (1) CN100440619C (fr)
AT (1) ATE397304T1 (fr)
DE (2) DE10245813A1 (fr)

Cited By (1)

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WO2012123125A1 (fr) 2011-03-15 2012-09-20 Delphi Deutschland Gmbh Antenne de réception multibande pour la réception combinée de signaux satellites et de signaux radiophoniques à émission terrestre

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EP1406349B1 (fr) 2008-05-28
KR100596126B1 (ko) 2006-07-05
CN100440619C (zh) 2008-12-03
US6888508B2 (en) 2005-05-03
DE10245813A1 (de) 2004-04-15
KR20040030365A (ko) 2004-04-09
DE50309908D1 (de) 2008-07-10
EP1406349A3 (fr) 2006-03-29
US20040113854A1 (en) 2004-06-17
CN1505206A (zh) 2004-06-16
ATE397304T1 (de) 2008-06-15

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