EP1417751A1 - Circuit de conversion tension/courant - Google Patents

Circuit de conversion tension/courant

Info

Publication number
EP1417751A1
EP1417751A1 EP02754422A EP02754422A EP1417751A1 EP 1417751 A1 EP1417751 A1 EP 1417751A1 EP 02754422 A EP02754422 A EP 02754422A EP 02754422 A EP02754422 A EP 02754422A EP 1417751 A1 EP1417751 A1 EP 1417751A1
Authority
EP
European Patent Office
Prior art keywords
transistor
output
input
current
signal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
EP02754422A
Other languages
German (de)
English (en)
Inventor
Michael Asam
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Infineon Technologies AG
Original Assignee
Infineon Technologies AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Infineon Technologies AG filed Critical Infineon Technologies AG
Publication of EP1417751A1 publication Critical patent/EP1417751A1/fr
Ceased legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/45—Differential amplifiers
    • H03F3/45071—Differential amplifiers with semiconductor devices only
    • H03F3/45076—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier
    • H03F3/4508—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier using bipolar transistors as the active amplifying circuit
    • H03F3/45098—PI types
    • H03F3/45103—Non-folded cascode stages
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/34—DC amplifiers in which all stages are DC-coupled
    • H03F3/343—DC amplifiers in which all stages are DC-coupled with semiconductor devices only

Definitions

  • the present invention relates to a circuit arrangement for voltage / current conversion.
  • a Gilbert multiplier When such a Gilbert multiplier is operated as a high-frequency mixer, it usually has a linear and a switching input. A differential amplifier is usually connected to the linear input and converts a symmetrical voltage signal into a symmetrical current signal. This current signal is fed to a transistor quartet which is triggered by switching with a local oscillator signal and which carries out the actual multiplication.
  • a negative feedback differential amplifier as specified, for example, in the document Tietze, Schenk: Semiconductor Circuit Technology, 10th edition, 1993, page 73, enables a reduction in the nonlinearity of the voltage / current conversion which occurs due to the strongly nonlinear transmission characteristic of transistors.
  • the negative feedback differential amplifier However, ker requires additional current sources at the emitter connections and, due to the current requirement correlated with the linearity properties, has a relatively high current consumption for good linearity. In addition, additional transistor levels must be inserted between the reference and supply potential, so that only relatively small signal amplitudes can be achieved at low supply voltages.
  • Operational amplifier circuits also offer the possibility of linear conversion of a voltage signal into a current signal due to the high input and low output resistance.
  • this requires a large amount of space. Due to the large number of components required to form an operational amplifier, mismatches occur, so that circuit offsets result.
  • Operational amplifier circuits can still become unstable and have relatively poor noise properties.
  • a transistor in an emitter circuit with current feedback or voltage feedback could be used.
  • the linearity properties are determined by the direct current flow through the resistor, which is required for negative feedback, so that a high current consumption results in such a circuit.
  • the voltage range available for modulation at the transistor output is severely limited in the case of relatively large negative feedback voltages.
  • the object of the present invention is therefore to provide a circuit arrangement for converting a voltage signal into a current signal, which has a low current requirement, is suitable for operation with low supply voltages, has good noise properties and offers good linearity properties.
  • the object is achieved by a circuit arrangement for voltage / current conversion, comprising the features of the present patent claim 1.
  • the output current has a linear dependence on the input voltage in a working range.
  • the transmission characteristic is the relationship between the input voltage, that is to say the base-emitter voltage, and between the output current, that is to say the collector current.
  • the transfer characteristic determines the relationship between drain current and gate-source voltage.
  • the non-linear transmission characteristic of the usually occurs Component distortions.
  • an active component for example a bipolar transistor, a metal oxide semiconductor (MOS) field-effect transistor, a tube, etc.
  • MOS metal oxide semiconductor
  • the non-linear transmission characteristic of the usually occurs Component distortions.
  • a known output current can be used to draw conclusions about the underlying input voltage. Accordingly, by knowing the output current, an associated voltage with the same nonlinear characteristic curve as in the voltage / current conversion can be generated and opposed to the original input voltage and thus the nonlinearities can be compensated for.
  • the principle given creates a strongly linear relationship between output current and input voltage.
  • the predistortion of the input voltage by generating a feedback voltage from the output current in compensating render way replaces a negative feedback for the linearization of the characteristic curve in the present principle.
  • the predistorted voltage accordingly has non-linear components which are just opposite to those of the active circuit, such that an output current which is linear with respect to the input voltage results at the output.
  • the voltage generated from the output current and superimposed on the input voltage is preferably generated by means of a transistor which has the same non-linear characteristic as that transistor which carries out the actual voltage / current conversion.
  • the circuit arrangement according to the present principle enables high linearity to be achieved with at the same time low power consumption.
  • the circuit can be implemented with relatively few components and thus offers the possibility of integration with a small footprint with good matching and thus low offsets.
  • the present principle enables operation at low supply voltages with a high modulation range.
  • a current mirror is provided for feedback of the output current to the input transistor, which current mirror couples the output transistor to the input transistor.
  • the coupling of the current paths in the output and input transistor by means of a current mirror offers precise current transmission with a high degree of freedom from distortion. This ensures that the same current flows through the input and output transistors, but in opposite directions.
  • the input transistor and the output transistor have an opposite conductivity type.
  • one of the two transistors is designed as an NPN transistor and the other of the two transistors as a PNP transistor.
  • the circuit is designed using MOS circuit technology, one of the two transistors is designed as an n-channel transistor and the other of the two transistors is designed as a p-channel transistor.
  • the input and output transistors are of an opposite conductivity type, so that the desired compensating superimposition of the input voltage on the one hand and the voltage derived from the output current on the other results.
  • the circuit arrangement is constructed symmetrically, with two input transistors and two output transistors, with a cross coupling being provided for the feedback of the output transistors to the input transistors.
  • the superimposition of the output signal on the input signal in the opposite manner is possible in a particularly simple manner in the case of an input and output signal carried differentially, ie as a push-pull signal on a symmetrical line, by the cross coupling described.
  • input and output transistors have the same
  • all transistors can be of the same conductivity type, that is to say all transistors can be designed as NPN or PNP transistors.
  • the overlay in opposite as described above, this takes place on the basis of the cross coupling with the respective push-pull signal.
  • the output transistor is in a first
  • a second current path which comprises a decoupling transistor, is provided, the second current path being connected in parallel to the first current path and also being controlled by the superimposed control signal.
  • the second current path couples the output transistor to the signal output of the circuit arrangement.
  • the further current path which preferably has a transistor that has the same electrical properties as the output transistor, a feedback-free coupling of the output signal with good linearity with respect to the input signal is possible while maintaining the good linearity between input voltage and output current.
  • the input transistor is operated in the collector circuit and the output transistor in the emitter circuit.
  • the input transistor accordingly works as an emitter follower, so that the input voltage is provided at its emitter connection at a level increased by the base-emitter voltage and predistorted with the characteristic curve of the input transistor.
  • the base terminal of the output transistor operated in a collector circuit is connected to the emitter terminal of the input transistor, so that the desired linear current arises due to the described superimposition of a superposition signal dependent on the output current.
  • the output transistor has an emitter No more an emitter resistor connected to a reference potential connection.
  • the emitter resistor is used for the actual voltage to current change, so that a current is generated which is used for the desired predistortion to compensate for the nonlinearities of the active transistor.
  • the signal output is connected to an input of a multiplier circuit for supplying a signal to be multiplied.
  • multiplier circuits which are designed as high-frequency mixers, require that at least one of these signals to be multiplied is provided as a current signal in order to control them with two signals to be multiplied at one input of the multiplier.
  • This is usually to be fed to the emitter terminal of the transistor quartet, which forms two cross-coupled differential amplifiers, and for example a useful signal, which is provided by a preceding stage, for example a baseband signal processing chain.
  • Such signals to be transferred between function blocks are usually available as a voltage signal, so that the signal input of the multiplier supplemented with the present circuit arrangement has the advantages which can be achieved with the present circuit.
  • FIG. 1 shows a first exemplary embodiment of a voltage / current conversion based on the present principle
  • FIG. 2 shows a development of the circuit according to FIG. 1 for symmetrical signals
  • FIG. 3 the present principle according to FIG. 1, applied to a differential amplifier
  • FIG. 4 shows a further embodiment of the circuit arrangement based on the principle of FIG. 2, applied to a differential amplifier
  • Figure 5 shows the present circuit arrangement in a development of the embodiment of Figure 2, applied to a mixer circuit and
  • Figure 6 shows the known, non-linear transfer characteristic of a bipolar transistor.
  • Figure 1 shows a circuit arrangement for voltage / current conversion, which is constructed in bipolar circuit technology.
  • An input voltage can be fed to a signal input 1, and an output current can be derived from a signal output 2, which is in a linear relationship to the input voltage.
  • the signal input 1 is connected to the base terminal of an input transistor 3, which is connected as an emitter follower.
  • the transistor 3 is designed as a PNP transistor and its emitter connection is connected to the base connection of an output transistor 4, which is operated in an emitter circuit.
  • the base connection of a coupling transistor 5 is connected to the emitter connection and the base connection of input or output transistor 3, 4, which, like the output transistor 4, is designed as an NPN transistor.
  • Coupling transistor 5, like output transistor 4, is in emitter switching tion operated.
  • the signal output 2 is formed by the collector connection of the coupling transistor 5. Furthermore, a current mirror 6, 7 is provided which couples the collector terminal of the output transistor 4 to the emitter terminal of the input transistor 2 and comprises a PNP transistor 6 connected as a diode with a PNP transistor 7 connected downstream. The current mirror transistors 6, 7 are each connected with their emitter connection to a supply potential connection 8. The emitter connections of output transistor 4 and coupling transistor 5 are each connected via a resistor 9, which have the same resistance values, to a reference potential connection 10, to which the collector connection of input transistor 3 is also connected.
  • the input transistor 1 serves as a level shifter or level shifter and provides the necessary predistortion of the input voltage with its characteristic curve. Apart from the non-linearities of its transmission characteristic, a voltage increased by its base-emitter voltage is available at the emitter output of the input transistor with respect to the input voltage of the transistor.
  • the output transistor 4, which is connected to the emitter output of the input transistor 3, provides at its emitter output the voltage present at its base reduced by its base-emitter voltage. At the emitter terminal of the output transistor 4 there is therefore, apart from distortions, the input voltage present at the signal input 1.
  • the resistor 9 connected to the emitter terminal of the output transistor 4 effects a voltage to current conversion, the current generated in this way being used for the necessary predistortion of the input signal.
  • the transistors 6, 7 forming a current mirror ensure that the same amount of current flows through the input and output transistors 3, 4. This ensures in the input and output transistors 3, 4 that the same, current-related, non-linear fluctuations occur with respect to their base-emitter voltages. Since the base-emitter paths of the transistors 3, 4 are opposite in the signal path of the circuit arrangement between the signal input and output 1, 2, these nonlinearities cancel each other out.
  • the collector current of transistor 4, that is to say of the output transistor, is therefore linearly dependent on the input voltage present at signal input 1.
  • the output transistor 4 including the emitter resistor 9 is provided in copy, namely as a coupling transistor 5, to the emitter connection of which an emitter resistor 9 of the same size as that of the output transistor 4 is also connected.
  • the base connections of output transistor 4 and coupling transistor 5 are directly connected to one another, so that the same collector current flows in the collector of transistor 5 as in the collector of transistor 4 due to this and due to the identical resistance values and the same transistor types. Accordingly, the output current, which is provided at the collector terminal of the coupling transistor 5, is linearly dependent on the input voltage.
  • the circuit according to FIG. 1 with the predistortion of the input voltage described makes a negative feedback superfluous and offers a particularly low current requirement with high linearity. Since current sources can be saved with respect to known voltage / current converter circuits or current sources with lower current requirements can be used, the circuit has improved noise behavior. The noise is further reduced by the fact that the predistortion circuit does not attenuate the input signal, as would be the case, for example, when predistortion of a differential amplifier by means of diodes.
  • the predistortion circuit Since the predistortion circuit has a very low output resistance as in FIG. 1, noise currents at the input of the active components, that is to say the transistors, are practically not converted into noise voltages. However, since the useful signal is present as a voltage at the input of the transistors, there is a good signal-to-noise ratio. Since only one transistor and no transistors connected in series are provided at the output of the circuit, there is a large voltage control range at the output, so that the circuit is suitable for low supply voltages with large signal amplitudes.
  • the coupling-out transistor 5 with connected emitter resistor 9 can also be designed to form a transmission ratio not equal to one so that an output current is available at the output 2 which is a multiple of the current flowing through the input and output transistor 3, 4.
  • FIG. 2 shows a development of the circuit according to FIG. 1, in which the signal input and output are designed symmetrically.
  • two input transistors 11, 12 are provided, each of which is connected with its base connection to the symmetrically designed signal input 1, 1 '.
  • the emitter connections of the input transistors 11, 12 are each with an output transistor 13, 14 each connected to its base terminal.
  • Cross-coupling is provided for the feedback of the output current from the output transistor 13, 14 to input transistors 11, 12, such that the collector connection of the output transistor 13 is connected to the emitter connection of the input transistor 12 and the collector connection of the output transistor 14 is connected to the emitter connection of the input transistor 11.
  • the signal output 2, 2 ' is formed on the collector connections of the coupling transistors 15, 16.
  • the coupling transistors 15, 16 are an electrical image of the output transistors 13, 14 and therefore, like these, each have an emitter resistor against a reference potential terminal 10.
  • the collector connections of the input transistors 11, 12 are connected to the supply potential connection 8 on the collector side.
  • the respectively complementary output current of the transistors 13, 14 is used for a suitable predistortion. Accordingly, the same current flows through the transistors 11, 14 and the same current flows through the transistors 12, 13 as well. The base currents are neglected in each case. Consequently, the same base-emitter voltages also form on the respective transistors, namely the base-emitter voltage U ß Ei un ⁇ ä on the transistors 11, 14
  • Transistors 12, 13 each have the base-emitter voltage Ugg2. The result is between signal input 1, 1 'and resistor 9 accordingly on both sides the same total voltage drop U ß El + UßE2 'which is calculated from the sum of the two base-emitter voltages. Therefore, the differential input voltage is also present between the emitter connections of the transistors 13, 14, each reduced by the sum of the base-emitter voltages. The differential current between the emitter nodes of the transistors 13, 14 accordingly results from the quotient of the input differential voltage and twice the resistance value of the resistor 9. The relationship between the output current and the input voltage is therefore linear and independent of non-linear transistor characteristics.
  • the transistors 15, 16 with the emitter resistors 9 are constructed as duplicates of the output resistors 13, 14 with emitter resistors 9, therefore the same current flows at the signal output 2, 2 '.
  • FIG. 3 shows a development of the circuit according to FIG. 1, applied to a differential amplifier, for the additional linearization thereof.
  • a signal input 1 is connected to an input transistor 3, an output transistor 4 and current mirror transistors 6, 7.
  • a coupling transistor 5 is also connected to the output transistor 4, on which the signal output 2 is formed on the collector side.
  • the circuit according to FIG. 3 corresponds in structure and function to that of FIG. 1 and is not explained again in detail.
  • the emitter connection of transistor 5 is connected directly to the emitter connection of transistor 4 and this emitter node is connected to reference potential connection 10 via a direct current source 17.
  • Such a subcircuit is also provided as a mirror image according to FIG.
  • the mirrored components each being identified by a corresponding reference symbol, however, provided with quotation marks.
  • the two mirrored subcircuits are on the emitter side with respect to the output transistors 4, 4 'either directly or, as shown, via an optional negative feedback resistor 18 connected to each other.
  • the negative feedback resistor 18 offers an enlarged modulation range, that is to say the maximum amplitude of the differential voltage signal which can be fed to the signal inputs 1, 1 'is enlarged.
  • the negative feedback resistor 18 is not required for the high linearity.
  • the output signal of the circuit according to FIG. 3 can be tapped at the differential current output 2, 2 'of the decoupling transistors 5, 5'.
  • FIG. 4 also shows the linearization principle described by predistortion of the input signal, applied to a differential amplifier, but with a cross coupling of the symmetrical currents as shown in FIG. 2.
  • the circuit according to FIG. 4 largely corresponds in structure and function to the circuit shown in FIG. 2.
  • the circuit according to FIG. 4 differs from this in that the emitter resistors 9 of the transistors 13 to 16 are omitted. Instead, the emitter connections of the transistors 13, 15 are connected to one another directly and via a current source 17 to the reference potential connection 10. Accordingly, mirror-symmetrically, output transistor 14 and decoupling transistor 16 are also connected directly to one another on the emitter side and to reference potential terminal 10 via current source 17.
  • the emitter connections of the output transistors 13, 14 are connected via a negative feedback resistor 18, which can also be omitted in alternative embodiments. Also in the circuit according to FIG. 4, the negative feedback resistor 18 is required to enlarge the modulation range at the input 1, 1 ', but not to linearize the circuit.
  • the coupling transistors 5, 5 ', 15, 16 and the resistors 9 can either be designed as duplicates of the output transistors, or be scaled as desired to increase or decrease the output current by a constant factor.
  • FIG. 5 finally shows a further development of the circuit according to FIG. 2 with a multiplier core connected to the signal output 2, 2 ′, which represents the electrical equivalent of a multiplication.
  • FIG. 2 The circuit structure of FIG. 2 is found in the circuit in FIG. 5 with the same reference numerals in structure and function and is therefore not repeated here. Only the couplings A and B, which are not shown in the drawing in FIG. 2, are shown in a resolved manner in FIG. 5.
  • the transistors 11, 12, 13, 14, 15, 16 are each formed twice in the circuit according to FIG. 5.
  • the multiplier core comprises two transistor pairs, each of which is connected like a differential amplifier, that is to say coupled to one another in pairs on the emitter side. These emitter nodes of the transistor pairs 19, 20 and 21, 22 are connected to the signal output 2, 2 'of the voltage / current converter circuit.
  • the transistor pairs 19, 20; 21, 22 connected in parallel to form a further signal input, this input connected in parallel being connected to a local oscillator input 23, 24 to which a second signal to be multiplied can be supplied.
  • the first signal to be multiplied can be supplied at voltage input 1, 1 '.
  • the transistor pairs 19, 20; 21, 22 connected to one another in a cross coupling and form the circuit output 25, 26 of the multiplier, at which the multiplied or mixed signal can be tapped.
  • the mixer circuit described offers high linearity with low power consumption and a large modulation range when operating with a low supply voltage.
  • FIG. 6 shows the known transmission characteristic of a bipolar transistor, which indicates the relationship between the input voltage and the output current. According to the diagram shown, the collector current is given as a function of the base-emitter voltage.
  • the transistors in particular the input, output and coupling transistors according to FIGS. 1 to 5, can each have transmission characteristics as shown in FIG. 6, for example.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)

Abstract

L'invention concerne un circuit servant à la conversion d'un signal de tension en un signal de courant, dans lequel un transistor de sortie (4) est commandé par une tension de commande qui est formée par superposition d'une tension d'entrée et d'une tension de rétroaction. La tension de rétroaction est dérivée du courant de sortie du transistor (4) et formée au moyen d'un autre transistor (3) qui présente la même caractéristique non linéaire que celle du transistor (4), ladite tension de rétroaction agissant de façon opposée aux non linéarités du transistor (4). Ainsi, on obtient une linéarité élevée avec de faibles besoins de courant. Ce circuit convient particulièrement aux applications haute fréquence, par exemple pour le câblage d'entrée de mélangeurs haute fréquence, dans la technique des circuits analogiques.
EP02754422A 2001-07-31 2002-07-24 Circuit de conversion tension/courant Ceased EP1417751A1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE10137434 2001-07-31
DE2001137434 DE10137434A1 (de) 2001-07-31 2001-07-31 Schaltungsanordnung zur Spannungs-/Stromwandlung
PCT/DE2002/002711 WO2003015262A1 (fr) 2001-07-31 2002-07-24 Circuit de conversion tension/courant

Publications (1)

Publication Number Publication Date
EP1417751A1 true EP1417751A1 (fr) 2004-05-12

Family

ID=7693821

Family Applications (1)

Application Number Title Priority Date Filing Date
EP02754422A Ceased EP1417751A1 (fr) 2001-07-31 2002-07-24 Circuit de conversion tension/courant

Country Status (3)

Country Link
EP (1) EP1417751A1 (fr)
DE (1) DE10137434A1 (fr)
WO (1) WO2003015262A1 (fr)

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0785616A1 (fr) * 1996-01-22 1997-07-23 Telefonaktiebolaget Lm Ericsson Dispositif équilibré intégré à semi-conducteur, fonctionnant avec un circuit résonnant en parallèle
US6230001B1 (en) * 1999-05-27 2001-05-08 Rockwell Collins, Inc. Active commutated double balanced mixer

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4456887A (en) * 1980-09-25 1984-06-26 Pioneer Electronic Corporation Differential amplifier
JPS592410A (ja) * 1982-06-28 1984-01-09 Sony Corp 電流増幅器
NL8602893A (nl) * 1986-11-14 1988-06-01 Philips Nv Filterschakeling.
US5142242A (en) * 1991-08-07 1992-08-25 Maxim Integrated Products Precision transconductance amplifier
US5491447A (en) * 1994-05-13 1996-02-13 International Business Machines Corporation Operational transconductance amplifier with independent transconductance and common mode feedback control
JP3119215B2 (ja) * 1997-10-14 2000-12-18 日本電気株式会社 差動アンプ

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0785616A1 (fr) * 1996-01-22 1997-07-23 Telefonaktiebolaget Lm Ericsson Dispositif équilibré intégré à semi-conducteur, fonctionnant avec un circuit résonnant en parallèle
US6230001B1 (en) * 1999-05-27 2001-05-08 Rockwell Collins, Inc. Active commutated double balanced mixer

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of WO03015262A1 *

Also Published As

Publication number Publication date
WO2003015262A1 (fr) 2003-02-20
DE10137434A1 (de) 2003-01-23

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