EP1465465A2 - Ballast électronique avec un circuit en pont complet - Google Patents

Ballast électronique avec un circuit en pont complet Download PDF

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Publication number
EP1465465A2
EP1465465A2 EP04013891A EP04013891A EP1465465A2 EP 1465465 A2 EP1465465 A2 EP 1465465A2 EP 04013891 A EP04013891 A EP 04013891A EP 04013891 A EP04013891 A EP 04013891A EP 1465465 A2 EP1465465 A2 EP 1465465A2
Authority
EP
European Patent Office
Prior art keywords
bridge
lamp
brightness
circuit
full
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP04013891A
Other languages
German (de)
English (en)
Other versions
EP1465465A3 (fr
EP1465465B1 (fr
Inventor
Alfred TRÖSTL
Alexander Nachbaur
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Tridonicatco GmbH and Co KG
Original Assignee
Tridonicatco GmbH and Co KG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Tridonicatco GmbH and Co KG filed Critical Tridonicatco GmbH and Co KG
Publication of EP1465465A2 publication Critical patent/EP1465465A2/fr
Publication of EP1465465A3 publication Critical patent/EP1465465A3/fr
Application granted granted Critical
Publication of EP1465465B1 publication Critical patent/EP1465465B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices
    • H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices by means of a bridge converter in the final stage
    • H05B41/2828—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices by means of a bridge converter in the final stage using control circuits for the switching elements
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
    • H05B41/3927—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations by pulse width modulation

Definitions

  • the present invention relates to an electronic ballast with a Full bridge circuit for controlling the operating behavior and the brightness of a Gas discharge lamp or a method for controlling the brightness of a Gas discharge lamp.
  • Electronic ballasts with full bridge circuits are preferably used for Operating high pressure gas discharge lamps used, but also found for Low pressure discharge lamps or fluorescent tubes use.
  • the Using a full bridge circuit the possibility of using the lamps with - if necessary polarity reversed - operate direct current, causing the emergence of disturbing alternating electromagnetic fields can be reduced. Furthermore, in In this case, the influence of the high frequency line impedances Lamp wiring negligible on operation.
  • Ballasts with Full bridge circuits are for example in DE 44 01 630 A1 or AT 392 384 B.
  • the full bridge circuit is formed by four controllable switches S1 to S4, which in the present example are field effect transistors, the first two switches S1 and S2 forming a first half bridge and the two switches S3 and S4 forming a second half bridge.
  • a series resonance circuit consisting of an inductor L and a capacitor C is arranged as the load of the full-bridge circuit in its diagonal branch, ie the series circuit comprising the inductor L and the capacitor C connects the common node between the two switches S1 and S2 of the first half-bridge to the common node between the two switches S3 and S4 of the second half bridge.
  • the gas discharge lamp LA is arranged parallel to the capacitor C.
  • the input of the full bridge circuit is fed with a direct voltage U BUS , the output of the full bridge circuit is connected to ground via a resistor R.
  • the four switches S1 to S4 are controlled by two driver circuits T1 and T2, to which the corresponding control commands for controlling the switches S 1 to S4 are in turn transmitted by a control circuit 6.
  • the four switches S 1 to S4 are usually activated in the following way: first, the switches S1 and S4 forming a first bridge diagonal are activated in a first phase, while the two switches S3 and S2 forming the second bridge diagonal are opened. In this first phase, there is a current flow from the input of the full bridge circuit via the first switch, the load circuit consisting of the series resonance circuit and the gas discharge lamp LA and the switch S4.
  • One of the two switches, for example switch S1 is closed permanently while switch S4 is clocked at high frequency.
  • switches S1 and S4 of the first bridge diagonal are then opened, while switches S3 and S2 of the second bridge diagonal are now activated in an analogous manner, ie switch S3 is permanently closed while switch S2 corresponds to the desired power Duty cycle clocks at high frequency.
  • the change between the two diagonals of the bridge has the consequence that the direction of the current through the lamp LA changes permanently, thereby avoiding mercury deposits on an electrode and increasing the life of the lamp.
  • control circuit 6 which is supplied on the one hand with a desired value I SOLL corresponding to the desired lamp brightness and, on the other hand, with the voltage dropping via the shunt resistor R via the input line 7 as an actual value.
  • control circuit 6 generates control commands which are fed via lines 8 1 to 8 4 to the two driver circuits T1 and T2, which in turn convert the control commands into corresponding signals for controlling the gates of the four field effect transistors S 1 to S4 ,
  • the clocked switch of the active bridge diagonals is at one frequency open and closed from approx. 20 to 50 kHz. Because of this high frequency clocking parasitic currents flow across the lamp line capacitances, which are accurate It is impossible to regulate the lamp brightness, especially with very low dimming values make, with the result that at very low dimming values an undesirable, for Eye noticeable flickering of lamp brightness occurs.
  • the full bridge circuit can supplied current are reduced to very low values, however, since the Constant current source is arranged at the input of the full bridge circuit is the Accuracy in controlling the lamp current itself is limited. Furthermore, at this known variant on the transistor used as a constant current source relatively high leakage currents occur.
  • the task is accomplished through a method of controlling the brightness of a Gas discharge lamp according to claim 1 and by an electronic ballast, which has the features of claim 5, solved.
  • the electronic ballast according to the invention has one with a DC voltage fed full bridge circuit, the gas discharge lamp being part of a Load of the full bridge circuit switched resonance circuit is.
  • a control circuit alternately switches on and off a diagonal of the full bridge circuit the other bridge diagonal.
  • the two Bridge diagonals each have an adjustable constant current source for regulating the Have lamp current.
  • the lamp current is then regulated by the two controllable constant current sources of the bridge diagonals, the In this case, inductance of the load circuit is not effective due to the direct current, but only their ohmic DC resistance.
  • a second operating mode in contrast, when the lamp brightness is high, the control of the lamp supplied is carried out Performance in a known manner by changing the duty cycle at a constant high frequency.
  • the switch-on time of a bridge diagonal to a high-frequency clocking of a switch waived.
  • the lamp turns on during the on time Bridge diagonals are operated with a regulated direct current, which eliminates the problem the parasitic currents due to the high-frequency switching operations is avoided.
  • the low-frequency switching between the two Bridge diagonals are retained and are preferably made with a Frequency of more than 100 Hz, i.e. with a frequency above the perception threshold of the human eye, especially with a frequency between 700 Hz and 2000 Hz.
  • the brightness is controlled by a Gas discharge lamp two operating modes are used, the gas discharge lamp in the first operating mode with low lamp brightness with a regulated DC voltage and in a second operating mode with high lamp brightness a direct current corresponding to the pulse duty factor with superimposed ripple current is operated.
  • the arrangement of the four field effect transistors S1 to S4 of the full bridge shown in FIG. 1 is identical to the known arrangement from FIG. 6. Again, a DC voltage U BUS is applied to the input of the full bridge circuit, the output of the full bridge circuit is formed by a shunt connected to ground. Resistor R. However, only the gas discharge lamp LA is now connected as a load; the elements of a resonance circuit are no longer present in the first exemplary embodiment. Switching between the two diagonals of the bridge again takes place through the two driver circuits T1 and T2, which control the four field effect transistors S1 to S4 in a suitable manner.
  • the lamp brightness is no longer regulated by switching the switches S1 to S4 on and off by the driver circuits T1 and T2, but by controlling the field effect transistors S2 and S4 arranged in the bridge diagonals as controllable constant current sources.
  • these two field effect transistors S2, S4 are each operated by an operational amplifier OP1 or OP2 in their modulation range. They thus form a resistor which is connected in series with the lamp LA and in this way defines an operating point for the lamp LA.
  • the controllable constant current sources are thus formed by the two lower field effect transistors S2 and S4 of the two half bridges and the two operational amplifiers OP1 and OP2, each of which controls the corresponding field effect transistors S2 and S4.
  • Via a feedback line 9 1 or 9 2 the current flowing through the respective field effect transistor S2 or S4 is supplied to the operational amplifier OP1, OP2 as an actual value, the second input signal forms a desired value I SET , corresponding to the desired lamp brightness, which, for example, the two operational amplifiers OP1, OP2 can be supplied by a dimming circuit or the like.
  • the two operational amplifiers OP1 and OP2 act as controllers which set the current flowing through the two field effect transistors S2 and S4 to a value corresponding to the setpoint I SHOULD .
  • the two driver circuits T1 and T2 are used to switch between the both bridge diagonals required control commands in the usual way by a Control circuit (not shown) supplied.
  • a Control circuit (not shown) supplied.
  • the two adjustable constant current sources can be used on a current limiting Inductance can be dispensed with.
  • the voltage drop across them should be relatively low.
  • the ballast also has a control circuit 1, to which the voltage dropping via the field effect transistor S2 or S4 of the respectively active bridge diagonal is supplied as an actual value via the two input lines 10 1 or 10 2 .
  • This actual value is compared with a setpoint I FETsoll , which corresponds to the value that enables a particularly effective current control.
  • the control circuit 1 generates a control signal which is used to control the DC voltage U BUS .
  • Fig. 2 shows the block diagram of a ballast.
  • the input of the ballast is formed by a rectifier circuit 11 connected to an AC voltage source, for example a full-bridge rectifier, which supplies a rectified AC voltage U 0 to a first switching regulator 3.
  • This first switching regulator 3 is formed by a step-up converter, which generates a high intermediate circuit voltage U Z , which is fed to a second switching regulator 4.
  • This second switching regulator 4 is a step-down converter which reduces the high intermediate circuit voltage U Z to the required lower value for the DC voltage U BUS .
  • Reference number 2 denotes the full-bridge circuit shown in FIG. 1.
  • the control circuit 1 controls the buck converter 4, in such a way that it generates a DC voltage U BUS , which, as provided, is only slightly above the lamp voltage LA, so that the via the two transistors S2 or S4 falling voltage corresponds to the setpoint U FETsoll .
  • the control circuit 1 controls the buck converter 4, in such a way that it generates a DC voltage U BUS , which, as provided, is only slightly above the lamp voltage LA, so that the via the two transistors S2 or S4 falling voltage corresponds to the setpoint U FETsoll .
  • U BUS DC voltage
  • the control circuit 1 controls the buck converter 4, in such a way that it generates a DC voltage U BUS , which, as provided, is only slightly above the lamp voltage LA, so that the via the two transistors S2 or S4 falling voltage corresponds to the setpoint U FETsoll .
  • U BUS DC voltage
  • the control circuit 1 controls the buck converter 4, in such a way that it generates a DC voltage U
  • the smoothing circuit for generating the DC voltage U BUS is not generated by two switching regulators connected in series, but by a buck boost converter 5, in which the functions of the switching regulators 3 and 4 shown in FIG. 2 are combined in one circuit.
  • This integration is possible because the requirements for the control speed of the smoothing circuit are relatively low and there is therefore no fear of harmonics occurring at the input of the ballast due to rapid changes in frequency and / or duty cycle.
  • the regulation of the lamp current by the two controllable Constant current sources has in addition to the suppression of flickering Consequence that when switching on the lamp LA at low lamp brightness no Lightning can occur because of the current due to the two adjustable constant current sources is limited to the desired value from the start. Ignition thus takes place the lamp LA at a current that has the lowest possible value for the Has triggered the ignition process.
  • the buck converter 4 or the buck boost converter controlled that it has a maximum output voltage, which is used for the ignition is sufficient.
  • Another option is to use a Ignition coil.
  • the lamp wiring has no influence on the dimming operation Has. This is because switching continues at a low frequency, however, the high-frequency switching of switches is dispensed with and thus this "quasi-direct current" there is no influence of the wiring impedances.
  • the low frequency pole reversal frequency i.e. the change between the two Bridge diagonals should be at least slightly above the frequency from Eye is still perceived, i.e. at least above 100 Hz. Especially a frequency between 700 Hz and 2000 Hz is advantageously selected.
  • FIG. 4 An embodiment of the full bridge circuit according to the invention is shown in FIG. 4. This differs on the one hand in that the gas discharge lamp LA is in turn part of a resonance circuit consisting of an inductor L and a capacitor C, which is connected as a load of the full-bridge circuit, and on the other hand in that the regulator 1 described in FIG. 1 to regulate the DC voltage U BUS is dispensed with.
  • the full-bridge circuit 2 is supplied with a constant DC voltage U BUS , as is shown schematically in FIG. 5.
  • the electronic ballast shown in FIG. 5 now has the rectifier circuit, a step-up converter 3 and the full-bridge circuit 2.
  • the two controllable constant current sources consisting of the operational amplifiers OP1 and OP2 and the associated field-effect transistors S2 and S4 are provided in the full-bridge circuit shown in FIG. 4. Due to the constant DC voltage U BUS in its level, there is now the risk that at high lamp currents, that is to say at high brightness, the power loss resulting from the two transistors S2 and S4 will rise to an impermissible level.
  • the function of the two controllable constant current sources is suppressed and the four transistors S1 to S4 are activated as in the known method shown in FIG. That is, a relatively low frequency is used to switch between the two diagonals of the bridge, one of the two transistors being clocked at high frequency during the on-time of a diagonal of the bridge, so that the lamp is operated with a direct current with a high-frequency ripple current superimposed on it.
  • control with a variable pulse duty factor is necessary; in this operating mode, the inductance L forms the current-limiting impedance in series with the lamp.
  • the control circuit 6 is again responsible for controlling the lamp brightness and transmits the corresponding control commands to the driver circuits T1 and T2 via lines 8 1 to 8 4 , which accordingly control the four transistors S1 to S4.
  • the concept according to the invention is thus characterized in that lamp operation is realized with which dimming over a very wide brightness range is made possible.
  • lamp operation is realized with which dimming over a very wide brightness range is made possible.

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Inverter Devices (AREA)
EP04013891A 2000-10-16 2001-09-11 Ballast électronique avec un circuit en pont complet Expired - Lifetime EP1465465B1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE10051139A DE10051139A1 (de) 2000-10-16 2000-10-16 Elektronisches Vorschaltgerät mit Vollbrückenschaltung
DE10051139 2000-10-16
EP01974243A EP1330945B1 (fr) 2000-10-16 2001-09-11 Ballast electronique avec circuit en pont integral

Related Parent Applications (1)

Application Number Title Priority Date Filing Date
EP01974243A Division EP1330945B1 (fr) 2000-10-16 2001-09-11 Ballast electronique avec circuit en pont integral

Publications (3)

Publication Number Publication Date
EP1465465A2 true EP1465465A2 (fr) 2004-10-06
EP1465465A3 EP1465465A3 (fr) 2004-10-13
EP1465465B1 EP1465465B1 (fr) 2008-12-31

Family

ID=7659903

Family Applications (2)

Application Number Title Priority Date Filing Date
EP01974243A Expired - Lifetime EP1330945B1 (fr) 2000-10-16 2001-09-11 Ballast electronique avec circuit en pont integral
EP04013891A Expired - Lifetime EP1465465B1 (fr) 2000-10-16 2001-09-11 Ballast électronique avec un circuit en pont complet

Family Applications Before (1)

Application Number Title Priority Date Filing Date
EP01974243A Expired - Lifetime EP1330945B1 (fr) 2000-10-16 2001-09-11 Ballast electronique avec circuit en pont integral

Country Status (8)

Country Link
US (1) US6876158B2 (fr)
EP (2) EP1330945B1 (fr)
AT (2) ATE291341T1 (fr)
AU (2) AU2001293807B2 (fr)
BR (1) BR0114678A (fr)
DE (3) DE10051139A1 (fr)
WO (1) WO2002034015A1 (fr)
ZA (1) ZA200302354B (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2223572A1 (fr) * 2007-12-14 2010-09-01 Koninklijke Philips Electronics N.V. Générateur de lumière atténuable

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EP1579743A1 (fr) * 2002-12-20 2005-09-28 Koninklijke Philips Electronics N.V. Mise sous tension a deux etats de lampes hid
DE102004016945A1 (de) * 2004-04-06 2005-10-27 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH EVG mit Regelschaltung und Störgrößenaufschaltung
KR100695525B1 (ko) * 2005-01-31 2007-03-15 주식회사 하이닉스반도체 반도체 기억 소자의 지연 고정 루프
EP1689212B1 (fr) * 2005-02-02 2008-01-23 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Méthode et dispositif pour varier l' intensité lumineuse de sources de lumière
DE102005028672A1 (de) * 2005-06-21 2006-12-28 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Glättungsschaltung zur Verbesserung der EMV
DE102006018569A1 (de) * 2006-04-21 2007-10-25 Tridonicatco Gmbh & Co. Kg Dimmbares elektronisches Vorschaltgerät
US8076871B2 (en) * 2007-04-27 2011-12-13 Koninklijke Philips Electronics N.V. Driver apparatus for a gas discharge lamp
GB2449931B (en) * 2007-06-08 2011-11-16 E2V Tech Power supply for radio frequency heating apparatus
DE102007049397A1 (de) 2007-10-15 2009-04-16 Tridonicatco Gmbh & Co. Kg DC-Versorgung, insbesondere für Leuchtdioden, in einem Betriebsgerät mit Wechselrichter
CN101884252B (zh) * 2007-12-03 2013-05-01 皇家飞利浦电子股份有限公司 驱动气体放电灯的方法
KR20110079905A (ko) 2008-10-23 2011-07-11 오스람 게젤샤프트 미트 베쉬랭크터 하프퉁 고압 방전 램프를 동작시키기 위한 회로 어레인지먼트 및 방법
US9513402B2 (en) 2011-08-23 2016-12-06 Exxonmobil Upstream Research Company Estimating fracture dimensions from microseismic data
US8754583B2 (en) * 2012-01-19 2014-06-17 Technical Consumer Products, Inc. Multi-level adaptive control circuitry for deep phase-cut dimming compact fluorescent lamp

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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2223572A1 (fr) * 2007-12-14 2010-09-01 Koninklijke Philips Electronics N.V. Générateur de lumière atténuable
RU2482639C2 (ru) * 2007-12-14 2013-05-20 Конинклейке Филипс Электроникс Н.В. Регулируемое светогенерирующее устройство

Also Published As

Publication number Publication date
EP1330945A1 (fr) 2003-07-30
US6876158B2 (en) 2005-04-05
AU2001293807B2 (en) 2006-02-16
ZA200302354B (en) 2004-03-26
BR0114678A (pt) 2003-10-07
DE50105645D1 (de) 2005-04-21
EP1465465A3 (fr) 2004-10-13
DE10051139A1 (de) 2002-04-25
DE50114634D1 (de) 2009-02-12
US20040004447A1 (en) 2004-01-08
EP1330945B1 (fr) 2005-03-16
EP1465465B1 (fr) 2008-12-31
AU9380701A (en) 2002-04-29
ATE419735T1 (de) 2009-01-15
WO2002034015A1 (fr) 2002-04-25
ATE291341T1 (de) 2005-04-15

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