JPH01200877A - Output circuit for horizontal high deflecting voltage - Google Patents

Abstract

PURPOSE:To constantly maintain a high voltage value, a flyback pulse and the value of a horizontal deflecting current even when the anode current of an image receiver is changed by adding an operational amplifier for controlling a voltage control circuit and an operational amplifier for controlling a saturable reactor. CONSTITUTION:When a high voltage pulse Vhv is increased to increase a direct current high voltage Ehv, a feed back passing through high divided voltage resistances 12, 13, the operational amplifier 14 and the voltage control circuit 10 operates and a direct current source voltage Eb' is dropped to make the direct current high voltage Ehv constant. The change of a horizontal deflecting amplitude is corrected according to the movement of the direct current source voltage Eb' by a feed back circuit consisting of a deflecting voltage detecting circuit 17, the operational amplifier 18, a constant current generating circuit 20 and the saturable reactor 15.

Description

DETAILED DESCRIPTION OF THE INVENTION (Field of Industrial Application) The present invention relates to improvements in horizontal deflection and high voltage output circuits of picture tubes.

(Prior Art) An example of a conventional horizontal deflection high voltage output circuit of a receiving tube is shown in FIG. Here, 1 is a horizontal deflection output NPN l-run raster, which performs a switching operation in cooperation with a damper diode 2 by an excitation pulse P from a previous stage (not shown). Further, 3 is a retrace resonance capacitor, 4 is a horizontal deflection coil, 5 is a horizontal amplitude adjustment coil, and 6 is an S-shaped correction. 7 is flyback 1-lance, 78
is the primary winding, and the DC power supply (voltage) Eb' of the circuit is applied to one end of the primary winding. Furthermore, 7b is a secondary winding of the flyback transformer 7, 8 connected thereto is a high voltage rectifier circuit, and 9 is a smoothing capacitor. Further, 10 is a voltage control circuit, and 11 is a variable resistor.

In this way, according to the well-known principle, the horizontal deflection sawtooth wave main stream 1y flows through the horizontal deflection coil 4, and since the horizontal deflection coil 4 is attached to the neck of the picture tube (not shown here), The electron beam of the picture tube is deflected left and right.

At the same time, a collector pulse ■p is generated at the collector of the horizontal deflection output transistor 1, which is repeated at the horizontal deflection period, and this is transformed by the flyback 1 to the lance 7 to become a high voltage pulse Vhv. It is rectified and smoothed by a capacitor 9 to obtain a DC high voltage Ehv, which is supplied as an anode voltage to a picture tube (not shown). In this case, the smoothing capacitor 9 can be omitted by utilizing the capacitance between the conductive gaps formed on the wall surface of the picture tube.

Further, 10 is a voltage control circuit whose state can be set by a variable resistor 11, which converts the DC power supply voltage Eb into the DC power supply voltage Eb' of the actual circuit. In this case, by changing the DC power supply voltage Eb' with the variable resistor 11, the pp (peak-to-peak) value of the horizontal deflection sawtooth wave current IV and the value of the output DC high voltage Ehv change simultaneously.

Furthermore, if the inductances of the horizontal deflection coil 4 and the horizontal amplitude adjustment coil 5 are each expressed as La, then the pp value of the horizontal deflection sawtooth wave m1ly flowing here is (L+La)
is inversely proportional to.

Therefore, if the horizontal amplitude adjustment coil 5 is adjusted to change the inductance and the value of a, the horizontal deflection sawtooth wave current IV's p-p (ia) will also change, which will cause the image on the picture tube surface to change. You can adjust the horizontal width of the displayed area (raster).

(Problem to be Solved by the Invention) In FIG. 4, when the peak value VpO of the rectifier pulse Vp is determined using the power supply voltage Eb' of the circuit, the following equation is obtained.

Vpo-(Eb'-Ts)/(2+ a
)...(1) However, here, Ts is the scanning time of horizontal deflection, and C is the capacitance value of the retrace resonant capacitor 3.

As can be seen from equation (1), if, for example, the value of the inductance La is increased in an attempt to change the horizontal amplitude, the peak value Vpo of the recta pulse Vp becomes smaller.

As a result, the high voltage pulse Vhv generated in the secondary winding 7b of the flyback transformer 7 also decreases, and the DC high voltage Ehv for the picture tube anode obtained by rectifying this pulse also decreases.

A decrease in the value of this DC high voltage [hv] for the picture tube anode not only causes deterioration of focus quality but also increases deflection efficiency. The effect of narrowing the amplitude will be weakened.

Therefore, in order to avoid such inconvenience, the variable range of the horizontal amplitude adjustment coil 5 cannot be set so large, and the limit is to move p - p (ii) of the horizontal deflection sawtooth wave current 1y by about 5%. Met.

In addition, when the image receiving screen of the picture tube is bright in FIG. 4, this anode current, that is, the high voltage load current 1a increases. Then,
DC high voltage Eh due to internal impedance IH of the circuit
(2) decreases, which not only causes deterioration in focus quality and fluctuations in image amplitude as described above, but also causes fluctuations in the values of pulses supplied from the flyback transformer 7 to various parts within the device.

For example, as shown in FIG. 4, the timing of the pulse Vp3 obtained from the tertiary winding 7C of the flyback transformer 7 is matched with the reference synchronization signal from the outside and the waveform of the horizontal deflection output circuit (not shown). It may be supplied to the horizontal AFC circuit for In such a case, if the magnitude of the pulse Vp3 changes depending on the magnitude of the high-voltage load current 1a, the phase relationship between the synchronization signal and the horizontal deflection output waveform (for example, the horizontal deflection sawtooth wave current IV) will shift, so the image Depending on the brightness of the image, the position of the image would shift in the horizontal direction, resulting in an extremely unsightly phenomenon.

The phenomenon in which the value of the DC high voltage Ehv fluctuates due to the high voltage load current 1a is tentatively resolved in the following Figure 5.

That is, the numbers 1 to 10 in FIG. 5 function in the same way as the parts with the same numbers in FIG. 4.

Furthermore, 12.13 is a high voltage dividing resistor, 14 is an operational amplifier,
11' is a variable resistor.

In this way, the DC high voltage Eh■ is connected to the high voltage dividing resistor 12,
The voltage control circuit 10 is controlled by the output voltage EO1 of the operational amplifier 14 so that the DC voltage E1 obtained by dividing the voltage by the DC power supply E always matches the reference voltage ES1 obtained by the variable resistor 11' from the DC power supply E. become.

In this way, if the high voltage load current 1a increases and the DC high voltage Ehv decreases, and the value of DC voltage [1 becomes the reference voltage ES
When an attempt is made to interrupt the value of 1, the output voltage of the operational amplifier 14 [
01 is the direction in which the voltage drop of the voltage control circuit 10 is reduced;
In other words, it works in the direction of increasing the DC power supply voltage Eb', so
As a result, the high voltage pulse yhv is added, and the DC high voltage Eh■
Compensation must be made to ensure that this does not decrease.

In this manner, according to FIG. 5, at least fluctuations in the DC high voltage Ehv due to the high voltage load current 1a can be prevented. However, as the high voltage load current 1a increases, the DC power supply voltage Eb'
This increase also means that the horizontal deflection sawtooth current IV also increases, and as a result, the horizontal deflection amplitude changes due to changes in the high-voltage load current 1a.

Therefore, although the circuit shown in Fig. 5 has conventionally been used as a circuit exclusively for high voltage generation, we will attempt to simplify the circuit by sharing the circuit for horizontal deflection and high voltage generation. There were problems in various cases.

Furthermore, in both FIGS. 4 and 5, the variable resistor 11°11'
Even if you try to change only the DC high voltage Ehv by moving the variable resistor 1, the horizontal deflection amplitude will always change at the same time.
1.11' could only be used for the purpose of absorbing variations in the DC power supply voltage Eb.

(Means for Solving the Problems) The present invention has been made to solve the above-mentioned problems, and includes a switching element that is spaced apart at the horizontal deflection period, and a switching element that is connected in parallel with the switching element. a first series circuit of a resonant capacitor, a horizontal deflection coil, a saturable reactor, a current detection circuit, and a figure-eight correction capacitor, also connected in parallel with the switching element; It consists of a DC power supply, a voltage control circuit, and a second series circuit of the primary winding of the flyback transformer, and further includes a DC high voltage obtained by rectifying the pulse voltage generated in the secondary winding of the flyback transformer. In the horizontal deflection high voltage output circuit applied to the anode of the picture tube, the transformer transforms the pulse voltage generated in the saturable reactor, and the pulse voltage obtained by transforming the pulse voltage is applied to the primary winding of the flyback transformer. is inserted in series with the primary winding of the flyback transformer with a polarity such that the voltage per winding is added to the first 2.4 quasi-voltage. A first operational amplifier is provided to compare the voltage 1. with the output of the first operational amplifier. A second operational amplifier is provided to control the llt[] circuit and further compare the output voltage of the current detection circuit with a second reference voltage, and the output of the second operational amplifier controls the saturable reactor t20-. ! By making it so that J
Even if the picture tube anode current changes, the high voltage value, flyback pulse, and horizontal deflection current values remain constant, and by varying the first and second reference voltages, the respective high voltage values can be changed. , the horizontal deflection current value can now be moved independently, and the problems of the prior art have been successfully solved.

(Embodiment) FIG. 1 shows the most basic embodiment of the horizontal deflection high voltage output circuit according to the present invention, and here, the parts numbered 1 to 14 are the same as those in FIG. 5 above. It shall be treated in the same way as the parts with the same number, and the explanation thereof will be omitted.

In FIG. 1 of the present invention, a saturable reactor 15 is inserted in place of the horizontal amplitude adjustment coil 5 in FIGS. 4 and 5 of the conventional example, and the inductance la of the controlled winding 15b of this reactor 15 is The width of the horizontal deflection is adjusted by utilizing the fact that it changes depending on the value of 1 dc of DC current flowing through the horizontal deflection.

Further, 16 is a 1-lance for transforming and inverting the pulse voltage Vpa generated across the controlled winding 15b of the saturable reactor 15 and applying it in series to the primary winding 7a of the flyback transformer 7.

Further, a new deflection current detection circuit 17 is inserted in series with the figure-8 correction capacitor 6, from which a DC voltage Ei directly proportional to p-pl of the horizontal deflection sawtooth wave current 1y is obtained.

This DC voltage Ei is applied to the second performance amplifier 18 and compared with a second reference voltage ES2 obtained from the DC power supply E through the variable resistor 19. Furthermore, the output voltage EO2 of the amplifier 2S18 is applied to the constant current generating circuit 20, so that the DC current 1 dc obtained from the constant current generating circuit 20 flows through the control tm winding 15a of the saturable reactor 15. It's happening.

Here, when calculating the pulse voltage Vpa generated across the controlled winding Ut+winding 15b of the saturable reactor 15 from the peak value Vpo of the collector pulse Vp, the inductance of the horizontal deflection coil 4 can be expressed as the inductance of the L1 controlled winding 15b. As a, it becomes as follows.

Vpa=(La/(L+La))Vpo−(2
3. Therefore, if the value of the inductance La is increased, the pulse voltage value Vpa at both ends will also increase.

This peak value (pulse voltage) Vpa is 0 at the transformer 16.
The primary winding 7a of the flyback transformer 7 is transformed to double the voltage.
added to one end of. At this time, the polarity is opposite to that of the -]rector pulse Vp, and it is applied to the opposite side of the primary winding 7a, so the pulse voltage value Vpl applied to the entire - secondary winding 7a is calculated by the following equation. It becomes the sum of both absolute values.

V 1) 1-V C1o+ n V Da
・(3) However, as mentioned earlier, this (
The first term in equation 3 is the controlled winding 15b of the saturable reactor 15.
The inductance of La decreases as the value of a increases, but the second term increases with the value of the inductance La.

Therefore, the coefficient n of the second term, that is, the turns ratio of the transformer 16 (
If the transformation ratio (transformation ratio) is increased to some extent by Ls, it is possible to make the peak value of the pulse voltage value Vpl increase as the value of the inductance 1-a increases.

When this condition is actually calculated by numerical calculation assuming that the value of the inductance L1 of the primary winding 7a of the flyback transformer 7 is sufficiently larger than the value of the inductance of the horizontal deflection coil 4, the value of n is 0. If it is somewhat larger than 57, the pulse (voltage value) on the flyback lance 7 will naturally increase as the value of inductance a increases.
pl, Vhv, etc. tend to increase.

However, similar to FIG. 5 described above, in FIG. 1 of the present invention, even if the high voltage pulse vhv increases and the voltage value of the DC high voltage Ehv attempts to increase, the high voltage dividing resistors 12, 13, .
Act q amplification 14. Feedback through the voltage control circuit 10 works, and the DC power supply voltage Eb' decreases, resulting in a DC high voltage E.
h■ becomes constant.

Here, the first shift of the horizontal deflection sawtooth wave electric Uly flowing through the horizontal deflection coil 4 is Iy = (Eb' - Ts)/(L+La
) - (4), and as you will soon see, when the DC power supply voltage Eb' decreases as the value of the inductance La increases, the leveling becomes more effective than in the conventional circuit where only the value of the inductance La changes. The value of the deflection sawtooth current 1y decreases. Moreover, in this case, since the DC high voltage Eh■ remains constant in principle, there is no fluctuation in the high voltage due to horizontal deflection width adjustment, which is advantageous.

Although it has been assumed above that the value of the inductance L1 of the primary winding 7a of the flyback transformer 7 is sufficiently larger than the value of the inductance L of the horizontal deflection coil 4, in reality this is often difficult due to the structure.

However, if this is too small, the reactive power handled by the circuit will increase unnecessarily, so it is designed to be at least twice the value of the inductance of the horizontal deflection coil 4, or at least the same value at the worst.

If tl=51, if we similarly find the limit value of the turns ratio n of the transformer 16 using the total q, then n>0.45, and L
l = 2L and n> 0.36, Ll = L and n>
It becomes 0.2G.

From this, if the winding ratio n of the transformer 16 is set above the above limit value according to the value of 11/2, the value of the inductance la of the controlled winding 15b of the saturable reactor 15 can be adjusted. Can effectively change the horizontal amplitude,
Moreover, it does not affect other characteristics.

How much the winding ratio n of the transformer 16 should be made larger than the above-mentioned limit value is determined by the saturable reactor 15 and the pressure control circuit 1.
It is determined by how much of the cost of horizontal amplitude adjustment is to be shared between the horizontal amplitude adjustment and the horizontal amplitude adjustment.

That is, if the winding ratio n is made larger than the limit value, the movement of the DC power supply voltage Eb' during horizontal amplitude adjustment becomes larger.

Therefore, if the voltage control circuit 10 is of the transistor series regulator type, the DC power supply voltage Eb'
It is possible to increase the value of n until the loss in this part falls within the allowable value even at the lower limit of the movement.

On the other hand, of course, in this case as well, as in the case of FIG.
is made constant. In the conventional case of FIG. 5, the problem was that the horizontal deflection amplitude also changed as the DC power supply voltage Eb' moved, but in FIG. This is corrected by a feedback circuit consisting of an operational amplifier 18, a constant current generating circuit 20, and a saturable reactor 15.

In this way, if the value of the horizontal deflection sawtooth wave current Iy increases, the output DC voltage E of the deflection current detection circuit 17
When i is about to exceed the second reference voltage Es2 preset by the variable resistor 19, the output voltage EO2 of the operational amplifier 18 becomes the output DC current 1dc of the constant current generation circuit 20.
It works in the direction of decreasing. Then, this increases the value of the inductance La of the controlled winding II 15b of the saturable reactor 15 and suppresses the horizontal deflection sawtooth wave current 1''/, so that the value of the horizontal deflection sawtooth wave current 1y eventually becomes a constant value. It is maintained.

At this time, as mentioned earlier), the inductance 1-a
The increase in value increases the pulse (voltage Ia) VDl, VhV of the flyback 1-lance 7, which also partially takes charge of the compensation operation for the drop in DC high voltage Ehv due to the increase in the high voltage load current 1a mentioned above. There will be. Then, the range in which the DC power supply voltage Eb' moves is reduced accordingly, and the operation of the voltage control circuit 10 becomes easier.

In this way, for example, even if the high voltage load current 1a fluctuates, the DC current i! 11 Voltage Eb', high voltage pulse Vhv
, DC current 1dc, inductance la, etc. change gradually, but the most important factor is DC high voltage Eh.
v and the horizontal deflection sawtooth current 1y do not change at all, which is the main feature of the present invention.

In addition, when the variable resistor 11' is moved in FIG. 1, the DC high voltage Ehv changes as described above, but the deflection current detection circuit 1
7. Operational amplification 418. Constant current generation circuit 20. Due to the action of the feedback circuit of the saturable reactor 15, the value of the horizontal deflection sawtooth wave current 1y does not change.

On the other hand, when the variable resistor 19 is moved to move the voltage ES2 to the second base, the horizontal deflection sawtooth wave current 1y is At this time, the resistance on the high voltage side is still 12.13
, the first operation increase 1i? It is made constant by the feedback of the voltage control circuit 14, the voltage control circuit 10, and the flyback transformer 7, and is unrelated to the movement of the horizontal deflection sawtooth wave current 1y.

Thus, according to the invention, the variable resistor 11'.

By moving 19, the values of the high voltage and horizontal deflection sawtooth current 1y can be adjusted independently of each other, making it possible to easily adjust the receiver to the correct standard value.

Further, in FIG. 1, a dedicated transformer 16 is used to transform the pulse voltage Vpa generated in the controlled winding 15b, but this can be omitted by modifying the saturable reactor 15.

That is, as shown in FIG. 2, the saturable reactor 15' used here uses an E-E type or E-1 type core 21, with a control winding 15a in the center leg and a control winding 15a in the left and right legs. It is assumed that the controlled winding 15b has a valley. Then, if a new winding 15c is wound along this controlled winding 15b, the controlled winding 15b1. : Generated pulse voltage ff
: Since V pa is transformed into the winding 15c and comes out,
As shown in the figure, connect the flyback 1 to the primary winding 7 of the lance 7.
Just add it to a.

In addition, when the high voltage load current (a) increases in Figure 1, as mentioned above, the DC high voltage Ehv is kept constant due to feedback, but in order to compensate for the original voltage drop, the high voltage pulse yhv is It increases with the current la.

Therefore, when the pulses obtained from other windings on the flyback 1-lance 7, such as Vp3, are supplied to other parts of the device, the pulse voltage also depends on the magnitude of the high-voltage load current 1a. (wave height value) will change, so be careful. As described above, if this pulse Vp3 is used as a comparison signal for the horizontal AFC circuit, a problem is likely to occur in which the horizontal position of the image varies depending on the brightness of the image.

This problem can be solved by using the collector pulse vp on the primary side of the flybar 1-lance 7.

That is, the peak value Vp of the collector pulse ■p in FIG.
o is Vpo=((πTs):/(2Tr)+1)Eb'...
・(It is expressed as →. (TS: Horizontal deflection scanning time, Tr
: horizontal retrace time) On the other hand, the horizontal deflection sawtooth wave current IV is Iy =
(Eb' - Ts)/(L+La), therefore, the DC current 'IQ voltage Eb' is [Eb' =
(L+La)Iy/Ts, so by substituting this DC power supply voltage Eb' into the equation (5) above, the peak value Vp
o is Vpo=((πTs)/(2Tr)+1)(L+La)Iy/Ts...■.

In this equation, as mentioned earlier, the horizontal deflection sawtooth current 1y is constant, and the other horizontal deflection scanning times Ts,
The horizontal retrace time Tr and the inductance are also constant. According to the above-mentioned theory, only the inductance la of the saturable reactor 15 changes slightly with changes in the high-voltage load current 1a, but its contribution is small, and the pulse peak value Vpo remains desirably constant with respect to changes in the high-voltage load current la. Good to see.

Therefore, no problem will arise even if this negative side collector pulse vp is voltage-divided by appropriate means and supplied to other parts of the device, such as the horizontal AFC circuit as described above.

FIG. 3 is a diagram showing an example of a specific circuit of the present invention. Here, it is assumed that numbers 1 to 14 operate in the same manner as the parts with the same numbers in FIGS. 1 and 5. However, the retrace line resonant capacitor 3 is here divided into two parts 3' and 3'', and the collector pulse Vp is divided into pulses Vl)4 at the connection point thereof.As mentioned above, this pulse Vp4 is Since it is hardly affected by the high-voltage load current 1a, it is supplied to other necessary circuit parts in the equipment, such as the horizontal AFC circuit.

The DC high voltage Ehv is divided by the high voltage dividing resistor 12.13 to become the DC voltage E1, which is compared with the first reference voltage ES1 by the operational amplifier 14. Here, 35 is an AC feedback capacitor. The output of the first operational amplifier 14 is applied to the voltage control circuit 10.

In this voltage control circuit 10, 22 is an excitation NPN transistor, 23.211 is its input resistance, and 25 is its collector resistance. Further, 26 is the main control NPN l-
27 is a Q base bias resistor.

Further, 28 is a smoothing capacitor.

In this way, if the DC height 1't E hv is above 51
Then, as the DC voltage E1 tries to exceed the reference voltage ES1, the output voltage EO1 of the operational amplifier 14 rises, causing the base current of the excitation transistor 22, and thus the collector current, to increase. Then, the base bias resistor 27
The current value flowing in this area also increases, and the voltage drop in this part also increases, causing the base voltage of the main control tall +- run raster 2G to decrease, and at the same time, the emitter voltage, that is, the DC power supply voltage Eb'
also decreases. And, since this decrease in DC power supply voltage Eb' leads to a decrease in DC high voltage Ehv, eventually,
The DC voltage E1 does not exceed the reference voltage ES1, the DC high voltage Ehv is stabilized, and each value can be freely set by adjusting the value of the reference voltage ESI.

A current detection circuit 1 connected in series to the horizontal deflection coil 4
7 can be considered a divine method, but here it is drawn using the method using the current detection lance 29.

That is, if the inductance of the primary winding 29a of this current detection transformer 29 is LO, then during the horizontal retrace time 7r,
Pulse voltage generated across this second winding fi129a
p1 is Vpi=-Lo (dIy/dt)-(πI
ypLo /Tr ) sin (πt /Tr
)...(1) [However, since it is during the horizontal retrace time, Iy=Iyp C05(7rt/Tr > 1.

This is the p-p value Iyp of the horizontal deflection sawtooth current IV
Therefore, the pulse V l) i l obtained by applying >7 voltage to the secondary winding 29b is proportional to the rectifier diode 30.
The DC voltage E1' is rectified and smoothed by the smoothing capacitor 31 and is further divided by the resistor 32.33.
It will be proportional to the p value.

Here, if the amplitude of the horizontal deflection sawtooth current 1y increases and the DC voltage E1 attempts to exceed the second reference voltage ES2, the output voltage EO2 of the operational amplifier 18 decreases.

Note that 34 is an AC feedback capacitor. Furthermore, 3G
is the current output NPN +- run raster, and 37 is the emitter resistance at.

Here, when the output voltage EO2 of the operational amplifier 18 decreases, the current output NPN becomes the collector current of the transistor 36, that is, the DC current 1 of the control winding 15a of the saturable reactor 15.
dc also decreases, which increases the value of the inductance la of the controlled winding 15b, which has the effect of decreasing the horizontal deflection sawtooth current 1y.

In the end, the horizontal deflection sawtooth current Iy does not increase and the DC type ffE+ does not exceed the second reference voltage ES2.

Therefore, in this circuit, the value of the horizontal deflection sawtooth current ty is stabilized, and the value can be freely set by adjusting the value of the second reference voltage ES2 with the variable resistor 19.

In addition, in Fig. 3, the values of both the high voltage Eh■ and the deflection current Iy are determined by a circuit that forms negative feedback, so it is affected by variations in the elements in the feedback loop, temperature characteristics, power supply voltage fluctuations, etc. It is extremely stable and difficult to damage.

Furthermore, even if the horizontal deflection frequency changes, the structure of the present invention maintains constant values for both the DC high voltage and the horizontal deflection sawtooth wave current, so it can be used as is, and can be used in computer display equipment and the like.

In this case, in order to accommodate a wide horizontal deflection frequency range, the DC power supply voltage Eb' must be changed significantly, and the voltage 1i1J a! in FIG. 1 circuit 10 4 [Transistor series regulators are difficult to design due to increased loss. In such a case, the 11 voltage regulating circuit 10 is not limited to this circuit, but may be replaced with a switching regulator or the like.

It is true that if the DC power supply voltage Eb' is determined so that the DC high voltage Ehv is constant in accordance with the horizontal deflection frequency, the horizontal deflection sawtooth wave current 1y also becomes a constant value in accordance with the horizontal deflection frequency. JP-A-61-1341 filed by the applicant.
This has already been made clear in issues such as No. 81.

Therefore, even when dealing with such a variety of horizontal deflection frequencies, the stabilizing circuit on the horizontal deflection side, the 1ill saturable reactor 15', the 1IiIi direction current detection circuit 17. Performance amplification 18. Variable low tolerance19. The dynamic range of the constant current generating circuit 20 etc. does not need to be particularly wide.

(Efficacy of the Invention! As is clear from the detailed explanation above, the horizontal deflection high voltage output circuit of the present invention is connected to J3 in the horizontal deflection high voltage output circuit of the picture tube, and when the picture tube anode current changes, the DC Characteristics in which both high voltage and horizontal deflection amplitude do not fluctuate can be achieved with a simple configuration, and a stable circuit that is not affected by fluctuations in ambient temperature or DC power supply can be provided.

Furthermore, the present invention can provide a horizontal deflection high voltage output circuit for a picture tube that can change only the high voltage output voltage without changing the amplitude of the horizontal deflection current.

Further, the present invention provides a horizontal deflection high voltage output circuit of a picture tube with a
Therefore, it is possible to provide a circuit in which only the width of the horizontal dead weight R11i can be changed without changing the high voltage output voltage.

Furthermore, the present invention can provide a circuit that reduces the horizontal change in image position when the high voltage current supplied to the picture tube anode changes in accordance with the brightness of the picture receiving screen.

[Brief explanation of the drawing]

FIG. 1 is a diagram showing the most basic embodiment of the horizontal deflection high voltage output circuit according to the present invention, FIG. 2 is a diagram showing a partial modification of the same, and FIG. FIG. 4 is a diagram showing an example of a conventional circuit, and FIG. 5 is a diagram showing another example of a conventional circuit. 1...Horizontal deflection output NPN l-run raster, 2...
・Damper diode, 3.3', 3"... Return line resonant capacitor, 4... Horizontal deflection coil, 5... Horizontal amplitude adjustment coil, 6...
S-shaped correction condenser, 7... flyback transformer, 7a, 29a...-secondary winding, 7b, 29b... secondary winding, 7C... tertiary winding, 8... high voltage rectifier circuit ,9
, 28.31... Smoothing capacitor, 10... Voltage control circuit, 11, 11', 19... Variable resistor,
12, 13... High voltage dividing resistance, 14.18... Actual Ω
Amplifier, 15, 15'...Saturable reactor, 15a
...controlled relo winding, 15b... controlled! 11 windings, 15
c...Winding, 16...Transformer, 17...Deflection current detection circuit, 2o...Constant current generation circuit, 21...E
-E type or E-1 type core, 22...excitation NPN
Transistor, 23.24... Input resistance, 25...
Collector resistance, 26... Main control 8PNI-run raster, 27... Base bias resistance, 29... Current detection transformer, 30... Rectifier diode, 32.33...
・Resistance, 34.35... AC feedback condenser, 36
...Current output NPN l-run raster, 37...Emitter resistance, Eb, Eb', E...DC power supply (voltage), Fhv...
・DC high voltage for picture tube anode, ESl, ES2...Reference voltage, El, [:i, Ei'...DC voltage, la...High voltage load current, Idc...DC current, Iy... Horizontal deflection sawtooth current, P...excitation pulse, Vhv...high voltage pulse, Vp...
...Collector pulse, ■pa...Pulse voltage, Vpl
...Pulse voltage value, Vl)3. VD4...Pulse. Figure 1 20 Figure 2 Figure 4

Claims (4)

[Claims] (1) A switching element that opens and closes at the horizontal deflection period, a resonant capacitor connected in parallel with the switching element, a horizontal deflection coil, a saturable reactor, a current detection circuit, and an S-shaped element also connected in parallel with the switching element. a first series circuit with a correction capacitor, and a second series circuit with a DC power supply, a voltage control circuit, and a primary winding of a flyback transformer connected in parallel to the switching element; In the horizontal deflection high voltage output circuit which applies DC high voltage obtained by rectifying the pulse voltage generated in the secondary winding of the flyback transformer to the anode of the picture tube, a transformation means for transforming the pulse voltage generated in the saturable reactor is provided. A pulse voltage obtained by transformation by the transformer is inserted in series into the primary winding of the flyback transformer with a polarity such that the voltage per winding is added to the primary winding of the flyback transformer. At the same time, a first operational amplifier is provided which compares a voltage obtained by dividing the DC high voltage with a resistor with a first reference voltage, the output of the first operational amplifier controls the voltage control circuit, and the voltage control circuit is controlled by the output of the first operational amplifier. A horizontal deflection high voltage characterized in that a second operational amplifier is provided for comparing the output voltage of the current detection circuit with a second reference voltage, and the saturable reactor is controlled by the output of the second operational amplifier. Output circuit. (2) The horizontal deflection high voltage output circuit according to claim 1, wherein the first reference voltage is varied to change the DC high voltage output independently of the horizontal deflection current. (3) The horizontal deflection high voltage output circuit according to claim 1, wherein the second reference voltage is varied to change the horizontal deflection amplitude independently of the DC high voltage. (4) A claim characterized in that the pulse obtained by transforming the pulse voltage generated across the switching element by a transformer is used for generating a comparison signal for horizontal AFC within the device. The horizontal deflection high voltage output circuit according to item 1.