JPH06165509A - Inverter device - Google Patents

Abstract

PURPOSE:To adjust power supplied to a load by varying the timing for turning on or off a switching element of the other series circuit for the timing for turning on or off the switching element of one series circuit from the same phase to a phase which is shifted by a specific angle. CONSTITUTION:The timing for turning on or off switching elements S3 and S4 is varied from the same phase to a phase which is shifted by 180 degrees for the timing for turning on or off switching elements S1 and S2. By changing the simultaneous ON period of the switching elements S1 and S4 and S2 and S3 at diagonal positions, power supplied to a load Z is adjusted without changing a switching frequency. By matching the switching periods of the switching elements S1 and S4 and differing the switching periods of S2 and S3 for unbalancing the positive and negative supply power to an oscillation circuit and for supplying DC content to the load Z, vanishing and flicking due to traveling stripes are prevented when the load Z is a discharge lamp.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an inverter device for converting DC power into AC power.

[0002]

2. Description of the Related Art FIG. 26 shows a conventional inverter device having a half-bridge structure used as a discharge lamp lighting device. In this inverter device, the MO is provided at both ends of the DC power source E.
A switching circuit S ₁ and S ₂ composed of SFETs are connected in series, and a load circuit composed of at least a resonance circuit composed of an inductor L ₁ and a capacitor C ₂ and a discharge lamp La serving as a load is connected to a DC cutting capacitor C ₁ . It is connected to both ends of the switching element S ₂ via. Further, the DC cutting capacitor C ₁ is normally the capacitor C
_{Since it} is considerably larger than the capacitance of ₂ , it is not normally included in the resonance circuit, but may be included in the resonance circuit depending on its capacitance.

Under the control of the control circuit 1, the switching elements S ₁ and S ₂ of the inverter device shown in FIG.
As shown in (b), the DC power supply E is turned on and off alternately.
Is converted into an AC voltage (high frequency voltage in this case) and supplied to the discharge lamp La, and the discharge lamp La is lit at high frequency.
This operation will be described in detail below. Now, at time t ₀ , FIG.
As shown in (a), if the control output V ₁ of the control circuit 1 is at high level and the control output V ₂ is at low level as shown in (b), the switching element S ₁ is turned on and The switching element S ₂ is turned off. At this time, from the DC power source E, the switching element S ₁ , the inductor L ₁ , the DC cutting capacitor C ₁ , the capacitor C ₂
A current is supplied to the discharge lamp La through the path of the discharge lamp La.

At this time, the DC cut capacitor C ₁ is charged. Energy is also stored in the resonance circuit. The following description will be made on the case where the operating frequency of the inverter circuit is set to a range higher than the resonant frequency of the resonant circuit. In this case, the energy stored in the inductor L ₁ mainly affects the circuit operation as described below.

Then, time t₁Then, Fig. 27 (a)
As shown in FIG.₁Is low level,
Control output V as shown in FIG.₂Becomes high level
Switching element S₁Turns off and the switch
Holding element S₂Turns on. However, the above switching
Element S₁, S₂So, unlike a pure switch,
And the polarity of the opposite polarity (the polarity of the polarity opposite to that of the DC power supply E).
Pressure) is applied, the switching element S₂Originally
Current I_S2Direction (current direction indicated by arrow in FIG. 26)
The parasitic diode that has the function of sending a current in the opposite direction
Have a Therefore, the switching element S₂Turn on
The current does not turn on in the original direction,
L₂The energy stored in the switching element S₂of
The parasitic diode turns on. In other words, switching element
S₂Becomes conductive in the opposite direction. And indak
L₁By the action of passing an electric current in the same direction as before,
Inductor L₁Energy stored in the
Capacitor C₁, Capacitor C ₂And discharge lamp La, Sui
Touching element S₂Emitted in the path of the parasitic diode of
It That is, the operating frequency of the inverter circuit is the same as that of the resonant circuit.
Since it is set to a range higher than the vibration frequency, the load circuit
Operates as described above.

The inductor L₁The energy of
Switching element S ₂Is originally on
(Current I in the direction indicated by the arrow in FIG._S2Flows
State), DC-cutting capacitor C₁Accumulated in
Capacitor C for direct current cutting₁,I
Inductor L₁, Switching element S₂, Capacitor C ₂
And, in the path of the discharge lamp La, the current flowing in the opposite direction to that
Be done.

Thereafter, at time t ₂ , the control output V ₁ of the control circuit ₁ is at the high level, as in the case of time t ₀ , as shown in FIG.
As shown in (b), since the control output V ₂ becomes low level, the switching element S ₁ is turned on and the switching element S ₂ is turned off. However, also in this case, the switching element S ₁ does not turn on in the direction in which the original current I _S1 flows (the direction shown by the arrow in FIG. 26), and the energy accumulated in the inductor L ₁ causes the switching element S ₁ to switch.
The parasitic diode of turns on. That is, the switching element S ₁ is turned on in the opposite direction. Then, the energy accumulated in the inductor L ₁ is discharged through the path of the parasitic diode of the switching element S ₁ , the DC power source E, the capacitor C _{2, the} discharge lamp La, and the DC cutting capacitor C ₁ .

When the energy of the inductor L ₁ is released, the switching element S ₁ is turned on, and the DC power source E, the switching element S ₁ , and the inductor L are turned on.
₁ , a current flows through the path of the DC cut capacitor C ₁ , the capacitor C ₂ and the discharge lamp La. Hereinafter, by repeating the series of operations described above, the DC power supply E is converted into high frequency power, and the high frequency power is supplied to the discharge lamp La. At this time, the current I _L1 flowing through the inductor L ₁ is as shown in FIG.

In the above description, the time t₀in the case of
And the switching element S₁Does not turn on in the original current direction.
However, until then, the switching element S₁, S₂
Is turned on and off alternately during steady lighting, time t₀
Also in the switching element S ₁Parasitic diode
Inductor L₁Release energy stored in
And then the original switching element S₁Current I_S1But
It goes without saying that it turns on in the flowing direction. Also,
In the above description, the switching element S₁, S₂The parasitic da
Inductor L₁To release the energy of
Used switching element S₁, S₂In reverse parallel to
You may make it connect a diode.

[0010]

When the electric power (that is, the output of the inverter device) supplied to the load in the inverter device is changed, the switching elements S ₁ , S
Change the switching frequency of ₂ . In addition, when the load is the discharge lamp La as described above, the dimming control of the discharge lamp La is performed.

Here, when the switching frequencies of the switching elements S ₁ and S ₂ are set to a range higher than the resonance frequency of the resonance circuit as described above, if the switching frequency is lowered, the switching frequency becomes resonance of the resonance circuit. As the frequency approaches, the electric power supplied to the discharge lamp La increases. On the contrary, if the switching frequency is increased, the switching frequency becomes far from the resonance frequency of the resonance circuit, and the power supplied to the discharge lamp La becomes smaller.

However, when the DC power source E is formed by rectifying and smoothing the AC power source, the switching element S
_When the switching frequency of ₁ and S ₂ is changed, there is a problem that high frequency leaks to the AC power supply side. Therefore, a filter that prevents high-frequency components from leaking to the AC power supply side is provided at the input end of a diode bridge that rectifies the AC power supply. However, when the operating frequency of the inverter device changes as described above, there is a problem that the design of the filter for removing high frequency components becomes complicated.

Further, when the load is the discharge lamp La and the operating frequency of the inverter device is changed, the frequency of the light emitted from the discharge lamp La also changes accordingly, so that the other devices such as an infrared remote controller can operate. There is also the problem of adverse effects. Further, when the discharge lamp La is an HID lamp, there is a high possibility that an acoustic resonance phenomenon will occur due to a change in the output frequency, which causes a reliability-related problem such as destruction of the discharge lamp La. That is, as the operating frequency of the inverter device increases, the possibility that the HID lamp coincides with the frequency that causes the acoustic resonance phenomenon increases.

Therefore, as a conventional example improving this point, "Off-Line Application of Fixed-Frequency Clam" is used.
ped Mode Series Resonant Converter ”, IEEE Tansacti
on on Power Electronics, Vol.6; No. 1, January, 1991. In this conventional example, two series circuits of two switching elements are connected in parallel with a DC power source, and
A load circuit including at least an LC resonance circuit and a load is connected between the connection points of the switching elements of the respective series circuits, and the switching elements of the respective series circuits are alternately turned on and off so as not to be turned on at the same time. The ON / OFF timing of the switching element of the other series circuit is deviated from the ON / OFF timing of the above switching element.

The operation of the above conventional example will be described in detail in the section of the embodiment of the present invention. According to this conventional example, the electric power supplied to the load can be changed without changing the operating frequency. However, there is a problem that the above-mentioned conventional example is applied as a discharge lamp lighting device, and the discharge lamp La is extinguished in a state where the electric power supplied to the discharge lamp La is reduced at a low temperature. Therefore, there is a problem that the dimming range of the discharge lamp La is limited.

The present invention has been made in view of the above points, and it is an object of the present invention to adjust the electric power supplied to a load without changing the switching frequency of the switching element and to supply the electric power. An object of the present invention is to provide an inverter device that can stably operate a load even when it is kept small.

[0017]

According to the invention of claim 1, in order to achieve the above object, two series circuits of two switching elements are connected in parallel with a DC power source, and the switching elements of each series circuit are connected. At least L between the connection points of
A load circuit including a C resonance circuit and a load is connected, and any two of the switching elements have the same switching cycle, and the switching cycles of the other switching elements are made different from the switching cycle to turn on and off. Then, the ON / OFF timing of the switching element of the other series circuit is varied with respect to the ON / OFF timing of the switching element of the one series circuit in a range from the same phase to a phase shifted by 180 degrees.

Further, in order to achieve the above object, in the second aspect of the present invention, two sets of series circuits of two switching elements are connected in parallel with a DC power source, and between the connection points of the switching elements of each series circuit. A load circuit composed of at least an LC resonance circuit and a load is connected to the switching element to turn them on and off with different switching periods of the switching elements. The on / off timings of the switching elements of the series circuit may be varied in the range from the same phase to a phase shifted by 180 degrees.

Incidentally, in order to prevent the fluctuation of the power supplied to the load due to the fluctuation of the power supply voltage, the fluctuation of the power supply voltage is detected and the switching elements of one of the series circuits are turned on and off at the timing. On the other hand, by adjusting the on / off timing of the switching element of the other series circuit,
The power supplied to the load may be controlled to be constant. Also,
In order to supply a constant power to the load, the load current is detected, and the other series circuit is detected with respect to the on / off timing of the switching element of the one series circuit as described in claim 4. The load current may be controlled to be constant by adjusting the on / off timing of the switching element.

Further, when power is supplied to a plurality of loads, a plurality of series circuits composed of the other two switching elements are provided, and the connection points of the switching elements of the one series circuit are connected to each of the series circuits. A plurality of load circuits each including at least an LC resonance circuit and a load can be connected between the connection points of other series circuits. In this case, as described in claim 6, all the switching elements of the other series circuit may not be turned on at the same time.

When the load is a discharge lamp, when the discharge lamp is started, the switching frequency of the switching element is set higher than the resonance frequency of the LC resonance circuit at least when the discharge lamp is defective. Set the switching frequency of the switching element to L when starting the discharge lamp.
The resonance frequency of the C resonance circuit may be approximated.

When the load is a discharge lamp, when the discharge lamp is started, as compared with the resonance frequency of the LC resonance circuit at least when the discharge lamp is defective,
Set the switching frequency of the switching element high,
At the time of starting the discharge lamp, the on / off timing of the switching element of the other series circuit is changed from the on / off timing of the switching element of the other series circuit by 180 degrees to the same phase. Good.

Furthermore, as described in claim 9, it is possible to provide a plurality of loads and separately supply an AC component and a DC component to each load.

[0024]

According to the invention of claim 1, the ON / OFF timing of the switching element of the other series circuit is 180 degrees from the same phase with respect to the ON / OFF timing of the switching element of the one series circuit as described above. By changing the range up to the shifted phase, it is possible to change the simultaneous ON period of the switching elements in the diagonal position and adjust the power supplied to the load without changing the switching frequency. Avoid various problems associated with changing the switching frequency. In addition, positive or negative supply to the LC resonance circuit is achieved by matching any two switching cycles of the switching elements and turning on and off by making the switching cycles of the other switching elements different from the switching cycle. The power is unbalanced, and the energy stored in the LC resonant circuit can be supplied to the load as a DC component, which prevents the lamp from extinguishing when the load is a discharge lamp, for example.

According to the second aspect of the invention, the positive and negative electric powers supplied to the LC resonance circuit are unbalanced and accumulated in the LC resonance circuit by turning the switching elements on and off with different switching cycles. Energy can be supplied to the load as a direct current component, for example, to prevent extinction when the load is a discharge lamp.

[0026]

(Embodiment 1) FIG. 1 shows an embodiment of the present invention. The inverter device of the present embodiment is for converting a DC voltage obtained by rectifying an AC power supply AC by a diode bridge DB into an AC voltage, and switching elements S ₁ , S.
₂ and switching elements S ₃ and S ₄ are respectively connected between the output terminals of the diode bridge DB, and an inductor is provided between the connection point of the switching elements S ₁ and S _{2 and} the connection point of the switching elements S ₃ and S _4. A series resonance circuit composed of L ₁ and a capacitor C ₂ and a load circuit composed of a load Z are connected. The load Z is connected in parallel with the capacitor C ₂ . That is, this inverter device has a so-called full bridge configuration in which switching elements S _{1 to} S ₄ are bridge-connected.

In this type of normal full-bridge inverter device, the control circuit 1 alternately turns on the switching elements S ₁ and S ₄ and the switching elements S ₂ and S ₃ , which are generally provided at diagonal positions, as a set. Turn off to supply alternating current to the load circuit. First, the above general operation will be described in more detail so that the operation of the present invention can be easily understood.
Now, at time t ₀ , the control outputs V ₁ and V ₄ of the control circuit 1 become high level, and the control outputs V ₂ and V ₃ become low level. At this time, the switching elements S ₁ and S ₄ are turned on in FIG.
As shown in (a) and (d), it is turned on, the switching elements S ₂ and S ₃ are turned off as shown in (b) and (c) of the figure, and the switching element S ₁ and inductor L are switched from the diode bridge DB. ₁ , capacitor C ₂ and load Z,
A current flows through the load Z through the path of the switching element S ₄ . That is, the load current I _{Z in the} direction shown by the arrow in FIG. 1 is supplied.

Time t₂Then, the control output of the control circuit 1
V₁, V_FourGoes to the low level, and the control output V₂, V₃But
High level. Then, the switching element S₁, S
_FourTurns off as shown in FIGS. 2 (a) and 2 (d),
Touching element S₂, S₃Are shown in (b) and (c) of the same figure.
Turn on. Here, the switch of the above-mentioned inverter device is
Inductor L₁And capacitor C₂Empty
If it is set higher than the resonance frequency of the resonance circuit,
As described in the section of the prior art, the inductor L₁Accumulated in
The generated energy is the inductor L ₁, Capacitor C₂Over
Load Z, switching element S₃Parasitic diode,
Iodo bridge DB, switching element S₂The parasitic da
It is released through the route of iodine.

Then, the inductor L₁Energy of
When released, the switching element S ₂, S₃Is on
, Diode bridge DB, switching element S₃，
Capacitor C₂And load Z, inductor L₁,switch
Element S₂The load current I_ZIs the opposite of that
In the opposite direction (opposite to the arrow in FIG. 1). Time t_FourThen
Time t₀The control output V of the control circuit 1₁，
V_FourBecomes high level and the control output V₂, V₃But
Low level, switching element S₁, S_FourIs on
And the switching element S₂, S₃Is off
It Also at this time, inductor L₁Enel accumulated in
Gi is inductor L₁, Switching element S₁The parasitic da
Iod, diode bridge DB, switching element
S_FourParasitic diode, capacitor C₂And the load Z
Emitted on the road.

Then, after the energy of the inductor L ₁ is discharged, a current is passed from the diode bridge DB to the load Z through the path of the switching element S ₁ , the inductor L ₁ , the capacitor C ₂ and the load Z, and the switching element S _4. . In the case where the inverter device is operating normal, even at the time t _0, the energy stored in the inductor L ₁ after discharged via the parasitic diode of the switching element S _1, S _4, the switching element S ₁ , S ₄ to supply the load current I _Z. Also, connecting diodes in antiparallel to the switching elements S _{1 to} S ₄ , respectively,
Some emit the energy of inductor L ₁ .

By the way, in the case of the latter conventional inverter device described in the section of the prior art, when the electric power supplied to the load Z is changed, the series-connected switching shown in FIGS. 3 (a) and 3 (b) is performed. The on / off timings of the elements S ₁ and S ₂ are shifted from the on / off timings of the switching elements S ₃ and S ₄ shown in FIGS. The switching elements S ₁ and S ₂ and the switching elements S ₃ and S ₄ connected in series between the output terminals of the diode bridge DB are alternately turned on and off.

Further, the operation of this conventional inverter device will be described in detail. In addition, the following description is similar to the above case,
An example will be described in which the switching frequency of the inverter device is set higher than the resonance frequency of the resonance circuit. At time t ₁ , the switching element S ₃ is turned on as shown in FIG. 7C, which causes the path of the diode bridge DB, the switching element S ₃ , the capacitor C ₂ and the load Z, the inductor L ₁ , and the switching element S ₂ to pass. Thus, the load current I _Z is supplied.

At time t ₂ , the switching element S ₂ is turned off as shown in FIG. 3B, so that the supply of the load current I _Z is stopped. In addition, switching S ₂
When the switching element S ₁ is turned off, the switching element S ₁ is turned on as shown in FIG.
₁ is applied. In this case, the energy accumulated in the inductor L ₁ causes the load current to flow in the same direction as that of the inductor L ₁ , the parasitic diode of the switching element S ₁ , the switching element S ₃ , the capacitor C ₂ and the load Z. I _Z is caused to flow, and the energy stored in the inductor L ₁ is released.

At time t ₃ , as shown in FIG.
Since the switching element S ₃ is turned off, the discharge of the energy stored in the inductor L ₁ in the above path is stopped. However, at this time, the switching element S _{4 is changed} to the one shown in FIG.
As shown in (d), the control circuit 1 applies the control output V ₄ so as to turn on. Therefore, when the energy of the inductor L ₁ remains, the inductor L ₁ , the parasitic diode of the switching element S ₁ , the diode bridge DB, the parasitic diode of the switching element S ₄ , the capacitor C _2, and the path of the load Z, The above-mentioned release of energy is continued.

When the energy of the inductor L ₁ is released, the switching elements S ₁ and S ₄ are both turned on, and the diode bridge DB, the switching element S ₁ ,
A load current I _{Z in the} opposite direction to the previous one is passed through the path of the inductor L ₁ , the capacitor C _{2, the} load Z, and the switching element S ₄ . However, when the energy of the inductor L ₁ is discharged at the time point t ₃ ,
At the same time that the control output V ₄ of the control circuit 1 becomes high level, the switching element S ₄ is turned on. In this case, since already the switching element S ₁ in this time t ₃ is on, at time t _3, the diode bridge D
A load current I _Z flows through the path of B, the switching element S ₁ , the inductor L ₁ , the capacitor C ₂ and the load Z, and the switching element S ₄ .

Time t_FourThen, the switching element S₁Is o
And the load current I on the above path _ZSupply is stopped
It At this time, at the same time, the switching element S₂Control circuit
Control signal V to turn on from 1₂Is applied to the inductor
L₁The energy stored in the inductor L₁, Conde
Sensor C₂And load Z, switching element S_Four,switch
Element S₂Emitted in the path of the parasitic diode of.

Time t_FiveThen, the switching element S_FourIs o
And switching as shown in Fig. 3 (c)
Element S₃High level control output of control circuit 1 to turn on
Force V ₃Is given. At this time, inductor L₁Energy of
If Lugi remains, inductor L₁, Conden
SA C₂And load Z, switching element S₃Parasitic dio
Diode, diode bridge DB, switching element S₂
The path of the parasitic diode of the inductor L₁Energy of
Is released. And that energy was released
At this time, diode bridge DB, switching element S
₃, Capacitor C₂And load Z, inductor L₁, Sui
Touching element S₂The load current I _ZIs washed away.

Also in this case, at time t ₅ , the inductor L
_When the energy of ₁ is released, at time t ₅ ,
A load current I _Z flows through the path of the diode bridge DB, the switching element S ₃ , the capacitor C ₂ and the load Z, the inductor L ₁ , and the switching element S ₂ . At the time of steady operation, the same operation state as described at time t _5, even the time t _1. Then, by repeating the above series of operations, the DC voltage output from the diode bridge DB is converted into an AC voltage, and the AC voltage is supplied to the load circuit. In this inverter device, the switching elements S ₁ and S ₄ and the switching elements S ₂ and S at diagonal positions are used.
The simultaneous on-periods of ₃ are shorter than if they were coincident as shown in FIG. 2, thus reducing the power supplied to the load Z. In the case where is set higher than the resonant frequency of the resonant circuit to the switching frequency of the switching elements S ₁ to S _4, it is set lowest switching frequency of the switching elements S ₁ to S _4.

That is, in this inverter device, the switching elements S ₃ and S ₄ are turned on and off, and the switching elements S ₁ and S ₂ are turned on and off.
By changing the timing of turning off, the time during which the switching elements S ₁ and S ₄ and the switching elements S ₂ and S ₃ are simultaneously turned on is changed to change the switching elements S _{1 to} S _1.
The power supplied to the load circuit can be changed without changing the switching frequency of ₄ . Therefore, it is easy to design a filter (not shown) that prevents leakage of high-frequency output to the AC power supply AC. Also, the load Z
Is a discharge lamp, the frequency of the light emitted by the discharge lamp does not change and does not adversely affect other devices such as an infrared remote controller. Furthermore, when the discharge lamp is an HID lamp, it is possible to reduce the risk of causing an acoustic resonance phenomenon due to a change in output frequency.

In the above description, the case where the switching phases of the switching elements S ₃ and S ₄ are delayed with respect to the switching phases of the switching elements S ₁ and S ₂ has been explained. The power supplied to the load circuit can be changed. However, when the load Z is a discharge lamp in the above-mentioned inverter device, when the power supplied to the discharge lamp is reduced at low temperature, the discharge lamp goes out and the dimming control range of the discharge lamp is narrowed. is there.

Therefore, in the present embodiment, in order to improve this point, as shown in FIG. 4, the switching elements S ₁ and S _{4 are}
The switching frequency (switching period) with varying the switching frequency of the switching element S _2, S ₃ (switching period) of the switching element S _2,
The switching frequency of S ₃ is different. The operation will be described below with reference to FIG. The operation at times t _{0 to} t ₃ is the same as the operation described with reference to FIG.
In addition, this description will be made also when the switching frequency of the inverter device is higher than the resonance frequency of the resonance circuit.

At time t ₃ , switching elements S ₂ , S
₃ does not turn on. Thus, without energy accumulated in the inductor L ₁ is emitted, it is directly stored in the inductor L _1. At time t _4, by turning on the switching element S _1, S _4, the diode bridge DB,
Switching element S ₁ , inductor L ₁ , capacitor C
_The load current I _Z flows through the path of _{2, the} load Z, and the switching element S ₄ . At this time, the inductor L
_The energy stored in ₁ is added to the output of the diode bridge DB, the load current I _Z is passed, and the energy stored in the inductor L ₁ is further increased.

At time t ₅ , the switching element S ₂ is turned on, but the switching element S ₃ is not turned on, and the switching elements S ₁ and S ₄ are also off. Thus, without energy accumulated in the inductor L ₁ is emitted, it is directly stored in the inductor L _1. Time t ₆ ~t operations until ₈ time t ₂ ~t ₄ of the above-described is repeated, the inductor L ₁ is maintained in a state of accumulated energy.

At time t ₉ , the switching elements S ₂ , S
When _{the third} control signal V ₂ to turn on, V ₃ is given, the energy stored in the inductor L ₁ is, inductor L _1, the load Z and a capacitor C _2, the parasitic diode of the switching element S _3, the diode bridge DB, emitted through the parasitic diode of the switching element S ₂ ,
After the energy is released, the switching elements S ₂ and S ₃ are turned on to turn on the diode bridge DB, the switching element S ₃ , the load Z and the capacitor C ₂ , the inductor L ₁ ,
The load current I _Z is supplied through the path of the switching element S ₂ . The switching elements S ₂ and S ₃ are adapted to be turned on within the turn-on possible period.

By doing so, the positive and negative voltages applied to the resonance circuit become unbalanced, and the energy accumulated in the inductor L ₁ is applied to the load Z as a DC component. In FIG. 5, as in the case of FIG. 3 described above, the on / off timings of the switching elements S ₁ and S _{2 and} the on / off timings of the switching elements S ₃ and S ₄ are shifted, and the switching element S _{1 in the} diagonal position is shifted. , S ₄ and switching elements S ₂ , S ₃ are simultaneously turned on for a shorter period of time to reduce the power supplied to the load Z.

In this way, the electric power supplied to the load Z can be changed without changing the switching frequency, as described with reference to FIG. Moreover, the switching elements S ₁ and S ₄ and the switching elements S ₂ and S ₃ have different switching frequencies (in this embodiment, the switching frequencies of the switching elements S ₁ and S ₄ are the same as those of the switching elements S ₂ and S ₃ ). Since it is higher than the frequency), the positive and negative voltages applied to the resonance circuit become unbalanced, and a DC voltage is applied to the load Z. Therefore,
When the load Z is a discharge lamp, the discharge lamp can be stably turned on even when the dimming state is deepened at a low temperature, and the dimmable range does not narrow.

6 and 7 show specific circuits of the control circuit 1 in the inverter device. The control circuit 1 includes an oscillating circuit 2 that generates a rectangular wave signal having a fundamental frequency, drive circuits 3 and 4 that drive switching elements S ₁ and S ₂ according to the output of the oscillating circuit 2, and an oscillating circuit 2. It is composed of a delay circuit 5 for producing a signal whose output is delayed by a certain time, and drive circuits 6, 7 for driving the switching elements S ₃ , S ₄ according to the output of the delay circuit 5.

The oscillation circuit 2 includes a timer IC 2a, an external resistor R _{11 of the} timer IC 2a, and variable resistors VR ₁₁ and VR.
₁₂ and the diodes D ₁₁ and D ₁₂ and the capacitor C ₁₁ to generate the rectangular wave signal of FIG. Here, by adjusting the variable resistors VR ₁₁ and VR ₁₂ , the ratio of the high level period and the low level period of the rectangular wave signal can be changed.

The drive circuit 3 for driving the switching element S ₁ sets the dead-off period at the output Va of the oscillating circuit 2 to prevent the diode bridge DB from being short-circuited at the same time as the switching element S ₂ is turned on.
1 and a level shift circuit 32 which level-shifts the output of the dead circuit 31 and supplies it to the switching element S ₁ .

By the way, the above case has not been described.
Was connected in series to the diode bridge DB
Switching element S₁, S₂And switching element
S₃, S _FourIf both are turned on at the same time, the
Therefore, in order to prevent this, the switching element S₁, S₂
Or switching element S₃, S_FourIs turned on and off
At the time of switching, the switching element S₁, S₂There
Is the switching element S₃, S_FourWill be off together
There is a dead-off period.

The dead-off circuit 31, a variable resistor VR ₁₃ ~
It is composed of VR ₁₅ , diodes D ₁₃ and D ₁₄ , a capacitor C ₁₂ and a buffer amplifier B ₁ . That is, the variable resistance V
The signal shown in FIG. 8C is created by delaying the rise of the output Va of the oscillation circuit 2 for the time determined by the time constants of R ₁₃ , VR ₁₄ and the capacitor C ₁₂ (the period of t ₀ -t ₁ in FIG. 8). . The level shift circuit 32 includes transistors Q _{11 to} Q ₁₄
Is composed of a current mirror circuit CM ₃ , a buffer amplifier B ₂ , a zener diode ZD ₁ for making the output voltage of the diode bridge DB a constant voltage, and a constant voltage circuit 33 made of a capacitor C ₁₈ . In the level shift circuit 32, the output of the dead-off circuit 31 is replaced by a current in the current mirror circuit CM ₃ , and a signal is transmitted to the buffer amplifier B ₂ which operates at a different potential, and the buffer amplifier B ₂ is operated.
The output of ₂ is given to the switching element S ₁ as the control signal V ₁ .

The driving circuit 4 of the switching element S ₂ includes a dead-off circuit 41 to set the dead-off time to prevent a short circuit between the diode bridge DB and simultaneous ON and the switching element S ₂ to the output Va of the oscillation circuit 2, From the output of this dead-off circuit 41, the switching element S ₁
And a frequency conversion circuit 42 that generates a control signal V ₂ that turns on the switching element S ₂ in a double switching period in synchronization with the time when the element turns off. Since the reference potential of the switching element S ₂ matches the reference potential of the control circuit 1, the level shift circuit is not necessary.

The dead-off circuit 41 includes an inverter gate I ₁ , variable resistors VR _{16 to} VR ₁₈ , diodes D ₁₅ ,
It is composed of D ₁₆ , a capacitor C ₁₃ and a buffer amplifier B ₃ . In this dead-off circuit 41, the output Va of the oscillation circuit 2 is inverted by the inverter gate I ₁ (the inverted signal Vb is shown in FIG. 8B), and the time constants of the variable resistors VR ₁₆ and VR ₁₇ and the capacitor C ₁₃ are used. Determining time (t ₄ −t in FIG. 8)
_The signal of FIG. 8 (d) in which the rising edge of the inverted signal Vb is delayed only for the period shown by ₅ ) is created.

The frequency conversion circuit 42 is the dead-off circuit 4
A frequency-dividing IC (for example, 4516B) 42a that produces an output that is divided by 2 using the rising edge of the output Vn of 1 as a clock;
The output O ₀ of the frequency dividing IC 42a and the dead-off circuit 41
Of the output Vn of the AND gate and AND gate AND ₄ . The output of the frequency dividing IC 42a is shown in FIG.
(R) is obtained, and when the output Vo and the output Vn of the dead-off circuit 41 are ANDed, as shown in (s) of the same figure, in synchronization with the time when the switching element S ₁ is turned off. Switching element S with double switching period
A control signal V ₂ that turns on ₂ is created.

The delay circuit 5 includes a delay time setting section 51 for setting a time for delaying the output Va of the oscillation circuit 2 and an output V of the oscillation circuit 2 according to the delay time of the delay time setting section 51.
and a delayed signal creating section 52 which creates a signal obtained by delaying a as a whole. The delay time setting unit 51 includes variable resistors VR ₁₉ , VR ₂₀ , a diode D ₁₇ , a capacitor C ₁₄ ,
Inverter gates I ₃ and I ₄ and variable resistor VR
The time determined by the time constant of ₁₉ and the capacitor C ₁₄ (for example, the period indicated by t ₀ −t ₂ in FIG. 8) is the output Va of the oscillation circuit 2.
Will be the time to delay. More specifically, when the charging of the capacitor C ₁₄ is started from the rise of the output Va of the oscillation circuit 2 as shown in FIG. 8 (e) and the voltage across the capacitor C ₁₄ reaches the threshold voltage of the inverter gate I ₃ , The output Vd of the inverter gate I ₃ is as shown in FIG.

The delay signal creating section 52 includes a delay time setting section 5
1 Inverter gate I₃Output Vd and output of oscillator circuit 2
AND gate AND that takes AND with force Va₁And delay
Capacitor C to get time₁₅And Andgate AN
D₁Output Vg of capacitor C₁₅Charging Transis
Q₂₀~ Q_{twenty four}Current mirror circuit CM₁And
Indexer C₁₅A comparator that compares the voltage across the
Data CP₁And an inverter that inverts the output Va of the oscillator circuit 2.
Data Gate I₂And inverter gate I₂Output Vf of
Comparator CP₁Output Vi of AND and AND
Gate AND₂And AND gate AND₂Output Vj of
OR gate that takes an OR with the output Ve of the delay time setting unit 51
OR₁And OR gate OR₁Output Vk and inverter
Gate I ₂AND gate A which takes the AND with the output Vf of
ND₃And AND gate AND₃Depending on the output Vl of
Indexer C₁₅Transistor Q that discharges_{twenty five}, Q₂₆From
Current mirror circuit CM₂It consists of and.

The operation of the delay signal generator 52 will be described below. The AND gate AND ₁ outputs the output Vd of the inverter gate I ₃ of the delay time setting unit 51 shown in FIG.
And the output Va of the oscillation circuit 2 are ANDed, the output Vg of the AND gate AND ₁ is high for a period corresponding to the delay time set by the delay time setting unit 51, as shown in FIG. It becomes a level. While the output Vg of the AND gate AND ₁ is at the high level, the capacitor C ₁₅ is charged by the current mirror circuit CM ₁ as shown in FIG. 8 (j). Here, since the reference voltage of the comparator CP ₁ is set to approximately 0V, its output Vi is maintained at the high level as shown in FIG. 8 (k).

At the time of the above-mentioned operation, the output Vf of the inverter gate I ₂ is at the low level as shown in FIG. 8 (h), and therefore the AND gate AND ₂ as shown in FIG. 8 (l).
Output Vj is at low level. The output Vi of the comparator CP ₁ is kept at high level while the capacitor C ₁₅ is being charged. Now, FIG. 8 (a)
When the output Va of the oscillating circuit 2 becomes low level as shown in FIG. ₃ , the output Vf of the inverter gate I ₂ becomes high level as shown in FIG. Therefore, the output Vj of the AND gate AND ₂ becomes high level as shown in FIG. As a result, even after the output Ve of the inverter gate I ₄ of the delay time setting unit 51 has fallen to the low level, the output Vk of the OR gate OR ₁ is kept at the high level as shown in FIG. 8 (m).

At this time, the output V of the AND gate AND ₃
When l becomes high level as shown in FIG. 8 (n), the current mirror circuit CM ₂ operates and the capacitor C
₁₅ discharges are started. Here, the current mirror circuit C
The mirror ratio of M ₂ and the current mirror circuit CM ₁ is 1:
Since it is set to 1, the capacitor C ₁₅ is completely discharged after the same time as the delay time set by the delay time setting unit 51, as shown in FIG. 8 (j).

When the capacitor C ₁₅ is completely discharged, the output Vi of the comparator CP ₁ becomes low level as shown in FIG. 8 (k). As a result, the output Vj of the AND gate AND ₂ becomes low level as shown in FIG. 8 (l), and the output Vk of the OR gate OR ₁ also becomes low level as shown in FIG. 8 (m). Then, the output Vk of the OR gate OR ₁ causes the output Vk of the AND gate AND ₃ .
l becomes low level as shown in FIG. 8 (n), and the operation of the current mirror circuit CM ₂ is stopped.

That is, the delay signal generating section 52
For the same amount of time as the time set in the time setting section 51,
Agate OR₁Set to delay the fall of the output Vk of
The oscillation is generated according to the delay time of the delay time setting unit 51.
Create a signal that delays the output Va of the circuit 2 as a whole
There is. Then, based on this signal Vk, the drive circuits 6, 7
Is the switching element S₃, S _FourTo drive. Switchon
Element S₃The drive circuit 6 includes a dead-off circuit 61, a frequency
The number conversion circuit 62 and the level shift circuit 63
Itching element S_FourThe drive circuit 7 is a dead-off circuit 7
It is composed of 1.

The dead-off circuit 61 includes an inverter gate I ₅ , variable resistors VR _{24 to} VR ₂₆ , a diode D ₂₀ ,
It is composed of D ₂₁ , a capacitor C _17, and a buffer amplifier B ₅ , and outputs Vk of the OR gate OR ₁ to the inverter I ₅
The rise of the output Vm (shown in FIG. 8 (o)) inverted by
The dead-off period is set by delaying the period (indicated by t ₆ -t ₇ in FIG. 8) determined by the time constants of the variable resistors VR ₂₄ , VR ₂₆ and the capacitor C ₁₇ . This output Vp is shown in FIG.
As shown in.

The frequency conversion circuit 62 is the dead-off circuit 6
Output divided by 2 using the rising edge of the output Vp of 1 as the clock
An IC for frequency division that produces Vq and an output Vs that is divided by four (for example,
For example, 4516B) 62a and the output of this frequency dividing IC 62a
AND of the force Vq and the output Vp of the dead-off circuit 61
AND gate AND_FiveAnd this AND gate AND _Five
AND of the output Vr of the frequency divider and the output Vs of the frequency dividing IC 62a
AND gate AND₆It consists of and.

The output Vq of the frequency dividing IC 62a is shown in FIG.
The one shown in (u) is obtained, and its output Vq and dead off
Taking the AND with the output Vp of the circuit 61,
The output Vr shown is obtained. Then, this output Vr and FIG.
AND with the output Vs of the frequency dividing IC 62a shown in (w)
Then, the switching element S_FourSync when is turned off
And switching element S with a switching cycle of 4 times₃To
Control signal V to turn on ₃Is created.

The level shift circuit 63 includes a current mirror circuit CM ₄ including transistors Q _{15 to} Q ₁₈ , and
It is composed of a buffer amplifier B ₆ and a constant voltage circuit 64 including a Zener diode ZD ₂ and a capacitor C ₁₉ which make the output voltage of the diode bridge DB a constant voltage. The operation is the same as that of the level shift circuit 32. The dead-off circuit 71 includes variable resistors VR _{21 to} VR ₂₃ and a diode D.
₁₈ and D ₁₉ , a capacitor C ₁₆ and a buffer amplifier B ₄ , and the rise time of the output Vk of the OR gate OR ₁ is determined by the time constants of the variable resistors VR ₂₁ , VR ₂₂ and the capacitor C ₁₆ (t in FIG. 8). ₂ −t ₃ ) delay,
Set the dead-off period. The output V ₄ is as shown in FIG.

In this way, the phase difference θ between the on and off timings of the switching elements S ₁ and S ₂ and the switching elements S ₃ and S ₄ can be calculated from the time t ₁ -t in FIG.
Given in ₃ . (Embodiment 2) FIG. 9 shows another embodiment of the present invention. This embodiment basically operates in the same manner as the above embodiment. The feature of this embodiment is that the load Z is the discharge lamp La and the operation of the above embodiment is applied. The point is that the discharge lamp La is satisfactorily preheated and turned on.

When the discharge lamp La is not defective, the impeller
The resonance becomes very high and does not affect the resonance of the resonance circuit.
The resonance frequency is highest. So switching
Element S ₁~ S_FourWith the lowest switching frequency
(In the above embodiment, the switching element S₃)
Set the switching frequency slightly lower than the resonant frequency of the resonant circuit.
Set it high. And the switching element S₁~ S_Four
The one with the highest switching frequency among the
In case of, switching element S₁, S_Four) Control signal
As a reference, the switching element S₁, S₂And switch
Element S₃, S _Four180 degrees of switching phase of
The state is changed to the same phase. Do this
Then, the switching element S₁, S_FourAnd switching element
Child S₂, S ₃Simultaneous turning on of the
The discharge lamp La is changed to the state of
Preheat the module, and then mark the discharge start voltage on the discharge lamp La.
In addition, it can be turned on for lighting.

As a method of starting the discharge lamp La after preheating, the switching frequency of the inverter device is set to the resonance frequency of the resonance circuit, as in the case of the discharge lamp lighting device using the usual inverter device of this type. It goes without saying that a method of starting and lighting by approaching may be adopted. However, it goes without saying that the dimming control is performed by changing the simultaneous ON periods of the switching elements S ₁ and S ₄ and the switching elements S ₂ and S ₃ during steady lighting.

(Embodiment 3) FIG. 10 shows another embodiment of the present invention. This embodiment is basically the same as the above-described first embodiment, and in the case of the present embodiment, the configuration is such that the power supplied to the load Z is prevented from fluctuating in accordance with fluctuations in the power supply voltage. There are features. In the case of the present embodiment, the power fluctuation prevention circuit 8 for preventing fluctuations in the power supplied to the load Z due to fluctuations in the power supply is provided with a transistor Q ₃₀ whose conduction state changes according to fluctuations in the output of the diode bridge DB. , A photocoupler PC ₁ whose input current changes according to the conduction state of the transistor Q ₃₀ .

That is, when the output voltage of the diode bridge DB changes, the diode bridge DB of the control circuit 1
The voltage between terminals a and b connected to the output of the transistor changes, and the conduction state of the transistor Q ₃₀ changes. Therefore, the current flowing through the output transistor of the photocoupler PC ₁ changes, the charging current of the capacitor C ₁₄ changes, and the delay time setting unit 5
The setting state of the delay time of 1 changes.

Now, when the power supply voltage rises, the current bypassed by the transistor Q ₃₀ increases and the photocoupler P 30
The current input to C ₁ decreases. Therefore, the output current of the photocoupler PC ₁ decreases, and the charging time of the capacitor C ₁₄ becomes longer. Therefore, the switching elements S ₁ , S ₄
Also, the period in which the switching elements S ₂ and S ₃ are simultaneously turned on is shortened, and the power supplied to the load Z is reduced. Thereby, the current flowing through the load Z can be suppressed according to the fluctuation of the power supply voltage.

On the contrary, when the power supply voltage becomes low, the load Z
It functions to increase the power supplied to. In this way, the power fluctuation prevention circuit 8 can stabilize the power supplied to the load Z by applying the feedforward, and can perform stable lighting when the load Z is a discharge lamp, for example. (Embodiment 4) Although the load Z is one in the above-mentioned embodiment, as shown in FIG. 11, electric power may be supplied to a plurality of loads Z and Z ′ from the same inverter device.
In the case of FIG. 11, a series circuit of the capacitor C ₄ and the load Z and a series circuit of the inductor L ₂ and the load Z ′ are connected to both ends of the capacitor C ₂ . If you do this,
Only the alternating current due to resonance can flow through the load Z, and the direct current can mainly flow through the load Z ′. If the load Z ′ is a discharge lamp and the inductor L ₂ is connected to both ends of the filament of the discharge lamp on the non-power source side, a direct current generated in the inductor L ₂ causes a preheating current to flow through the filament, and the discharge lamp is adjusted to a low level. It is possible to turn on stably up to the light level.

(Embodiment 5) FIG. 12 shows another embodiment of the present invention.
Indicates. In this embodiment, the lamp current flowing through the discharge lamp La is
It is detected and supplied to the discharge lamp La according to the lamp current.
The power is automatically adjusted. In this example,
Itching element S₃, S_FourIn parallel with the series circuit of
Holding element S_Five, S₆Connect inductor L₁And discharge
Connect the series circuit with the lamp La to the switching element S₁, S₂Contact
Continuation point and switching element S₃, S_FourConnection between the
Continue, inductor L₁And the connection point between the discharge lamp La and the switch
Holding element S_Five, S₆Capacitor C between the connection point₂
Are connected. And the switching element S _FourSaw
Current detection resistor R for detecting lamp current₀Connect
I am doing it. The switching element S_Five, S₆Is a switch
Holding element S₃, S_FourOn and off in sync with each
The operation of the inverter device is no different from that of the above-described embodiment.
Works without any problems.

That is, the structure as described above is as follows.
To ensure that the current of the discharge lamp La can be detected,
The flow channel and the resonance current channel are separated.
And the detection resistance R₀Lamp current according to the detection output of
Is reduced, the switching element S₁, S_FourAnd switch
Holding element S₂, S₃The simultaneous ON period of
If the lamp current increases and the lamp current increases,
Touching element S₁, S _FourAnd switching element S₂, S
₃Reduce the lamp current by shortening the simultaneous on period of
Feedback control may be applied as described above.

(Embodiment 6) FIG. 13 shows a plurality of discharge lamps La.
A discharge lamp lighting device using an inverter device that lights up is shown.
You That is, the switching element S₁, S₂Each discharge
It also serves as a discharge lamp lighting device for the lamp La and is used as a switching element.
Child S₃, S_FourNew switching element S on the side _Five, S₆To
Connected in parallel, switching element S₁, S₂Connection point of
Switching element S₃, S_FourThe first negative between the connection point of
Connect the load circuit and switch S ₁, S₂Connection point
And switching element S_Five, S₆Between the connection point of the second
A load circuit is connected. And switching
Element S_Five, S₆Is the switching element S₃, S_FourEach of
They are turned on and off synchronously.

In the case of the present embodiment, it has been described with reference to FIGS.
Although it may be operated according to the operating state, this implementation
In the case of the example, as shown in FIG.
₁, S₂Are turned on and off alternately, and the switching element S
₃Is the switching element S ₁, S₂At twice the cycle
And the ON period of the switching element S₁, S
₂2 times the ON period, and the switching element S_Four
Is the switching element S ₃Is turned on at twice the cycle of
The ON period is the switching element S₃Same on period as
I am doing it.

A detailed description of the operation in this case is omitted,
As shown in (e) of the figure, the voltage applied to the load circuit is unbalanced in the negative direction, and a negative DC component is applied to the load circuit. Also in this case, it is possible to prevent the load, in particular, the discharge lamp La from extinguishing, substantially as in the case of the first embodiment. When changing the power supplied to the discharge lamp La, the switching elements S ₁ , S
_{As in} the case of the first embodiment, the power supply to the load can be varied and the frequency can be changed by shifting the on / off timings of ₂ and the switching elements S ₃ , S ₄ . You can work around the problem.

With the circuit configuration shown in FIG. 13, a discharge lamp lighting device for multiple lights can be constructed by adding a series circuit of one set of switching elements. Moreover,
Even if any one of the discharge lamps La is in a faulty state, there is an advantage that it does not affect the lighting states of the other discharge lamps La.
In addition, although the case of two lights has been described in the above case,
It can also be applied to the case of three or more lights.

(Embodiment 7) Similar to Embodiment 6, a plurality of discharges
Discharge lamp lighting device using an inverter device for lighting the lamp La
Position, switch the control circuit 1 as shown in FIG.
Element S₃~ S ₆I also controlled each individually
Of. FIG. 16 shows the operating state. This example is based on
This operation is basically the same as that of FIG. 14, and in the case of this embodiment,
Is the switching element S₃, S_FiveIs a switching element
S₁, S₂To turn on at 4 times the switching cycle
The switching element S _Four, S₆Is even more
Holding element S₃, S_FiveSo that it turns on at twice the cycle
There is. And the switching element S₃~ S_FourOn period of
It is set not to turn on at the same time. In this case
Also, the same effect as that of the third embodiment can be obtained.

FIG. 17 shows another operation method, in which the switching elements S ₃ and S ₅ are alternately turned on and off in the same switching cycle to switch the switching elements S ₄ and S ₆ to the switching elements S ₃ and S ₄ . The switching elements S ₃ and S ₄ connected in series have a double cycle and are turned on in synchronization with the off period. Even in this case, the lighting control can be performed by substantially the same operation as that of the sixth embodiment.

(Embodiment 8) In each of the embodiments described above, any two of the switching elements have the same switching cycle, and the switching cycles of the other switching elements are made different from the switching cycle to turn on. However, the embodiment will be described below in which the switching cycles of all the switching elements are different.

The circuit of this embodiment is the same as that shown in FIG. 1. In this embodiment, the switching cycle of the switching element S ₄ is the shortest, and the switching cycle of this switching element S ₄ is , Switching element S
₂ is doubled and is turned on in synchronization with the off time, and the switching element S ₃ is four times as long as the switching cycle of the switching element S ₄ (twice as long as the switching cycle of the switching element S ₂ ). ) And is turned on in synchronism with the off time, and the switching element S ₁ is turned on 8 times (twice the switching cycle of the switching element S ₃ ) and turned on in synchronism with the on time. is there.

The operation will be briefly described. Time t₀~ T₁of
During the period, the switching element S₁, S_FourIs turned on,
Diode bridge DB, switching element S₁,load
Circuit, switching element S_FourThe current in the load circuit
Flows. Time t₁~ T₂Then, switching element
S₂, S₃Is turned on, and the diode bridge DB, switch
Itching element S₃, Load circuit, switching element S₂
The current in the opposite direction flows through the load circuit to the load circuit.
It Time t₂~ T₃Switching element S during the period₃，
Switching element S_FourIs turned on, but the load
Is not supplied with current. Time t₃~ T_FourThen again
Itching element S₂, S₃Turns on and the diode
Ridge DB, switching element S₃, Load circuit, switch
Holding element S₂The current flows through the load circuit along the path. Time
Tick t_Four~ T_FiveThen, the switching element S ₃， Switchon
Element S_FourAlthough there is a period when the
Not supplied. And time t_FiveFrom time t₀~
t_FiveThe series of operations indicated by is repeated.

Also in the case of this embodiment, the positive and negative voltages applied to the load circuit are unbalanced, and the energy accumulated in the resonance circuit is supplied to the discharge lamp La as a direct current component so that the discharge lamp La is extinguished. Can be prevented. And FIG.
Reference numeral 9 shows a case where the switching phases of the switching elements S ₂ and S ₃ are shifted with respect to the switching phases of the switching elements S ₁ and S ₄ to reduce the power supplied to the discharge lamp La. Also in the case of this embodiment, the switching elements S _{1 to} S _1
The electric power supplied to the discharge lamp La can be adjusted without changing the switching frequency of ₄ and no problem occurs when the switching frequency is changed.

FIG. 20 shows a specific circuit of the control circuit of this embodiment. Since most of the specific circuit is the same as that of the first embodiment described with reference to FIG. 6, only a brief description will be given. In the case of the present embodiment, the frequency conversion circuit 3 is newly added to the drive circuit 3 with respect to the control circuit of FIG.
The feature is that 4 is provided. Frequency conversion circuit 34
Are output Vu divided by 2 and outputs Vw and 8 divided by 4 using the rising edge of the output Vt of the dead-off circuit 31 as a clock.
A frequency dividing IC (for example, 451 which produces a divided output Vy)
6B) AND gate AND ₇ that ANDs the output Vu of the frequency dividing IC 34a and the output Vt of the dead-off circuit 31, and the output Vv of the AND gate AND ₇
AND gate AND ₈ that ANDs the output Vw of the frequency dividing IC 34a, and the output V of this AND gate AND ₈
It is constituted by an AND gate AND ₉ which ANDs x and the output Vy of the frequency dividing IC 34a.

FIG. 21 (x) shows the output Vt of the dead-off circuit 31, and FIGS. 21 (y), (A) and (C) show the frequency dividing IC 3 respectively.
4a outputs Vu, Vw, Vy, AND gate AND ₇ ,
The outputs Vv and Vx of the AND ₈ are shown in the same figure (z) and (B).
Shown in. Then, the control signal V ₁ shown in FIG. 21C is obtained as the output of the AND gate AND ₉ . In the drive circuit 7 that drives the switching element S ₄ , the control signal V ₄ is generated with the output Va of the oscillation circuit 2 as a reference, so that the switching cycle thereof is equal to the output Va of the oscillation circuit 2. Since the drive circuit 4 that drives the switching element S ₂ roughly divides the output Va of the oscillation circuit 2 by _two to generate the control signal V ₂ , the switching cycle thereof is twice that of the switching element S _4. . Further, since the drive circuit 7 for driving the switching element S ₃ divides the output Va of the oscillation circuit 2 by 4 to generate the control signal V ₂ , the switching cycle thereof is four times that of the switching element S ₄ . The drive circuit 3 for driving the switching element S ₁ divides the output Va of the oscillation circuit 2 by 8 to generate the control signal V ₂ , so that the switching cycle is 8 times that of the switching element S ₄ .
Doubled.

(Ninth Embodiment) FIG. 22 is described in the third embodiment.
The power supplied to the load Z fluctuates according to the fluctuation of the power supply voltage.
The function for preventing this is provided in the eighth embodiment.
A power fluctuation prevention circuit 8 similar to that shown by 0 is provided.
It (Embodiment 10) FIG. 13 shows an inverter device according to Embodiment 8 above.
It is also possible to apply to Example 6 shown in FIG. That is,
The load is the discharge lamp La and the switching element S₁, S₂
Is also used as a discharge lamp lighting device for each discharge lamp La.
Itching element S₃, S_FourNew switching element on the side
S_Five, S₆Are connected in parallel and the switching element S₁, S
₂Connection point and switching element S₃, S_FourWith the connection point of
The first load circuit is connected between the switching element S and₁，
S₂Connection point and switching element S_Five, S₆Connection point of
The second load circuit is connected between the two. And
Switching element S_Five, S₆Is the switching element S₃，
S_FourIt is turned on and off in synchronization with each of.

In this embodiment, as shown in FIG. 23, the switching element S ₁ is turned on in the shortest switching cycle,
The switching element S ₂ is turned off and the switching element S _2
The switching element S ₁ is turned on in synchronization with the off time of the switching element S ₁ in a switching cycle twice as long as ₁ and the switching element S ₃ is turned on in synchronization with the off time of the switching element S ₁ in 3 times the switching cycle of switching element S _1. is allowed, and in synchronization with the turn-on time switching element S ₁ to turn on the switching element S ₄ at four times the switching period of the switching element S _1.

In this case, contrary to the case of the sixth embodiment, the discharge is performed.
A positive DC component is applied to the electric lamp La to generate a plurality of discharge lamps La.
Can be turned on. The switching element S₁
~ S _FourThe switching cycle length of₁> S₂> S₃
> S_FourNeedless to say, the above case may be reversed.
Absent. In addition, the switching element S₁~ S_FourSwitchon
The ratio of the cycle period may be 1: 2: 4: 8. In short,
The switching of four switching elements corresponding to one load circuit
All the switching cycles are different and the switch
The switching elements turn on simultaneously, and the load circuit is positively or negatively avalanized.
If the configuration can apply a fixed voltage, switching
There is no particular limitation on how to switch the elements.

(Embodiment 11) The inverter of Embodiment 8 described above.
It is also possible to apply the device to the sixth embodiment shown in FIG.
It That is, the switching element S in the tenth embodiment₃
~ S₆I will turn them on alternately so that they are not all turned on at the same time
It is something that will be done. In this embodiment, as shown in FIG.
Switching element S₁Is turned on and off at the shortest cycle
Switch element S₂The switching element S₁Oh
Switch on at twice the period in synchronization with the
Element S₃, S_FiveThe switching element S₂Switch on
Element S₁It is turned on at 6 times cycle in synchronization with the off time of
Switching element S_Four, S₆The switching element S
₁It is turned on at an 8 times cycle in synchronization with the on time of
Touching element S₃, S_FiveAnd switching element S_Four, S
₆Turn off each of the on times so that they do not turn on at the same time
I am doing it.

Further, as shown in FIG. 25, switching
Element S₃, S_FiveThe switching element S₂Switching
Element S₁Is synchronized with the off time of the
Switching element S_Four, S₆The switching element S
₁It is turned on at a cycle of 4 times in synchronization with the on time of
Touching element S₃, S_FiveAnd switching element S_Four, S
₆Turn off each of the on times so that they do not turn on at the same time
You may

Also in the case of this embodiment, the switching periods of the four switching elements corresponding to one load circuit are all different, and the respective switching elements connected in series on the non-usable side of each load circuit are As long as the switching elements at diagonal positions of the four switching elements corresponding to the respective load circuits are not turned on at the same time and a voltage with unbalanced positive / negative is applied to the load circuits, The switching method of the switching element is not particularly limited.

In the eighth embodiment, when the load Z is a discharge lamp, as in the second embodiment, the switching element S ₁
The switching frequency of the one having the lowest switching frequency (switching element S ₁ in the above embodiment) among S ₄ to S ₄ is set to be slightly higher than the resonance frequency of the resonance circuit when the discharge lamp La is faulty. The switching elements S _{1 to} S
Based on the control signal of the _fourth most have high switching frequency in (switching element S ₄ in the case of the above embodiment), the switching phase of the switching element S _1, S ₂ and the switching element S _3, S ₄ It is also possible to change from a state shifted by 180 degrees until the phase becomes the same, preheat the filament with the discharge lamp in a spot state, and then apply a discharge start voltage to the discharge lamp to start lighting.

Further, only during the start-up lighting, the start-up lighting may be performed by bringing the switching frequency of the inverter device close to the resonance frequency of the resonance circuit. Furthermore, as described in the fourth embodiment shown in FIG. 11, power may be supplied to a plurality of loads Z, Z ′ from the same inverter device, and further, as in the fifth embodiment shown in FIG. Alternatively, the lamp current flowing through the discharge lamp La may be detected, and the electric power supplied to the discharge lamp La may be automatically adjusted according to the lamp current.

Furthermore, in the above description, the case where the switching element is the FET has been described, but a diode connected in antiparallel to a bipolar transistor or a thyristor may be used. Further, it goes without saying that the DC power source includes a pure DC power source and a DC power source that is created by rectifying and smoothing an AC power source.

[0096]

As described above, according to the invention of claim 1, when the switching element of one series circuit is turned on and off, the switching element of the other series circuit is turned on and off.
Since the OFF timing is changed in the range from the same phase to the phase shifted by 180 degrees, the simultaneous ON period of the switching elements in the diagonal position is changed to supply the load to the load without changing the switching frequency. The power can be adjusted and the various problems associated with changing the switching frequency can be avoided. In addition, any two of the switching elements have the same switching cycle,
The switching cycles of the other switching elements are made to differ from the switching cycle to turn them on and off, thereby making the positive and negative supply power to the LC resonance circuit unbalanced, and the energy stored in the LC resonance circuit to be DC. It can be supplied to the load as a minute, and can prevent the lamp from going out when the load is a discharge lamp.

According to the second aspect of the invention, the positive and negative electric powers supplied to the LC resonance circuit are unbalanced and accumulated in the LC resonance circuit by making the switching periods of the switching elements different and turning them on and off. Energy can be supplied to the load as a direct current component, and it is possible to prevent the lamp from going out when the load is a discharge lamp, for example.

Further, as described in claim 3, the fluctuation of the power supply voltage is detected, and the ON / OFF timing of the switching element of the other series circuit is checked with respect to the ON / OFF timing of the switching element of the one series circuit. By adjusting the timing and controlling the power supplied to the load to be constant, it is possible to prevent fluctuations in the power supplied to the load due to fluctuations in the power supply voltage.

Further, as described in claim 4, the load current is detected, and the ON / OFF timing of the switching element of the other series circuit is compared with the ON / OFF timing of the switching element of the one series circuit. If the load current is controlled to be constant by adjusting, the constant power can be supplied to the load. Furthermore, as described in claim 5, a plurality of series circuits composed of the other two switching elements are provided, and between the connection points of the switching elements of one series circuit and the connection points of the respective other series circuits, By connecting a plurality of load circuits each including at least an LC resonance circuit and a load,
A plurality of loads can be driven at the same time, and only a series circuit composed of the other two switching elements needs to be added according to the loads, so that the circuit configuration becomes simple.

Further, as described in claim 6, the load is a discharge lamp, and the switching frequency of the switching element is set to be higher than the resonance frequency of the LC resonance circuit at least when the discharge lamp is at a fault, and the discharge lamp is started. Sometimes, for the on / off timing of the switching element of one series circuit,
The timing of turning on and off the switching element of the other series circuit can be changed from a phase shifted by 180 degrees to the same phase, so that the discharge lamp can be preheated favorably and turned on.

[Brief description of drawings]

FIG. 1 is a circuit diagram of an embodiment of the present invention.

FIG. 2 is an explanatory diagram of a basic operation of an inverter device having a full bridge configuration.

FIG. 3 is an operation explanatory diagram showing a method of varying the power supplied to the load without changing the switching frequency.

FIG. 4 is an operation explanatory diagram showing a method of applying a DC component to a load.

FIG. 5 is an operation explanatory diagram when a DC component is applied to the load and the power supplied to the load is changed without changing the switching frequency.

FIG. 6 is a circuit diagram showing a part of a specific configuration of the control circuit of the above.

FIG. 7 is a circuit diagram showing another portion of the specific configuration of the control circuit of the above.

FIG. 8 is an operation explanatory diagram of the control circuit of the above.

FIG. 9 is a circuit diagram of another embodiment.

FIG. 10 is a specific circuit diagram of a control circuit provided with a power fluctuation prevention circuit.

FIG. 11 is a circuit diagram of an embodiment for driving a plurality of loads driven by AC and DC.

FIG. 12 is a circuit diagram of an embodiment having a function of controlling a load current to be constant.

FIG. 13 is a circuit diagram of an embodiment for driving a plurality of loads.

FIG. 14 is an explanatory diagram of an operation of the above.

FIG. 15 is a circuit diagram of another embodiment for driving a plurality of loads.

FIG. 16 is an explanatory diagram of an operation of the above.

FIG. 17 is an operation explanatory diagram when the same is operated in a different state.

FIG. 18 is an operation explanatory diagram of still another embodiment in which the switching cycles of the switching elements are all different.

FIG. 19 is an operation explanatory diagram showing a method of varying the power supplied to the load without changing the switching frequency in the above.

FIG. 20 is a circuit diagram showing a part of a specific configuration of the above control circuit.

FIG. 21 is an operation explanatory diagram of the control circuit of the above.

FIG. 22 is a specific circuit diagram of a part of the control circuit in the case where the power fluctuation prevention circuit is provided in the case where the switching cycles of the switching elements are all different.

FIG. 23 is an operation explanatory diagram of the embodiment in which a plurality of loads are driven in the case where the switching cycles of the switching elements are all different.

FIG. 24 is an operation explanatory diagram of another example in which a plurality of loads are driven in different states when the switching cycles of the switching elements are all different.

FIG. 25 is an operation explanatory diagram in the case where a plurality of loads are driven in different states in a case where switching cycles of switching elements are all different.

FIG. 26 is a circuit diagram of a conventional half-bridge inverter device.

FIG. 27 is an explanatory diagram of the operation of the above.

[Explanation of symbols]

AC AC power supply DB Diode bridge S _{1 to} S ₄ Switching element L ₁ Inductor C ₂ Capacitor Z Load 1 Control circuit

─────────────────────────────────────────────────── ───

[Procedure amendment]

[Submission date] October 1, 1993

[Procedure Amendment 1]

[Document name to be amended] Statement

[Name of item to be corrected] 0005

[Correction method] Change

[Correction content]

Then, at time t ₁ , FIG.
, The control output V ₁ of the control circuit ₁ is low level,
As shown in FIG. 6B, the control output V ₂ becomes high level, the switching element S ₁ is turned off, and the switching element S ₂ is turned on. However, unlike the pure switch, the switching elements S ₁ and S ₂ are applied to the switching element S ₂ when a voltage having a polarity opposite to the normal polarity (voltage having a polarity opposite to the polarity of the DC power source E) is applied. Originally
The parasitic diode has a function of causing a current to flow in the direction opposite to the direction in which the current I _S2 flows (the current direction indicated by the arrow in FIG. 26). Therefore, when the switching element S ₂ is turned on, the switching element S ₂ is not turned on in the original direction of the current, and the current flows through the parasitic diode of the switching element S ₂ by the energy accumulated in the inductor L ₂ . That is, the switching element S ₂ becomes conductive in the opposite direction. Then, by the action of electric current in the same direction as far inductor L _1, the energy stored in the resonant circuit,
A current flows through the path of the inductor L ₁ , the DC cut capacitor C ₁ , the capacitor C _{2, the} discharge lamp La, and the parasitic diode of the switching element S ₂ . That is, since the operating frequency of the inverter circuit is set to a range higher than the resonant frequency of the resonant circuit, the load circuit operates as described above.

[Procedure Amendment 2]

[Document name to be amended] Statement

[Correction target item name] 0006

[Correction method] Change

[Correction content]

When the current of the resonance circuit becomes zero
From the point , the switching element S ₂ is in the original ON state (a state in which the current I _S2 flows in the direction shown by the arrow in FIG. 26), and the DC cut capacitor C ₁ and the resonance circuit capacitor are connected.
Using the electric charge accumulated in the capacitor C ₂ as a power source, a current in the opposite direction flows through the path of the DC cut capacitor C ₁ , the inductor L ₁ , the switching element S ₂ , the capacitor C ₂ and the discharge lamp La.

[Procedure 3]

[Document name to be amended] Statement

[Correction target item name] 0007

[Correction method] Change

[Correction content]

Thereafter, at time t ₂ , the control output V ₁ of the control circuit ₁ is at the high level, as in the case of time t ₀ , as shown in FIG.
As shown in (b), since the control output V ₂ becomes low level, the switching element S ₁ is turned on and the switching element S ₂ is turned off. However, even in this case, the switching element S ₁ does not turn on in the direction in which the original current I _S1 flows (the direction indicated by the arrow in FIG. 26), and the resonance circuit S ₁ does not turn on.
The energy stored in the path turns on the parasitic diode of the switching element S ₁ . That is, the switching element S
₁ becomes a state of conducting in the opposite direction. Then, the energy stored in the resonant circuit, the parasitic diode of the switching element S _1, a DC power source E, a capacitor C ₂ and the discharge lamp La, the current flow in the path of the DC cut capacitor C ₁
Be done .

[Procedure amendment 4]

[Document name to be amended] Statement

[Correction target item name] 0008

[Correction method] Change

[Correction content]

When the current of the resonance circuit becomes zero
From the point , the switching element S ₁ is in the original ON state, and the DC power source E, the switching element S ₁ , the inductor L
₁ , a current flows through the path of the DC cut capacitor C ₁ , the capacitor C ₂ and the discharge lamp La. Hereinafter, by repeating the series of operations described above, the DC power supply E is converted into high frequency power, and the high frequency power is supplied to the discharge lamp La. At this time, the current I _L1 flowing through the inductor L ₁ is as shown in FIG.

[Procedure Amendment 5]

[Document name to be amended] Statement

[Correction target item name] 0009

[Correction method] Change

[Correction content]

In the above description, the time t₀in the case of
And the switching element S₁Does not turn on in the original current direction.
However, until then, the switching element S₁, S₂
Is turned on and off alternately during steady lighting, time t₀
Also in the switching element S ₁Parasitic diode
Depending onElectric current flows, Then the original switching element
S₁Current I_S1Will turn on in the direction
not. In the above description, the switching element S
₁, S₂Parasitic diode of inductor L₁Energy of
The switching element S₁, S
₂You may connect a diode in anti-parallel to each
Yes.

[Procedure correction 6]

[Document name to be amended] Statement

[Correction target item name] 0012

[Correction method] Change

[Correction content]

However, when the DC power source E is obtained by rectifying and smoothing the AC power source, the switching elements S ₁ ,
When the switching frequency of S ₂ is changed, there is a problem that high frequency leaks to the AC power source side. Therefore, a filter that prevents high-frequency components from leaking to the AC power supply side is provided at the input end of a diode bridge that rectifies the AC power supply. However, when the operating frequency of the inverter device changes as described above, there is a problem that the design of the filter for removing high frequency components becomes complicated.

[Procedure Amendment 7]

[Document name to be amended] Statement

[Correction target item name] 0014

[Correction method] Change

[Correction content]

As a conventional example that can improve this point, "Off-Line Application of Fixed-Frequency Clam"
ped Mode Series Resonant Converter ”, IEEE Tansacti
on onPower Electronics, Vol.6; No.1, January, 1991. In this conventional example, two series circuits of two switching elements are connected in parallel with a DC power source, and
A load circuit including at least an LC resonance circuit and a load is connected between the connection points of the switching elements of the respective series circuits, and the switching elements of the respective series circuits are alternately turned on and off so as not to be turned on at the same time. Change the ON / OFF phase of the switching element of the other series circuit with respect to the ON / OFF timing of the switching element of
It is as that.

[Procedure Amendment 8]

[Document name to be amended] Statement

[Name of item to be corrected] 0015

[Correction method] Change

[Correction content]

The operation of the above conventional example will be described in detail in the section of the embodiment of the present invention. According to this conventional example, the electric power supplied to the load can be changed without changing the operating frequency. However, in a state in which applied in particular as a discharge lamp lighting device of a conventional example described above, squeezed reduce power supplied to the discharge lamp La at a low temperature, the discharge lamp La Shi Oko extinction
There is also a problem that flicker occurs due to moving stripes . Therefore, there is a problem that the dimming range of the discharge lamp La is limited.

[Procedure Amendment 9]

[Document name to be amended] Statement

[Name of item to be corrected] 0027

[Correction method] Change

[Correction content]

In this type of normal full-bridge inverter device, the control circuit 1 alternately turns on the switching elements S ₁ and S ₄ and the switching elements S ₂ and S ₃ , which are generally provided at diagonal positions, as a set. Turn off to supply alternating current to the load circuit. First, the above general operation will be described in more detail so that the operation of the present invention can be easily understood.
Now, at time t ₀ , the control outputs V ₁ and V ₄ of the control circuit 1 become high level, and the control outputs V ₂ and V ₃ become low level. At this time, the switching elements S ₁ and S ₄ are turned on in FIG.
As shown in (a) and (d), it is turned on, the switching elements S ₂ and S ₃ are turned off as shown in (b) and (c) of the figure, and the switching element S ₁ and inductor L are switched from the diode bridge DB. ₁ , capacitor C ₂ and load Z,
A current is passed through the load Z through the path of the switching element S ₄ and the diode bridge DB . That is, the load current I _{Z in the} direction shown by the arrow in FIG. 1 is supplied.

[Procedure Amendment 10]

[Document name to be amended] Statement

[Correction target item name] 0028

[Correction method] Change

[Correction content]

Time t₂Then, the control output of the control circuit 1
V₁, V_FourGoes to the low level, and the control output V₂, V₃But
High level. Then, the switching element S₁, S
_FourTurns off as shown in FIGS. 2 (a) and 2 (d),
Touching element S₂, S₃Are shown in (b) and (c) of the same figure.
Turn on. Here, the switch of the above-mentioned inverter device is
Inductor L₁And capacitor C₂Empty
If it is set higher than the resonance frequency of the resonance circuit,
As explained in the prior art section,In the resonant circuitAccumulated
EnergyBy, Inductor L ₁, Capacitor C₂Over
Load Z, switching element S₃Parasitic diode,
Iodo Bridge DB,AC power supply AC,Switching element
Child S₂In the path of the parasitic diode ofCurrent flows.

[Procedure Amendment 11]

[Document name to be amended] Statement

[Name of item to be corrected] 0029

[Correction method] Change

[Correction content]

Then, the current in the resonance circuit becomes zero.
From that moment , the switching elements S ₂ and S ₃ are turned on, and the switching element S is turned on from the diode bridge DB.
₃ , the path of the capacitor C ₂ and the load Z, the inductor L ₁ , the switching element S ₂ , the diode bridge DB ,
The load current I _Z is made to flow in the opposite direction (the direction opposite to the arrow in FIG. 1). At time t ₄ , the control outputs V ₁ and V ₄ of the control circuit 1 become high level and the control outputs V ₂ and V ₃ become low level, as in the case of time t ₀ , and the switching elements S ₁ and S _{1 4} is turned on and the switching elements S ₂ and S ₃ are turned off. Also in this case, the co
The energy stored in the Fukairo, inductor L _1, a parasitic diode of the switching element S _1, the diode bridge DB, the AC power source AC, the switching element S
Current flows through the path of the parasitic diode of ₄ , the capacitor C ₂ and the load Z.

[Procedure Amendment 12]

[Document name to be amended] Statement

[Name of item to be corrected] 0030

[Correction method] Change

[Correction content]

When the current of the resonance circuit becomes zero
From the point, from the diode bridge DB, the switching element S ₁ , the inductor L ₁ , the capacitor C ₂ and the load Z,
Switching element S _4, a path of the diode bridge DB, a current Ru into the load Z. In addition, when the inverter device is in steady operation, even at the time point of time t ₀ , electric power is supplied through the parasitic diodes of the switching elements S ₁ and S _4.
After the current flows, through the switching elements S ₁ and S ₄ ,
A load current I _{Z in the} positive direction is supplied. Further, there is also one in which a diode is connected in antiparallel to each of the switching elements S _{1 to} S ₄ to allow a current of the resonance circuit to flow .

[Procedure Amendment 13]

[Document name to be amended] Statement

[Name of item to be corrected] 0032

[Correction method] Change

[Correction content]

Further, the operation of this conventional inverter device will be described in detail. In addition, the following description is similar to the above case,
An example will be described in which the switching frequency of the inverter device is set higher than the resonance frequency of the resonance circuit. At time t ₁ , the switching element S ₃ is turned on and the switching element S ₄ is turned off , as shown in FIGS.
Therefrom by a diode bridge DB, a switching element S _3, capacitor C ₂ and the load Z, inductor L _1, the switching element S _2, the diode bridge DB
The load current I _Z is supplied through the path.

[Procedure Amendment 14]

[Document name to be amended] Statement

[Correction target item name] 0033

[Correction method] Change

[Correction content]

At time t ₂ , the switching element S ₂ is turned off as shown in FIG.
There is no voltage applied to the . In addition, the switching element S
_When the switching element S ₁ is turned off, the switching element S ₁ is turned on as shown in FIG.
The control output V ₁ is applied from the control circuit 1 so as to be turned on as shown in FIG. In this case, the inductor L ₁ and the switching element S ₁ are stored by the energy stored in the resonance circuit.
In the path of the parasitic diode, the switching element S ₃ , the capacitor C ₂ and the load Z, the load current I _Z flows in the same direction as before .

[Procedure Amendment 15]

[Document name to be amended] Statement

[Correction target item name] 0034

[Correction method] Change

[Correction content]

At time t ₃ , as shown in FIG.
The switching element S ₃ is turned off . The switching element S ₄ 3 control outputs V ₄ from the control circuit 1 so as to turn on as shown in (d) is applied at the time of this. Therefore, when energy remains in the resonance circuit , the inductor L ₁ , the parasitic diode of the switching element S ₁ ,
Diode bridge DB, AC power supply AC, parasitic diode of switching element S ₄ , capacitor C ₂ and load Z
The current flows through the path.

[Procedure Amendment 16]

[Document name to be amended] Statement

[Correction target item name] 0035

[Correction method] Change

[Correction content]

AndWhen the current of the resonance circuit becomes zero
From the point, Switching element S₁, S _FourAre both on
Diode bridge DBFrom, Switching element S
₁, Inductor L₁, Capacitor C₂And load Z, Sui
Touching element S ₄ , diode bridge DBIn the route of
Load current I in the opposite direction_ZIs washed away. However,
Above time t₃At the time ofResonance circuit current is zeroPlace
The control output V of the control circuit 1_FourBecomes high level
At the same time, the switching element S_FourTurns on. This place
In this case, this time t₃Already switching element S₁Is o
Time t₃At the diode bridge
DBFrom, Switching element S₁, Inductor L₁,
Indexer C₂And load Z, switching element S ₄ , die
Aude Bridge DBThe load current I_ZButflowIt

[Procedure Amendment 17]

[Document name to be amended] Statement

[Correction target item name] 0036

[Correction method] Change

[Correction content]

Time t_FourThen, the switching element S₁Is o
And the load current I on the above path _ZSupply is stopped
It At this time, at the same time, the switching element S₂Control circuit
Control signal V to turn on from 1₂Is applied,Resonant circuitTo
Stored energyBy, Inductor L₁, Conde
Sensor C₂And load Z, switching element S_Four,switch
Element S₂In the path of the parasitic diode ofCurrent flows.

[Procedure 18]

[Document name to be amended] Statement

[Name of item to be corrected] 0037

[Correction method] Change

[Correction content]

Time t_FiveThen, the switching element S_FourIs o
And switching as shown in Fig. 3 (c)
Element S₃High level control output of control circuit 1 to turn on
Force V ₃Is given. At this time,In the resonant circuitEnergy
If it remains, inductor L₁, Capacitor C₂
And load Z, switching element S₃Parasitic diode,
Diode bridge DB,AC power supply AC,Switching
Element S₂In the path of the parasitic diode ofCurrent flows. That
hand,After the current in the resonant circuit becomes zero, Diode
Judge DBFrom, Switching element S₃, Capacitor C₂
And load Z, inductor L₁, Switching element S ₂ ,
Diode bridge DBThe load current I_ZButflow
It

[Procedure Amendment 19]

[Document name to be amended] Statement

[Correction target item name] 0038

[Correction method] Change

[Correction content]

Also in this case, at time t ₅ , the resonance circuit error
When the energy is zero , the switching element S ₃ , the capacitor C ₂ and the load Z, the inductor L ₁ , and the switching element S are switched from the diode bridge DB at time t _5.
2 , the load current I _Z in the diode bridge DB path
Flow Ru. At the time of steady operation, the same operation state as described at time t _5, even the time t _1. Then, by repeating the above series of operations, the DC voltage output from the diode bridge DB is converted into an AC voltage, and the AC voltage is supplied to the load circuit. In this inverter device, the simultaneous ON periods of the switching elements S ₁ and S ₄ and the switching elements S ₂ and S _{3 in} the diagonal position are shorter than in the case where they coincide as shown in FIG. The power supplied is reduced. Incidentally, the switching frequency of the inverter device has higher than the resonant frequency of the resonant circuit
Set the lowest in the range .

[Procedure amendment 20]

[Document name to be amended] Statement

[Correction target item name] 0039

[Correction method] Change

[Correction content]

That is, in this inverter device, the switch
Holding element S₁, S₂For the on / off timing of
The switching element S₃, S_FourOn, offPhase ofTo
By changing the switching element S₁, S_FourOver
And switching element S₂, S ₃At the same timeToTime to turn on
Change the switching element S₁~ S_FourSwitching
Change the power supplied to the load circuit without changing the frequency.
It can be transformed. Therefore, AC power supply A
A filter (not shown) for preventing leakage of high frequency output to C
It becomes easier to design The load Z is a discharge lamp.
In this case, the frequency of the light emitted by the discharge lamp changes and the infrared
Do not adversely affect other devices such as Mokon.
Yes. Furthermore, if the discharge lamp is a HID lamp,
There is little risk of causing acoustic resonance due to frequency changes.
I can do it.

[Procedure correction 21]

[Document name to be amended] Statement

[Correction target item name] 0040

[Correction method] Change

[Correction content]

In the above description, the case where the switching phases of the switching elements S ₃ and S ₄ are delayed with respect to the switching phases of the switching elements S ₁ and S ₂ has been explained. The power supplied to the load circuit can be changed. However, when the load Z is a discharge lamp in the above-mentioned inverter device, when the power supplied to the discharge lamp is reduced at low temperature, the discharge lamp goes out and the dimming control range of the discharge lamp is narrowed. is there. Also, the power supplied to the discharge lamp should be reduced.
However, there is also the problem of flickering due to moving stripes.
It

[Procedure correction 22]

[Document name to be amended] Statement

[Correction target item name] 0042

[Correction method] Change

[Correction content]

At time t ₃ , switching elements S ₂ , S
₃ does not turn on. Therefore, the energy accumulated in the resonance circuit causes the inductor L ₁ , the capacitor C _2, and
Load Z, parasitic diode of switching element S ₃ ,
Iodo bridge DB, AC power supply AC, switching element
A current flows in the path of the parasitic diode of the child S ₂ . Time t
_{At 4} , when the switching elements S ₁ and S ₄ are turned on, the load current I flows from the diode bridge DB to the switching element S ₁ , the inductor L ₁ , the capacitor C ₂ and the load Z, the switching element S ₄ and the diode bridge DB. _Z is shed. At this time, the resonance circuit should be
If the energy remains , the load current I _Z flows in the form of being added to the output of the diode bridge DB and the inductor L
_The energy stored in ₁ is even greater.

[Procedure amendment 23]

[Document name to be amended] Statement

[Correction target item name] 0043

[Correction method] Change

[Correction content]

At time t ₅ , the switching element S ₃ is turned on, but the switching element S ₂ is not turned on, and the switching elements S ₁ and S ₄ are also off. Therefore, due to the energy stored in the resonant circuit , the inductor
Data L _1, a capacitor C ₂ and the load Z, the switching element
S ₃ parasitic diode, diode bridge DB, AC
Power supply AC, parasitic diode of switching element S ₂
Current flows on the road . At times t _{6 to} t ₈ , the above-mentioned time t
Operation up to ₂ ~t ₄ is Ru repeated.

[Procedure correction 24]

[Document name to be amended] Statement

[Correction target item name] 0044

[Correction method] Change

[Correction content]

At time t ₉ , the switching elements S ₂ , S
_When the control signals V ₂ and V ₃ for turning on ₃ are applied, the inductor L ₁ , the load Z and the capacitor C ₂ , the parasitic diode of the switching element S ₃ , the diode bridge DB are generated by the energy stored in the resonance circuit. , Exchange
A current flows through the power supply AC and the parasitic diode of the switching element S ₂ . And the current of the resonance circuit is zero.
After that, the switching elements S ₂ and S ₃ are turned on,
The load current I _Z is supplied through the path of the diode bridge DB, the switching element S ₃ , the load Z, the capacitor C ₂ , the inductor L ₁ and the switching element S ₂ . In addition,
The switching elements S ₂ and S ₃ are adapted to be turned on within the turn-on possible period.

[Procedure correction 25]

[Document name to be amended] Statement

[Correction target item name] 0052

[Correction method] Change

[Correction content]

The driving circuit 4 of the switching element S ₂ includes a dead-off circuit 41 to set the dead-off time to prevent a short circuit between the diode bridge DB and simultaneous ON and the switching element S ₂ from the output Va of the oscillation circuit 2,
From the output of the dead-off circuit 41, the switching element S
_The frequency conversion circuit 42 creates a control signal V ₂ for turning on the switching element S ₂ in a double switching period in synchronization with the time when ₁ is turned off. Since the operation reference potential of the switching element S ₂ matches the reference potential of the control circuit 1, the level shift circuit is not necessary.

[Procedure Amendment 26]

[Document name to be amended] Statement

[Correction target item name] 0074

[Correction method] Change

[Correction content]

That is, the structure as described above is as follows.
To ensure that the current of the discharge lamp La can be detected,
The flow channel and the resonance current channel are separated.
And the detection resistance R₀Lamp current according to the detection output of
Is reduced, the switching element S₁, S_FourAnd switch
Holding element S₂, S₃The simultaneous ON period of
If the lamp current increases and the lamp current increases,
Touching element S₁, S _FourAnd switching element S₂, S
₃Reduce the lamp current by shortening the simultaneous on period of
Feedback control may be applied as described above.
It should be noted that the diodes D _{A to} D
By providing _D , each current can be separated by the forward voltage.
I have it. Also, instead of the diodes D _{A to} D _D
A resistor may be used.

[Procedure Amendment 27]

[Document name to be amended] Statement

[Correction target item name] 0076

[Correction method] Change

[Correction content]

In the case of the present embodiment, it has been described with reference to FIGS.
Although it may be operated according to the operating state, this implementation
In the case of the example, as shown in FIG.
₁, S₂Are turned on and off alternately, and the switching element S
₃Is the switching element S ₁, S₂At twice the cycle
And the ON period of the switching element S₁, S
₂2 times the ON period, and the switching element S_Four
Is the switching element S ₃Is turned on at twice the cycle of
The ON period is the switching element S₃Same on period as
I am doing it.The diodes D _{A to} D _D are the same as those in the fifth embodiment.
It works like this.

[Procedure correction 28]

[Document name to be amended] Statement

[Correction target item name] 0082

[Correction method] Change

[Correction content]

The circuit of this embodiment is the same as that shown in FIG. 1, and its operating state is shown in FIG. In the present embodiment Yes and shortest switching period of the switching element S _4, and the switching period of the switching element S _4, the period of the switching element S ₂ 2-fold, and the turned on synchronously with the off time, 4 times the period of the switching element S ₃ with respect to the switching period of the switching element S ₄ (2-fold relative to the switching period of the switching element S _2), and in synchronization with the off-time and on, the switching element S ₁ The period is eight times (twice as much as the switching period of the switching element S ₃ ) and is turned on in synchronization with the on time.

[Procedure correction 29]

[Document name to be amended] Statement

[Name of item to be corrected] 0083

[Correction method] Change

[Correction content]

The operation will be briefly described. Time t₀~ T₁of
During the period, the switching element S₁, S_FourIs turned on,
Diode bridge DBFrom, Switching element S₁,
Load circuit, switching element S ₄ , diode bridge
DBThe current flows through the load circuit along the path. Time t₁~ T
₂Then, the switching element S₂, S₃Is turned on,Both
The energy stored in the vibration circuit causes the inductor
L ₁ , load Z, capacitor C ₂ , switching element S
₃ parasitic diode, diode bridge DB, switch
The current flows through the path of the parasitic diode of the ching element S _2.
It afterwards,Diode bridge DBFrom, Switchon
Element S₃, Load circuit, switching element S₂The route
Then, the current in the opposite direction to that before flows through the load circuit. Times of Day
t₂~ T₃Switching element S during the period₃,switch
Element S_FourIs on, but the loadresonance
A free-vibration current flows due to the circuit.Time t₃~ T_Fourso
IsTime t ₁~ T₂alike,Switching element S again
₂, S₃Turns on and the diode bridge DBFrom,
Switching element S₃, Load circuit, switching element S
₂ , diode bridge DBThe current in the load circuit
Flows. Time t_Four~ T_FiveThen, switching element
S₃, Switching element S_FourIs on
But for the loadA free-vibration current flows due to the resonance circuit.
And time t_FiveFrom time t₀~ T_FiveShown by
The operation of is repeated.

[Procedure amendment 30]

[Document name to be amended] Statement

[Correction target item name] 0096

[Correction method] Change

[Correction content]

[0096]

As described above, according to the invention of claim 1, when the switching element of one series circuit is turned on and off, the switching element of the other series circuit is turned on and off.
Since the OFF timing is changed in the range from the same phase to the phase shifted by 180 degrees, the simultaneous ON period of the switching elements in the diagonal position is changed to supply the load to the load without changing the switching frequency. The power can be adjusted and the various problems associated with changing the switching frequency can be avoided. In addition, any two of the switching elements have the same switching cycle,
The switching cycles of the other switching elements are made different from the switching cycle to turn them on and off, thereby making the positive and negative supply power to the LC resonance circuit unbalanced, and the energy stored in the LC resonance circuit to be DC. The load can be supplied as a minute to the load. For example, when the load is a discharge lamp, it is possible to prevent flickering due to extinction and moving stripes .

[Procedure correction 31]

[Document name to be corrected] Drawing

[Name of item to be corrected] Fig. 12

[Correction method] Change

[Correction content]

[Fig. 12]

[Procedure correction 32]

[Document name to be corrected] Drawing

[Name of item to be corrected] Fig. 13

[Correction method] Change

[Correction content]

[Fig. 13]

Claims (9)

[Claims] 1. A series circuit of two switching elements is connected in parallel with two sets of a DC power source, and a load circuit consisting of at least an LC resonant circuit and a load is connected between the connection points of the switching elements of each series circuit, Matching any two switching cycles of the above switching elements,
With respect to the switching cycle, the switching cycle of the other switching element is changed to be turned on and off respectively, and when the switching element of one series circuit is turned on and off, the switching element of the other series circuit is turned on, An inverter device characterized in that an off timing is variable within a range from the same phase to a phase shifted by 180 degrees. 2. A series circuit of two switching elements is connected in parallel with two sets of a DC power source, and a load circuit consisting of at least an LC resonance circuit and a load is connected between the connection points of the switching elements of each series circuit, The above switching elements are turned on and off with different switching cycles, and the on and off timings of the switching elements of the other series circuit are changed from the same phase with respect to the on and off timings of the switching element of the other series circuit. An inverter device characterized by being variable within a range up to 180 degrees out of phase. 3. A load is detected by detecting a power supply voltage fluctuation and adjusting the on / off timings of the switching elements of one series circuit to the on / off timings of the other series circuit. 3. The electric power supplied is controlled to be constant, and the electric power is supplied.
Inverter device described. 4. The load current is detected, and the ON / OFF timing of the switching element of one of the series circuits is
The inverter device according to claim 1 or 2, wherein the on / off timing of the switching element of the other series circuit is adjusted to control the load current at a constant level. 5. A plurality of series circuits composed of the other two switching elements are provided, and at least the LC resonance circuit and the load are provided between the connection points of the switching elements of the one series circuit and the connection points of the respective other series circuits. The inverter device according to claim 1 or 2, wherein a plurality of load circuits each consisting of are connected to each other. 6. The inverter device according to claim 5, wherein all the switching elements of the other series circuit are not turned on at the same time. 7. The load is a discharge lamp, the switching frequency of the switching element is set higher than the resonance frequency of the LC resonance circuit at least when the discharge lamp is defective, and the switching frequency of the switching element is set at the start of the discharge lamp. The inverter device according to claim 1 or 2, wherein the inverter device is arranged close to the resonance frequency of the LC resonance circuit. 8. The load is a discharge lamp, and the switching frequency of the switching element is set to be higher than the resonance frequency of the LC resonance circuit at least when the discharge lamp is faulty, and the switching of one of the series circuits is performed at the time of starting the discharge lamp. 3. The on / off timing of the switching element of the other series circuit is changed from the phase shifted by 180 degrees to the same phase with respect to the on / off timing of the element. Inverter device described. 9. The inverter device according to claim 1, wherein a plurality of loads are provided and an AC component and a DC component are separately supplied to each load.