JPH0851390A - Fm multiplex receiver of diversity system - Google Patents
Fm multiplex receiver of diversity systemInfo
- Publication number
- JPH0851390A JPH0851390A JP6187592A JP18759294A JPH0851390A JP H0851390 A JPH0851390 A JP H0851390A JP 6187592 A JP6187592 A JP 6187592A JP 18759294 A JP18759294 A JP 18759294A JP H0851390 A JPH0851390 A JP H0851390A
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- 238000001514 detection method Methods 0.000 claims description 16
- 238000010586 diagram Methods 0.000 description 12
- 238000007796 conventional method Methods 0.000 description 9
- 239000003990 capacitor Substances 0.000 description 8
- 238000006243 chemical reaction Methods 0.000 description 7
- 230000003321 amplification Effects 0.000 description 4
- 238000001914 filtration Methods 0.000 description 4
- 238000003199 nucleic acid amplification method Methods 0.000 description 4
- 230000007423 decrease Effects 0.000 description 2
- 230000005684 electric field Effects 0.000 description 2
- 238000005562 fading Methods 0.000 description 2
- 230000035945 sensitivity Effects 0.000 description 2
- 230000005236 sound signal Effects 0.000 description 2
- 239000004020 conductor Substances 0.000 description 1
- 235000019800 disodium phosphate Nutrition 0.000 description 1
- 239000005357 flat glass Substances 0.000 description 1
- 239000011521 glass Substances 0.000 description 1
- 230000012447 hatching Effects 0.000 description 1
- 230000002452 interceptive effect Effects 0.000 description 1
- 238000000034 method Methods 0.000 description 1
- 238000001228 spectrum Methods 0.000 description 1
- 230000007704 transition Effects 0.000 description 1
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Abstract
Description
【０００１】[0001]
【産業上の利用分野】本発明は、ダイバーシティ方式を
用いて、ＦＭ放送に多重されて送信される多重信号を受
信するダイバーシティ方式のＦＭ多重受信装置に関す
る。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a diversity type FM multiplex receiving apparatus which receives a multiplex signal multiplexed and transmitted in an FM broadcast by using the diversity type.
【０００２】[0002]
【従来の技術】ＦＭ多重放送は、ＶＨＦ帯のＦＭ放送に
図５の階層１に示すように、通常の放送番組用の信号に
斜線を施して示すデジタル信号による多重信号を付加
し、この多重信号によって種々の情報を伝達することが
できる。ここに紹介する１例のＦＭ多重放送では、ＯＳ
Ｉ(Open System Interconnection）参照モデルに従っ
て、階層１のフィジカル層の上に、階層２のリンク層、
階層３のネットワーク層、階層４のトランスポート層、
階層５のセッション層、階層６のプレゼンテーション層
および階層７のアプリケーション層がそれぞれ定められ
ている。階層１のフィジカル層としては、周波数スペク
トルが約７６ｋＨｚ±１０ｋＨｚで、１６ｋｂｉｔ／ｓ
のビットレートで、Ｌ−ＭＳＫ（Minimum Shift Keyin
g；最小推移キーイング）変調されて送信されることが
定められている。2. Description of the Related Art In FM multiplex broadcasting, as shown in layer 1 of FIG. 5, a multiplexed signal of a digital signal shown by hatching is added to a signal for a normal broadcast program, as shown in layer 1 of FIG. Various kinds of information can be transmitted by signals. In the example of FM multiplex broadcasting introduced here, the OS
According to the I (Open System Interconnection) reference model, on top of the physical layer of layer 1, the link layer of layer 2,
Layer 3 network layer, Layer 4 transport layer,
A layer 5 session layer, a layer 6 presentation layer, and a layer 7 application layer are defined. As the physical layer of layer 1, the frequency spectrum is about 76 kHz ± 10 kHz, and 16 kbit / s.
At the bit rate of L-MSK (Minimum Shift Keyin
g; minimum transition keying) It is specified that the data is modulated and transmitted.
【０００３】図６に従来技術を用いたＦＭ多重受信装置
のブロック図を示す。このＦＭ多重受信装置は、フェー
ジング現象などの影響が受けにくく、また車載用の受信
装置として好適なダイバーシティ方式が用いられてい
る。ダイバーシティ方式を用いた受信装置として、たと
えば車載用の受信装置として用いられるときには、車両
に搭載されるロッドアンテナや、後部窓ガラスに貼着さ
れた導電体から成るいわゆるガラスアンテナなどで実現
される複数のアンテナ５１，５２毎に受信手段としてチ
ューナ５３，５４を備える。このようなダイバーシティ
方式の受信装置は、車両の走行に伴う各アンテナ５１，
５２への入力感度、すなわち受信される電波の電界強度
の変化などに応じて、前記各アンテナ５１，５２の間に
電界強度の差がある場合、より良好な受信感度を得るた
めに、受信するアンテナ５１，５２を前記複数のチュー
ナ５３，５４間で切換える。FIG. 6 shows a block diagram of an FM multiplex receiver using a conventional technique. This FM multiplex receiver is not easily affected by a fading phenomenon, etc., and a diversity system suitable for an on-vehicle receiver is used. When used as a receiver using the diversity system, for example, as a vehicle-mounted receiver, it is realized by a plurality of rod antennas mounted on a vehicle, a so-called glass antenna made of a conductor attached to a rear window glass, or the like. Tuners 53 and 54 are provided as receiving means for each of the antennas 51 and 52. Such a diversity-type receiving device includes the antennas 51,
When there is a difference in the electric field strength between the antennas 51 and 52 according to the input sensitivity to 52, that is, the change in the electric field strength of the received radio wave, the reception is performed in order to obtain better reception sensitivity. The antennas 51 and 52 are switched between the plurality of tuners 53 and 54.
【０００４】図６（１）に示すように、アンテナ５１，
５２で受信された信号はそれぞれ別々に、チューナ５
３，５４に入力される。後述するようにチューナ５３，
５４でＦＭ復調された信号は、比較制御回路５５に入力
され、比較制御回路５５は受信状態が良好な信号を選択
し、切換スイッチ５６を切換制御する。オーディオ回路
５７およびデコーダ５８には、チューナ５３，５４のど
ちらか一方からの信号が選択されて入力される。オーデ
ィオ回路５７は、信号のうち通常の放送用の信号を音声
信号に変換し、スピーカ６２から音声として出力する。
デコーダ５８は信号のうち多重信号からデジタル信号を
復調し、そのデジタル信号をデータ処理回路５９に入力
する。データ処理回路５９は、操作手段６０から入力さ
れた命令に従ってデータを表示手段６１に表示する。As shown in FIG. 6A, the antennas 51,
The signals received at 52 are separately received by the tuner 5
3, 54. As will be described later, the tuner 53,
The signal demodulated by FM in 54 is input to the comparison control circuit 55, and the comparison control circuit 55 selects a signal in a good reception state and controls the changeover switch 56 to change over. A signal from one of the tuners 53 and 54 is selected and input to the audio circuit 57 and the decoder 58. The audio circuit 57 converts a normal broadcast signal out of the signals into an audio signal and outputs it as a sound from the speaker 62.
The decoder 58 demodulates a digital signal from the multiplexed signal among the signals and inputs the digital signal to the data processing circuit 59. The data processing circuit 59 displays the data on the display unit 61 in accordance with the instruction input from the operation unit 60.
【０００５】また図６（２）は、図６（１）のチューナ
５３，５４の簡略化した電気的構成を示す。アンテナ５
１または５２で受信された信号は、高周波増幅回路６３
（以後、ＲＦ回路と称する）に入力される。ＲＦ回路６
３に入力された信号は増幅され、周波数変換回路６４で
局部発振器６５から出力された信号と混合され、２つの
信号の差の周波数の信号が中間周波フィルタ（以後、Ｉ
Ｆフィルタと称する）６６に入力される。ＩＦフィルタ
６６はたとえばバンドパスフィルタなどから成り、特定
の範囲内にある周波数の信号を濾波する。ＩＦフィルタ
６６で濾波された信号は、アンプ６７で増幅され、ＦＭ
検波回路６８で復調され、比較制御回路５５および切換
スイッチ５６に出力される。Further, FIG. 6 (2) shows a simplified electrical configuration of the tuners 53, 54 of FIG. 6 (1). Antenna 5
The signal received at 1 or 52 is sent to the high frequency amplifier circuit 63.
(Hereinafter, referred to as RF circuit). RF circuit 6
The signal input to 3 is amplified and mixed with the signal output from the local oscillator 65 in the frequency conversion circuit 64, and the signal of the frequency of the difference between the two signals is output to the intermediate frequency filter (hereinafter, I
(Referred to as F filter) 66. The IF filter 66 is composed of, for example, a bandpass filter, and filters a signal having a frequency within a specific range. The signal filtered by the IF filter 66 is amplified by the amplifier 67 and
The signal is demodulated by the detection circuit 68 and output to the comparison control circuit 55 and the changeover switch 56.
【０００６】図７は、チューナ５３，５４の周波数特性
を示すグラフである。たとえば実線６９がチューナ５３
の出力を、１点破線７０がチューナ５４の出力をそれぞ
れ示している。チューナの出力レベル、位相などの周波
数特性はそれぞれ異なっており、その原因は特に各チュ
ーナ５３，５４内のＩＦフィルタ６６の濾波特性の違い
などにある。図７の領域ａはオーディオ信号の周波数帯
域を示し、領域ｂは多重信号の周波数帯域を示す。ＩＦ
フィルタ６６の濾波特性はＳ／Ｎ比や隣接妨害等を考慮
してある程度通過帯域となるように設定されており、そ
のカットオフ周波数が多重信号の周波数帯域である領域
ｂ内に位置することがある。このため２系統のチューナ
５３，５４の出力レベルや位相が領域ｂでは同一周波数
でも異なる。ダイバーシティ方式を用いて、受信状態に
よって２系統のチューナ５３，５４を切換えると、切換
わった瞬間の多重信号の検波出力波形のつながりが悪
く、その部分でデータエラーが発生する可能性がある。FIG. 7 is a graph showing frequency characteristics of the tuners 53 and 54. For example, the solid line 69 is the tuner 53
Of the tuner 54 is indicated by a dashed-dotted line 70. The frequency characteristics such as the output level and phase of the tuner are different from each other, and the cause is in particular the difference in the filtering characteristics of the IF filter 66 in the tuners 53 and 54. Region a in FIG. 7 shows the frequency band of the audio signal, and region b shows the frequency band of the multiplexed signal. IF
The filtering characteristic of the filter 66 is set so as to have a pass band to some extent in consideration of the S / N ratio, adjacent interference, etc., and its cutoff frequency may be located in the region b which is the frequency band of the multiplex signal. is there. Therefore, the output levels and phases of the two tuners 53, 54 are different even in the same frequency in the region b. If the tuners 53 and 54 of the two systems are switched according to the reception state by using the diversity system, the detection output waveform of the multiplexed signal at the moment of switching is poorly connected, and a data error may occur at that portion.
【０００７】ダイバーシティ方式の各チューナの位相を
揃える第１の従来技術としては、特開平４−２０７８２
１が挙げられる。図８は、本従来技術の簡略化した電気
的構成を示す。主アンテナ７１で受信された信号は周波
数変換回路７２で局部発振器７３からの信号と混合さ
れ、その出力信号がＩＦフィルタで濾波されて分配器７
４に入力される。分配器７４に入力された信号（以後、
主信号と称する）は２分配され、一方は自動利得制御増
幅器（以後、ＡＧＣ増幅器と称する）７５を通って位相
検波器７６で絶対位相が検出される。また第１，第２副
アンテナ７７，７８で受信した信号も、主信号と同様
に、周波数変換回路７９，８０で周波数変換された後、
その出力信号（以後、第１、第２副信号と称する）は無
限移相器（以後、ＥＰＳと称する）８１，８２、分配器
８３，８４およびＡＧＣ増幅器８５，８６を通って位相
検波器８７，８８に加えられて絶対位相がそれぞれ検出
される。As a first conventional technique for aligning the phase of each tuner of the diversity system, there is disclosed in Japanese Patent Laid-Open No. 20782/1992.
1 is mentioned. FIG. 8 shows a simplified electrical configuration of this prior art. The signal received by the main antenna 71 is mixed with the signal from the local oscillator 73 by the frequency conversion circuit 72, and the output signal thereof is filtered by the IF filter to be distributed to the distributor 7.
4 is input. The signal input to the distributor 74 (hereinafter,
The main signal) is divided into two, one of which passes through an automatic gain control amplifier (hereinafter referred to as an AGC amplifier) 75, and an absolute phase is detected by a phase detector 76. Further, the signals received by the first and second sub-antennas 77 and 78 are also frequency-converted by the frequency conversion circuits 79 and 80 in the same manner as the main signal, and then,
The output signal (hereinafter referred to as first and second sub-signals) passes through infinite phase shifters (hereinafter referred to as EPS) 81 and 82, distributors 83 and 84, and AGC amplifiers 85 and 86, and a phase detector 87. , 88 to detect the absolute phase, respectively.
【０００８】主信号と第１副信号の絶対位相はミキサ８
９に、主信号と第２副信号の絶対位相はミキサ９０にそ
れぞれ入力され、ここで主信号の位相を基準にして第１
および第２副信号の位相差を求め、対応する位相差信号
を制御部９１，９２に送出する。制御部９１，９２はこ
の位相差信号がたとえば０となるような無限移相器制御
信号（以後、ＥＰＳ制御信号と称する）を生成してＥＰ
Ｓ８１，８２に入力する。The absolute phase of the main signal and the first sub signal is the mixer 8
9, the absolute phase of the main signal and the absolute phase of the second sub-signal are respectively input to the mixer 90, where the first phase is based on the phase of the main signal.
Then, the phase difference between the second sub-signal is obtained, and the corresponding phase difference signal is sent to the control units 91 and 92. The control units 91 and 92 generate an infinite phase shifter control signal (hereinafter referred to as an EPS control signal) such that the phase difference signal becomes 0, for example.
Input in S81 and S82.
【０００９】そこで、ＥＰＳ８１，８２はＥＰＳ制御信
号に従って第１，第２副信号の位相を主信号と同相とな
るように調整しながら、主信号と第１，第２副信号とを
合成器９３で合成する。Therefore, the EPSs 81 and 82 adjust the phases of the first and second sub-signals to be in phase with the main signal in accordance with the EPS control signal, and combine the main signal with the first and second sub-signals 93. To synthesize.
【００１０】また第２の従来技術としては、特開平３−
９７３２４が挙げられる。図９は本従来技術の簡略化し
た構成を示す。主アンテナ１０１および副アンテナ１０
２で受信された信号は、周波数変換回路１０３，１０４
で局部発振器１０５からの信号と混合され、中間周波数
に変換される。主アンテナ１０１からの信号は、分配器
１０６を経て、振幅偏差検出器１０７へ入力される。振
幅偏差検出器１０７は、この信号について周波数ｆ-，
ｆ0，ｆ+ におけるレベルを検出してそれに比例した電
力を出力する。ここでｆ-，ｆ0，ｆ+ はたとえば受信帯
域でのそれぞれ最低、中心、最高周波数である。ＩＦフ
ィルタ１０８，１０９，１１０はそれぞれ中心周波数が
ｆ+，ｆ0，ｆ- であり、同様にＩＦフィルタ１１８，１
１９，１２０はそれぞれ中心周波数がｆ+，ｆ0，ｆ- で
ある。A second conventional technique is Japanese Patent Laid-Open No.
97324. FIG. 9 shows a simplified configuration of this prior art. Main antenna 101 and sub antenna 10
The signals received at 2 are frequency conversion circuits 103, 104.
Is mixed with the signal from the local oscillator 105 and converted into an intermediate frequency. The signal from the main antenna 101 is input to the amplitude deviation detector 107 via the distributor 106. The amplitude deviation detector 107 detects the frequency f − ,
The levels at f 0 and f + are detected and power proportional to that is output. Here, f − , f 0 , and f + are, for example, the lowest, center, and highest frequencies in the reception band, respectively. The center frequencies of the IF filters 108, 109 and 110 are f + , f 0 and f − , respectively.
The center frequencies of 19 and 120 are f + , f 0 , and f − , respectively.
【００１１】第２制御器１１１は振幅偏差検出器１０７
の出力電圧を比較し、それらのうちで最低レベルの出力
電圧となる周波数に相当するＩＦフィルタが選択される
ようにスイッチ１１２，１１３，１２１，１２２を制御
する。分配器１０６を経て、主アンテナ１０１からの信
号は３つのＩＦフィルタのうち選択された１つのＩＦフ
ィルタで濾波されて、可変利得アンプ１１４でレベル一
定に制御され、ミキサ１１５に供給される。副アンテナ
１０２からの信号は無限移相器１１６、分配器１１７を
経て３つのＩＦフィルタ１１８，１１９，１２０のうち
選択された１つのＩＦフィルタで濾波されて可変利得ア
ンプ１２３でレベル一定に制御され、ミキサ１１５に供
給される。ミキサ１１５では入力信号の乗算を行い、双
方の入力信号が同相であるときに出力が最大振幅とな
る。第１制御器１２４はミキサ１１５からの出力信号の
振幅が最大となるように、無限移相器１１６を制御し、
合成器１２５で２つの系統からの信号を合成して、同相
合成波を得る。The second controller 111 is an amplitude deviation detector 107.
The output voltages of the above are compared, and the switches 112, 113, 121, 122 are controlled so that the IF filter corresponding to the frequency having the lowest output voltage among them is selected. The signal from the main antenna 101 passes through the distributor 106, is filtered by one IF filter selected from the three IF filters, is controlled to a constant level by the variable gain amplifier 114, and is supplied to the mixer 115. The signal from the sub-antenna 102 is passed through the infinite phase shifter 116 and the distributor 117, filtered by one IF filter selected from the three IF filters 118, 119 and 120, and controlled by the variable gain amplifier 123 to a constant level. , To the mixer 115. The mixer 115 multiplies the input signals, and the output has the maximum amplitude when both input signals are in phase. The first controller 124 controls the infinite phase shifter 116 so that the amplitude of the output signal from the mixer 115 becomes maximum,
The combiner 125 combines the signals from the two systems to obtain an in-phase combined wave.
【００１２】さらにまた第３の従来技術としては、特開
昭５６−１３６０３９が挙げられる。図１０は本従来技
術の簡略化した電気的構成を示す。本従来技術では、主
アンテナ１３１で受信したい信号を、副アンテナ１３２
で干渉波源からの信号を、それぞれ受信している。副ア
ンテナ１３２で受信した信号（以後、副信号と称する）
は、振幅位相制御回路１３３に入力される。振幅位相制
御回路１３３はたとえばベクトル変調器で実現される。
前記振幅位相制御回路１３３に入力された副信号は、電
圧積算器１３４，１３５の出力と、低周波発振器１３６
の出力とを、加算器１３７，１３８で加算した出力電圧
によって、主アンテナ１３１で受信した信号と逆位相と
なるように制御され、合成器１３９で主アンテナで受信
した信号と合成される。なお、加算器１３８に与えられ
る低周波発振器１３６の出力は、９０°移相器１４５に
よって９０°の位相差が与えられている。合成された信
号は周波数変換回路１４０で中間周波数の信号に変換さ
れ、ＩＦフィルタ１４１で干渉波周波数成分のみを取出
され、アンプ１４２で適当なレベルに増幅された後、包
絡線検波器１４３に入力される。包絡線検波器１４３で
出力信号の振幅を検出し、アンプ１４４で適当なレベル
に増幅する。アンプ１４４の出力を、低周波発振器１３
６の出力およびこれに９０°移相器１４５によって９０
°の位相差を与えた信号によって位相検波器１４６，１
４７においてそれぞれ位相検波を行い、位相検波器１４
６，１４７の出力を電圧積算器１３４，１３５に入力す
る。この電圧積算器１３４，１３５の出力によって制御
された振幅位相制御回路１３３の出力によって、本従来
技術では干渉波を抑圧している。Further, as a third conventional technique, there is JP-A-56-136039. FIG. 10 shows a simplified electrical configuration of this prior art. In this conventional technique, a signal to be received by the main antenna 131 is transmitted to the sub antenna 132.
The signals from the interfering wave sources are respectively received at. A signal received by the sub antenna 132 (hereinafter referred to as a sub signal)
Is input to the amplitude / phase control circuit 133. The amplitude / phase control circuit 133 is realized by, for example, a vector modulator.
The sub-signal input to the amplitude / phase control circuit 133 is output from the voltage integrators 134 and 135 and the low frequency oscillator 136.
Is controlled by the output voltage added by the adders 137 and 138 so as to have a phase opposite to that of the signal received by the main antenna 131, and is combined with the signal received by the main antenna by the combiner 139. The output of the low-frequency oscillator 136 given to the adder 138 is given a 90 ° phase difference by the 90 ° phase shifter 145. The combined signal is converted into an intermediate frequency signal by the frequency conversion circuit 140, only the interference wave frequency component is extracted by the IF filter 141, amplified by the amplifier 142 to an appropriate level, and then input to the envelope detector 143. To be done. The envelope detector 143 detects the amplitude of the output signal, and the amplifier 144 amplifies it to an appropriate level. The output of the amplifier 144 is the low frequency oscillator 13
6 and the 90 ° phase shifter 145
The phase detectors 146, 1 by the signals given the phase difference of °
The phase detector 14 performs phase detection at 47 respectively.
The outputs of 6, 147 are input to the voltage integrators 134, 135. The output of the amplitude / phase control circuit 133 controlled by the outputs of the voltage integrators 134 and 135 suppresses the interference wave in the conventional technique.
【００１３】[0013]
【発明が解決しようとする課題】図６に示す従来技術で
は、２系統のチューナ５３，５４のＩＦフィルタ６６の
濾波特性の差異などに基づき、切換え時に波形のつなが
りが悪く、データエラーが出る可能性がある。In the prior art shown in FIG. 6, the waveform connection is poor at the time of switching and a data error may occur due to the difference in the filtering characteristics of the IF filters 66 of the two tuners 53 and 54. There is a nature.
【００１４】またダイバーシティ方式の受信についての
第１の従来技術では、受信装置が移動体に車載されるな
どして受信状態が変動するアンテナで受信した信号の位
相のみを補償するものであり、チューナ特性を補償する
ものではない。さらにまた第２の従来技術では、フェー
ジング等で特定の周波数のみのレベルが減少することを
補償し、第３の従来技術では副アンテナの出力によって
干渉波を排除するものである。これら従来技術は、ＩＦ
フィルタの濾波特性などに起因する多重信号についての
出力レベルまたは位相などの差を補償することはできな
い。In the first conventional technique for receiving the diversity method, the receiver compensates only the phase of the signal received by the antenna whose reception state varies due to the fact that the receiver is mounted on a mobile body. It does not compensate the characteristics. Furthermore, the second prior art compensates for the decrease in the level of only a specific frequency due to fading or the like, and the third prior art eliminates the interference wave by the output of the sub-antenna. These conventional techniques are
It is not possible to compensate for the difference in output level or phase for multiple signals due to the filtering characteristics of the filter or the like.
【００１５】本発明は、チューナの周波数特性に起因し
て、多重信号帯域に生じるチューナ間の特性の差異を調
整し、ダイバーシティ切換え時のデータエラー発生を防
ぐことのできるダイバーシティ方式のＦＭ多重受信装置
を提供することを目的とする。The present invention is a diversity type FM multiplex receiving apparatus capable of adjusting the characteristic difference between tuners caused in the multiple signal band due to the frequency characteristic of the tuner and preventing the occurrence of a data error at the time of diversity switching. The purpose is to provide.
【００１６】[0016]
【課題を解決するための手段】本発明は、複数系統のア
ンテナ入力からＦＭ検波出力までの受信手段を備え、各
受信手段からのＦＭ検波出力を比較して信号品質が良好
な系統の受信手段から受信信号を取出すように切換える
ダイバーシティ方式のＦＭ多重受信装置において、各系
統の受信手段間の周波数特性の差異を補償する補償手段
と、切換えて取出されたＦＭ検波出力から多重化された
デジタル信号を復調する復調手段とを含むことを特徴と
するダイバーシティ方式のＦＭ多重受信装置である。ま
た本発明は、前記補償手段は、１系統の受信手段を除い
て残余の系統の受信手段に個別的に挿入され、各補償手
段は、各系統の受信手段の周波数特性が、補償手段を挿
入しない前記１系統の受信手段の周波数特性と合致させ
られるように、補償対象となる特性を正および負の両方
向に調整可能であることを特徴とする。また本発明は、
２系統の受信手段と、補償対象となる特性を正または負
のいずれか一方向に調整可能な補償手段と、予め測定さ
れる各系統の受信手段の周波数特性に基づいて、周波数
特性間の差異を前記一方向の調整によって減少可能な方
の系統の受信手段に、前記補償手段を挿入するように切
換える切換手段とを含むことを特徴とする。SUMMARY OF THE INVENTION The present invention comprises receiving means from a plurality of systems of antenna inputs to FM detection outputs, and compares the FM detection outputs from the respective reception means with a receiving means of a system having good signal quality. In a diversity type FM multiplex receiving apparatus for switching so as to extract a received signal from a receiver, a compensating means for compensating for a difference in frequency characteristic between the receiving means of each system and a digital signal multiplexed from the FM detected output taken out by switching And a demodulation means for demodulating the signal. Further, in the present invention, the compensating means is individually inserted into the receiving means of the remaining system except for the receiving means of one system, and each compensating means has the frequency characteristic of the receiving means of each system inserted with the compensating means. The characteristic to be compensated can be adjusted in both the positive and negative directions so as to match the frequency characteristic of the receiving means of the one system. The present invention also provides
Based on the frequency characteristics of the receiving means of the two systems, the compensating means capable of adjusting the characteristic to be compensated in one direction, either positive or negative, and the frequency characteristics of the receiving means of each system measured in advance, the difference between the frequency characteristics Is included in the receiving means of the system that can be reduced by adjusting in one direction, and a switching means for switching the compensating means to be inserted.
【００１７】[0017]
【作用】本発明に従えば、ダイバーシティ方式のＦＭ多
重受信装置では複数系統のアンテナからＦＭ検波出力ま
での受信手段を備え、各受信手段からのＦＭ検波出力を
比較して信号品質が良好な１系統の受信手段から受信信
号を取出すように切換える。各系統の受信手段間の周波
数特性の差異を補償する補償手段と、切換えて取出され
たＦＭ検波出力から多重化されたデジタル信号を復調す
る復調手段とを備えているので、常により良好な信号を
入力することができ、また各系統の受信手段間の周波数
特性の差異を調整することができるとともに、ＦＭ放送
波に多重されて送信されたデータ信号を復調し、利用す
ることができる。According to the present invention, the diversity type FM multiplex receiver is provided with receiving means from the antennas of a plurality of systems to the FM detection output, and the FM detection outputs from the respective receiving means are compared to obtain a good signal quality. Switching is performed so that the reception signal is extracted from the reception means of the system. Since a compensating means for compensating for the difference in frequency characteristic between the receiving means of each system and a demodulating means for demodulating a multiplexed digital signal from the FM detection output picked up by switching are provided, a better signal is always provided. Can be input, the difference in frequency characteristics between the receiving means of each system can be adjusted, and the data signal multiplexed and transmitted with the FM broadcast wave can be demodulated and used.
【００１８】好ましくは前記補償手段は、１系統の受信
手段を除いて、残余の系統の受信手段に個別的に挿入さ
れる。各補償手段は各系統の受信手段の周波数特性を補
償手段を挿入しない前記１系統の受信手段の周波数特性
と合致するように、補償対象の特性を正または負の両方
向に調整することが可能なので、各受信手段の周波数特
性を揃えるのに必要な補償手段の数を減少させることが
できる。Preferably, the compensating means is individually inserted into the receiving means of the remaining system except for the receiving means of one system. Since each compensating means can adjust the characteristic to be compensated in both positive and negative directions so that the frequency characteristic of the receiving means of each system matches the frequency characteristic of the receiving means of the one system in which the compensating means is not inserted. It is possible to reduce the number of compensating means required to make the frequency characteristics of each receiving means uniform.
【００１９】また好ましくは、前記受信装置には、２系
統の受信手段と、補償対象の特性を正または負のいずれ
か一方向に調整可能な補償手段と、予め測定される各系
統の受信手段の周波数特性に基づいて、周波数特性間の
差異を前記一方向の調整によって減少可能な一方の系統
の受信手段に前記補償手段を挿入するように切換える切
換手段とを備えるので、能動素子を使わない簡単な補償
手段を用いることができるとともに、必要な補償手段の
数を減少させることができる。Further, preferably, in the receiving device, the receiving means of two systems, the compensating means capable of adjusting the characteristic to be compensated in one of positive and negative directions, and the receiving means of each system which is preliminarily measured. A switching means for switching the receiving means of one system so that the difference between the frequency characteristics can be reduced by adjusting in one direction based on the frequency characteristics of the switching means, the active element is not used. Simple compensating means can be used and the number of compensating means required can be reduced.
【００２０】[0020]
【実施例】図１は本発明の一実施例のＦＭ多重受信装置
のブロック図である。アンテナ１，２でそれぞれ受信さ
れた信号は、チューナ３，４に入力される。チューナ
３，４はたとえばスーパヘテロダイン方式が用いられ、
ＲＦ回路、周波数変換回路、局部発振器、ＩＦフィル
タ、アンプ、ＦＭ検波回路などから成り、図６（２）と
基本的に同等である。チューナ３，４に入力された信号
はＲＦ回路で増幅され、周波数変換回路で局部発振器か
らの出力信号と混合されて、２つの信号の差の周波数で
ある中間周波数の信号に変換される。この信号がＩＦフ
ィルタで濾波された後、アンプで増幅されて、ＦＭ検波
回路で復調されて出力される。チューナ３，４の出力信
号は、比較制御回路６に入力される。比較制御回路６
は、入力された２系統のチューナ３，４からの信号に基
づいて、Ｓ／Ｎ比やマルチパス歪みなどを検出し、受信
状態の良い方のチューナ３，４からの信号をオーディオ
回路などに出力するように、図示を省略する切換スイッ
チを切換制御する。1 is a block diagram of an FM multiplex receiver according to an embodiment of the present invention. The signals respectively received by the antennas 1 and 2 are input to the tuners 3 and 4. The tuners 3 and 4 use, for example, a superheterodyne system,
It is composed of an RF circuit, a frequency conversion circuit, a local oscillator, an IF filter, an amplifier, an FM detection circuit and the like, and is basically equivalent to FIG. The signals input to the tuners 3 and 4 are amplified by the RF circuit, mixed with the output signal from the local oscillator by the frequency conversion circuit, and converted into an intermediate frequency signal which is the difference frequency between the two signals. This signal is filtered by the IF filter, amplified by the amplifier, demodulated by the FM detection circuit, and output. The output signals of the tuners 3 and 4 are input to the comparison control circuit 6. Comparison control circuit 6
Detects the S / N ratio, multipath distortion, etc. based on the input signals from the two tuners 3 and 4 and outputs the signals from the tuners 3 and 4 with the better reception condition to the audio circuit or the like. A change-over switch (not shown) is controlled to change the output.
【００２１】チューナ３からの出力信号は、直接、切換
スイッチ７を介してデコーダ回路等に出力される。また
チューナ４からの出力信号は、補償回路５で信号の出力
レベルまたは位相などの周波数特性をチューナ３の周波
数特性に合わせるように調整されてから、切換スイッチ
７を介してデコーダ回路等に出力される。The output signal from the tuner 3 is directly output to the decoder circuit or the like via the changeover switch 7. The output signal from the tuner 4 is adjusted by the compensating circuit 5 so that the frequency characteristic such as the output level or phase of the signal matches the frequency characteristic of the tuner 3, and then output to the decoder circuit or the like via the changeover switch 7. It
【００２２】図２（１）は、図１の補償回路５の電気的
構成を示す回路図である。図１の補償回路５は、たとえ
ばオペアンプのような能動素子が用いられた回路となっ
ている。チューナ４からの信号を入力する入力端子は、
可変抵抗器Ｒ１の入力端子側に接続されている。可変抵
抗Ｒ１の可動片はコンデンサＣ１の一端に接続されてお
り、コンデンサＣ１の他端はオペアンプＯＰ１の反転入
力端子および可変抵抗器Ｒ１の中点に接続されている。
また、このオペアンプＯＰ１の非反転入力端子はアース
されている。オペアンプＯＰ１の出力端子と可変抵抗器
Ｒ１の出力端子側との接続点には抵抗Ｒ２の一端も接続
されている。抵抗Ｒ２の他端はオペアンプＯＰ２の反転
入力端子と抵抗Ｒ３の一端とに接続され、オペアンプＯ
Ｐ２の非反転入力端子はアースされている。オペアンプ
ＯＰ２の出力端子と抵抗Ｒ３の他端との接続点は、切換
スイッチ７への入力端子に接続される。また抵抗Ｒ２お
よび抵抗Ｒ３には抵抗値が等しいものが用いられてい
る。FIG. 2A is a circuit diagram showing an electrical configuration of the compensation circuit 5 of FIG. The compensation circuit 5 of FIG. 1 is a circuit using an active element such as an operational amplifier. The input terminal for inputting the signal from the tuner 4 is
It is connected to the input terminal side of the variable resistor R1. The movable piece of the variable resistor R1 is connected to one end of the capacitor C1, and the other end of the capacitor C1 is connected to the inverting input terminal of the operational amplifier OP1 and the midpoint of the variable resistor R1.
The non-inverting input terminal of the operational amplifier OP1 is grounded. One end of the resistor R2 is also connected to the connection point between the output terminal of the operational amplifier OP1 and the output terminal side of the variable resistor R1. The other end of the resistor R2 is connected to the inverting input terminal of the operational amplifier OP2 and one end of the resistor R3.
The non-inverting input terminal of P2 is grounded. The connection point between the output terminal of the operational amplifier OP2 and the other end of the resistor R3 is connected to the input terminal to the changeover switch 7. The resistors R2 and R3 having the same resistance value are used.
【００２３】図２（２）および図２（３）は補償回路５
の周波数特性を示すグラフである。補償回路５は、図２
（１）に示すように、たとえば能動回路を用いた低周波
増幅回路となっている。回路の増幅度が３ｄＢ低下する
カットオフ周波数ｆc はコンデンサＣ１の電気容量Ｃと
可変抵抗器Ｒ１の入力端子側と、出力端子側との間の抵
抗値の半分の抵抗値Ｒを用いて表すと、2 (2) and 2 (3) show a compensating circuit 5.
It is a graph which shows the frequency characteristic of. The compensation circuit 5 is shown in FIG.
As shown in (1), it is a low frequency amplifier circuit using an active circuit, for example. The cutoff frequency f c at which the amplification factor of the circuit decreases by 3 dB is expressed by using a resistance value R that is half the resistance value between the electric capacitance C of the capacitor C1 and the input terminal side of the variable resistor R1 and the output terminal side. When,
【００２４】[0024]
【数１】 [Equation 1]
【００２５】となる。コンデンサＣ１のリアクタンスが
抵抗値Ｒと同程度になるカットオフ周波数ｆc付近で
は、図２（２）および図２（３）に示すように、出力信
号のレベルおよび位相はそれぞれ変化する。[0025] In the vicinity of the cutoff frequency f c at which the reactance of the capacitor C1 becomes approximately the same as the resistance value R, the level and phase of the output signal change, as shown in FIGS. 2 (2) and 2 (3).
【００２６】すなわち、この回路の増幅度は、反転増幅
回路として、可変抵抗器Ｒ１の入力端子側の抵抗値Ｒl
と、出力端子側の抵抗値Ｒrとの比によって決定され
る。したがって、入力端子側の抵抗値Ｒlを出力端子側
の抵抗値Ｒrより小さく設定すると、増幅度は正方向に
増加するので、図２（２）の２点鎖線で示すような周波
数特性を示し、出力レベルは補償回路を挿入しない場合
よりも増加し、また出力信号の位相は図２（３）の２点
鎖線で示すように入力信号の位相よりも遅れる。逆に入
力信号側の抵抗値Ｒlを出力信号側の抵抗値Ｒrより大き
くすると、増幅度は負側に増加するので図２（２），
（３）の１点鎖線で示すような周波数特性を示し、出力
レベルを補償回路を挿入しない場合よりも減少し、また
出力信号の位相は入力信号の位相よりも進む。That is, the degree of amplification of this circuit is the resistance value R l on the input terminal side of the variable resistor R1 as an inverting amplifier circuit.
And the resistance value R r on the output terminal side. Therefore, when the resistance value R l on the input terminal side is set to be smaller than the resistance value R r on the output terminal side, the amplification degree increases in the positive direction. Therefore, the frequency characteristic shown by the chain double-dashed line in FIG. The output level increases as compared with the case where the compensation circuit is not inserted, and the phase of the output signal lags the phase of the input signal as indicated by the chain double-dashed line in FIG. Conversely, when the resistance value R l on the input signal side is made larger than the resistance value R r on the output signal side, the amplification degree increases to the negative side.
The frequency characteristic shown by the one-dot chain line in (3) is exhibited, the output level is reduced as compared with the case where the compensation circuit is not inserted, and the phase of the output signal leads the phase of the input signal.
【００２７】このようにして、補償回路５を２系統のチ
ューナのどちらか一方に予め組込むことによって、補償
回路５が組込まれたチューナ４の出力レベルまたは位相
などの周波数特性を補償回路が組込まれていないチュー
ナ３の周波数特性と一致するように正方向、負方向どち
らへも調整することができる。In this way, by preliminarily incorporating the compensating circuit 5 into either one of the two tuners, the compensating circuit is incorporated into the frequency characteristic such as the output level or phase of the tuner 4 incorporating the compensating circuit 5. It can be adjusted in both the positive and negative directions so as to match the frequency characteristic of the tuner 3 which is not provided.
【００２８】また本実施例では、能動素子を用いた回路
を用いたが、抵抗、コンデンサおよびコイルなどの受動
素子のみを用いた回路でもよく、またその他のＤＳＰな
どを用いた回路でもよい。さらに本実施例では可変抵抗
器Ｒ１が用いられているので、同一の構成の補償回路を
用いて、様々な周波数特性を持つチューナの出力信号を
調整することができる。In this embodiment, a circuit using active elements is used, but a circuit using only passive elements such as resistors, capacitors and coils may be used, or a circuit using other DSPs may be used. Further, since the variable resistor R1 is used in this embodiment, the output signals of the tuners having various frequency characteristics can be adjusted by using the compensating circuit having the same structure.
【００２９】図３は、本発明の他の実施例のＦＭ多重受
信装置のブロック図である。図１の実施例に対応する部
分には同一の符号を付し、説明は省略する。チューナ
３，４はディップスイッチまたはショート端子などで実
現される入替回路８に接続される。入替回路８は、２系
統のチューナのうちたとえば周波数特性の延びている一
方のチューナに補償回路５ａが挿入されるように接続を
切換える。補償回路５ａは、たとえば可変抵抗Ｒ４とコ
ンデンサＣ２とで構成されたローパスフィルタで実現さ
れ、周波数特性の延びている方のチューナの出力を抑え
る。FIG. 3 is a block diagram of an FM multiplex receiver according to another embodiment of the present invention. The parts corresponding to those in the embodiment of FIG. 1 are designated by the same reference numerals and the description thereof will be omitted. The tuners 3 and 4 are connected to a replacement circuit 8 realized by a DIP switch or a short terminal. The replacement circuit 8 switches the connection so that the compensation circuit 5a is inserted into, for example, one of the two tuners whose frequency characteristic is extended. The compensation circuit 5a is realized by, for example, a low-pass filter including a variable resistor R4 and a capacitor C2, and suppresses the output of the tuner having the extended frequency characteristic.
【００３０】図４は補償回路５ａを挿入したチューナ４
の周波数特性を示すグラフである。図４（１）は出力レ
ベル特性を示し、図４（２）は位相特性を示す。実線は
補償回路５ａを挿入する前のチューナ４の周波数特性を
示し、２点鎖線は補償回路５ａが挿入されたチューナ４
の周波数特性を示す。補償回路５ａで、可変抵抗器Ｒ４
の抵抗値をＲ4、コンデンサＣ２の容量をＣ2とすると、
補償回路５ａのカットオフ周波数は、FIG. 4 shows a tuner 4 having a compensation circuit 5a inserted therein.
It is a graph which shows the frequency characteristic of. 4 (1) shows the output level characteristic, and FIG. 4 (2) shows the phase characteristic. The solid line shows the frequency characteristic of the tuner 4 before the compensation circuit 5a is inserted, and the chain double-dashed line shows the tuner 4 with the compensation circuit 5a inserted.
Shows the frequency characteristics of. In the compensation circuit 5a, the variable resistor R4
Let the resistance value of R be R 4 and the capacitance of the capacitor C 2 be C 2 ,
The cutoff frequency of the compensation circuit 5a is
【００３１】[0031]
【数２】 [Equation 2]
【００３２】で表され、カットオフ周波数ｆより高い周
波数の信号は、図４（１）に示すように補償回路５ａを
通過すると出力レベルが減少する。また図４（２）に示
すように、補償回路５ａを通過する前の信号と、通過し
た後の信号との間には位相差が生じ、補償回路５ａを通
過した後の信号は補償回路５ａを通過する前の信号より
も位相が遅れている。A signal having a frequency higher than the cut-off frequency f is reduced in output level when passing through the compensation circuit 5a as shown in FIG. 4 (1). Further, as shown in FIG. 4B, a phase difference occurs between the signal before passing through the compensating circuit 5a and the signal after passing, and the signal after passing through the compensating circuit 5a is The phase is behind that of the signal before passing through.
【００３３】このような補償回路５ａを入替回路８によ
って周波数特性の延びている一方のチューナに挿入する
ことによって、位相または出力レベルなどの周波数特性
を抑え、補償回路が挿入されていないもう一方のチュー
ナの周波数特性と一致させることができる。また可変抵
抗Ｒ４の抵抗値Ｒ4が大きくなると、出力信号の出力レ
ベルまたは位相がより低く抑えられる。By inserting the compensating circuit 5a into one tuner whose frequency characteristic is extended by the replacing circuit 8, the frequency characteristic such as the phase or the output level is suppressed, and the other compensating circuit is not inserted. It can be matched with the frequency characteristic of the tuner. When the resistance value R 4 of the variable resistor R 4 increases, the output level or phase of the output signal can be suppressed to a lower level.
【００３４】また本実施例では抵抗とコンデンサを用い
た回路を用いたが、コイルと抵抗を用いた回路でもよ
く、またその他の回路を用いてもよい。Further, although the circuit using the resistor and the capacitor is used in this embodiment, a circuit using the coil and the resistor may be used, or another circuit may be used.
【００３５】さらに本実施例では補償回路５ａに可変抵
抗器が用いられているので、同一の構成の補償回路を用
いて、様々なチューナの周波数特性を任意に調整するこ
とができる。Further, in this embodiment, since the variable resistor is used for the compensation circuit 5a, the frequency characteristics of various tuners can be adjusted arbitrarily by using the compensation circuit having the same structure.
【００３６】[0036]
【発明の効果】以上のように本発明によれば、複数系統
のアンテナ入力からＦＭ検波出力までの受信手段を備
え、各受信手段からのＦＭ検波出力を比較して信号品質
が良好な１系統の受信手段からの受信信号を取出すよう
に切換えるダイバーシティ方式のＦＭ多重受信装置に、
各系統の受信手段間の周波数特性の差異を補償する補償
手段と、切換えて取出されたＦＭ検波出力から多重化さ
れたデジタル信号を復調する復調手段とを備えるので、
チューナを切換える際に各チューナの出力レベルまたは
位相などの周波数特性の違いによる多重信号のデータエ
ラーの発生を防ぐことができる。As described above, according to the present invention, there is provided a receiving means from a plurality of systems of antenna inputs to an FM detection output, and the FM detection outputs from the respective receiving means are compared to obtain one system having a good signal quality. To the FM multiplex receiver of the diversity system for switching so as to extract the reception signal from the reception means of
Since the compensating means for compensating the difference in the frequency characteristic between the receiving means of each system and the demodulating means for demodulating the multiplexed digital signal from the FM detection output picked up by switching are provided.
When the tuners are switched, it is possible to prevent the occurrence of a data error of the multiplexed signal due to the difference in frequency characteristics such as output level or phase of each tuner.
【００３７】好ましくは前記補償手段は、１系統の受信
手段を除いて残余の系統の受信手段に個別に挿入され、
各補償手段は各系統の受信手段の周波数特性を補償手段
を挿入しない前記１系統の受信手段の周波数特性と合致
するように補償対象の特性を正または負の両方向に調整
することが可能なので、必要な補償手段の数を減少させ
てコストを減少させることができる。Preferably, the compensating means is individually inserted into the receiving means of the remaining system except the receiving means of one system,
Since each compensating means can adjust the characteristic of the compensation target in both positive and negative directions so that the frequency characteristic of the receiving means of each system matches the frequency characteristic of the receiving means of the one system in which the compensating means is not inserted, The cost can be reduced by reducing the number of compensation measures required.
【００３８】また好ましくは、前記受信装置は２系統の
受信手段と、補償対象の特性を正または負のいずれか一
方に調整可能な補償手段と、予め測定される各系統の受
信手段の周波数特性に基づいて、周波数特性間の差異を
前記一方向の調整によって減少可能な方の系統の受信手
段に前記補償手段を挿入するように切換える切換手段と
を備えるので、能動素子を使わない簡単な補償手段を容
易に実現することができ、コストダウンを図ることがで
きる。Further, preferably, the receiving device has two systems of receiving means, a compensating means capable of adjusting the characteristic to be compensated to either positive or negative, and frequency characteristics of the receiving means of each system which are measured in advance. On the basis of the above, there is provided a switching means for switching so that the compensation means is inserted into the receiving means of the one system capable of reducing the difference between the frequency characteristics by the adjustment in the one direction, so that simple compensation without using an active element is provided. The means can be easily realized, and the cost can be reduced.
【図１】本発明の一実施例のＦＭ多重受信装置のブロッ
ク図である。FIG. 1 is a block diagram of an FM multiplex receiver according to an embodiment of the present invention.
【図２】図１の補償回路５の回路図および周波数特性を
示すグラフである。FIG. 2 is a circuit diagram of a compensation circuit 5 of FIG. 1 and a graph showing frequency characteristics.
【図３】本発明の他の実施例のＦＭ多重受信装置のブロ
ック図である。FIG. 3 is a block diagram of an FM multiplex receiving apparatus according to another embodiment of the present invention.
【図４】図３の補償回路５ａを挿入したチューナの周波
数特性を示すグラフである。FIG. 4 is a graph showing frequency characteristics of a tuner in which the compensation circuit 5a of FIG. 3 is inserted.
【図５】ＦＭ多重放送のプロトコルの階層構造を示す図
である。FIG. 5 is a diagram showing a hierarchical structure of an FM multiplex broadcasting protocol.
【図６】従来技術を用いたダイバーシティ方式ＦＭ多重
受信装置のブロック図である。FIG. 6 is a block diagram of a diversity type FM multiplex receiver using a conventional technique.
【図７】図６のチューナ５３，５４の周波数特性を示す
グラフである。7 is a graph showing frequency characteristics of tuners 53 and 54 of FIG.
【図８】従来技術を用いたダイバーシティ方式受信装置
のブロック図である。FIG. 8 is a block diagram of a diversity receiver according to the related art.
【図９】従来技術を用いたダイバーシティ方式受信装置
のブロック図である。FIG. 9 is a block diagram of a diversity receiver according to the related art.
【図１０】従来技術を用いたダイバーシティ方式受信装
置のブロック図である。FIG. 10 is a block diagram of a diversity receiver according to the related art.
１，２ アンテナ ３，４ チューナ ５，５ａ 補償回路 ６ 比較制御手段 ７ 切換スイッチ ８ 入替手段 1, 2 Antenna 3, 4 Tuner 5, 5a Compensation circuit 6 Comparison control means 7 Changeover switch 8 Replacement means
Claims (3)
力までの受信手段を備え、各受信手段からのＦＭ検波出
力を比較して信号品質が良好な系統の受信手段から受信
信号を取出すように切換えるダイバーシティ方式のＦＭ
多重受信装置において、 各系統の受信手段間の周波数特性の差異を補償する補償
手段と、 切換えて取出されたＦＭ検波出力から多重化されたデジ
タル信号を復調する復調手段とを含むことを特徴とする
ダイバーシティ方式のＦＭ多重受信装置。1. A reception means from a plurality of systems of antenna inputs to an FM detection output is provided, and FM detection outputs from the respective reception means are compared with each other so that the reception signal is switched from the reception means of a system having a good signal quality. Diversity FM
In the multiplex receiving device, a compensating means for compensating for a difference in frequency characteristic between the receiving means of each system, and a demodulating means for demodulating a multiplexed digital signal from the FM detection output taken out by switching are included. A diversity-type FM multiplex receiving device.
いて残余の系統の受信手段に個別的に挿入され、 各補償手段は、各系統の受信手段の周波数特性が、補償
手段を挿入しない前記１系統の受信手段の周波数特性と
合致させられるように、補償対象となる特性を正および
負の両方向に調整可能であることを特徴とする請求項１
記載のダイバーシティ方式のＦＭ多重受信装置。2. The compensating means is individually inserted into the receiving means of the remaining system except for the receiving means of one system, and each compensating means has the frequency characteristic of the receiving means of each system inserted with the compensating means. The characteristic to be compensated can be adjusted in both positive and negative directions so as to match the frequency characteristic of the receiving means of one system.
A diversity-type FM multiplex receiver described.
整可能な補償手段と、予め測定される各系統の受信手段
の周波数特性に基づいて、周波数特性間の差異を前記一
方向の調整によって減少可能な方の系統の受信手段に、
前記補償手段を挿入するように切換える切換手段とを含
むことを特徴とする請求項１記載のダイバーシティ方式
のＦＭ多重受信装置。3. A receiving means of two systems, a compensating means capable of adjusting a characteristic to be compensated in one of positive and negative directions, and frequency characteristics of the receiving means of each system which are measured in advance, In the receiving means of the system that can reduce the difference between the frequency characteristics by adjusting the one direction,
2. The diversity-type FM multiplex receiving apparatus according to claim 1, further comprising: switching means for switching to insert the compensating means.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP6187592A JPH0851390A (en) | 1994-08-09 | 1994-08-09 | Fm multiplex receiver of diversity system |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP6187592A JPH0851390A (en) | 1994-08-09 | 1994-08-09 | Fm multiplex receiver of diversity system |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPH0851390A true JPH0851390A (en) | 1996-02-20 |
Family
ID=16208811
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP6187592A Pending JPH0851390A (en) | 1994-08-09 | 1994-08-09 | Fm multiplex receiver of diversity system |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH0851390A (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005184534A (en) * | 2003-12-19 | 2005-07-07 | Fujitsu Ten Ltd | Reception apparatus, tuner and tuner management apparatus |
| JP2007189419A (en) * | 2006-01-12 | 2007-07-26 | Fujitsu Ten Ltd | Receiver, method and device for diagnosing abnormality thereof, and program |
| CN100382440C (en) * | 2004-11-22 | 2008-04-16 | Lg电子株式会社 | Apparatus and method for processing digital multimedia broadcast (DMB) signals |
-
1994
- 1994-08-09 JP JP6187592A patent/JPH0851390A/en active Pending
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005184534A (en) * | 2003-12-19 | 2005-07-07 | Fujitsu Ten Ltd | Reception apparatus, tuner and tuner management apparatus |
| CN100382440C (en) * | 2004-11-22 | 2008-04-16 | Lg电子株式会社 | Apparatus and method for processing digital multimedia broadcast (DMB) signals |
| JP2007189419A (en) * | 2006-01-12 | 2007-07-26 | Fujitsu Ten Ltd | Receiver, method and device for diagnosing abnormality thereof, and program |
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