EP0098801A2 - Ligne avec filtre passe-bas réparti - Google Patents

Ligne avec filtre passe-bas réparti Download PDF

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Publication number
EP0098801A2
EP0098801A2 EP83810289A EP83810289A EP0098801A2 EP 0098801 A2 EP0098801 A2 EP 0098801A2 EP 83810289 A EP83810289 A EP 83810289A EP 83810289 A EP83810289 A EP 83810289A EP 0098801 A2 EP0098801 A2 EP 0098801A2
Authority
EP
European Patent Office
Prior art keywords
line
wave impedance
line section
section
losses
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP83810289A
Other languages
German (de)
English (en)
Other versions
EP0098801B1 (fr
EP0098801A3 (en
Inventor
Jean-Joseph Max
Arvind Shah
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Feller AG
Original Assignee
Feller AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Feller AG filed Critical Feller AG
Priority to AT83810289T priority Critical patent/ATE24983T1/de
Publication of EP0098801A2 publication Critical patent/EP0098801A2/fr
Publication of EP0098801A3 publication Critical patent/EP0098801A3/de
Application granted granted Critical
Publication of EP0098801B1 publication Critical patent/EP0098801B1/fr
Expired legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/202—Coaxial filters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01B—CABLES; CONDUCTORS; INSULATORS; SELECTION OF MATERIALS FOR THEIR CONDUCTIVE, INSULATING OR DIELECTRIC PROPERTIES
    • H01B11/00—Communication cables or conductors
    • H01B11/02—Cables with twisted pairs or quads
    • H01B11/12—Arrangements for exhibiting specific transmission characteristics
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01B—CABLES; CONDUCTORS; INSULATORS; SELECTION OF MATERIALS FOR THEIR CONDUCTIVE, INSULATING OR DIELECTRIC PROPERTIES
    • H01B11/00—Communication cables or conductors
    • H01B11/18—Coaxial cables; Analogous cables having more than one inner conductor within a common outer conductor
    • H01B11/1895—Particular features or applications

Definitions

  • the invention relates to an electrical line with at least one distributed low-pass filter for suppressing high-frequency interference signals on the line.
  • DE-OS 29 39 616 describes a lossy electrical cable in which at least one conductive element in connection with an absorbent mixture at least partially surrounding the conductor has a composite structure, namely a core formed by a thread or a fiber and one conductive coating, such that the element has a high resistance with good mechanical properties.
  • the known distributed low-pass or interference protection filters have the disadvantages that they have to be subject to high magnetic losses, dielectric losses or line losses in the insulating material, since such losses only their low-pass effect and that they have a complicated structure that not only complicates their manufacture, but also their universal applicability.
  • the object of the present invention is to provide an electrical line of the type mentioned at the beginning, the distributed low-pass filter of which has a low cut-off frequency and, for signal frequencies up to the highest frequency range, high attenuation without noticeable resonance phenomena, and with a simple structure, neither on the use of materials with high loss factors is still dependent on great lengths.
  • a comparatively low cut-off frequency of the low-pass filter and at the same time high frequencies of resonances, in particular the lowest of the occurring resonances can be achieved.
  • a line with a line section, or, to increase the interference filter effect, with several successive line sections of different impedance and higher dielectric losses or skin effect losses can be produced in a relatively simple manner and practically any length, so that the present line as an interference filter, which allows low-frequency or direct-current electrical current to pass through without noticeable damping, but has high damping for high-frequency currents and can be used universally.
  • the line 1 shows schematically a coaxial line 1, which in a manner known per se has a conductor 2, an outer shield 3 and an insulating material or dielectric 4, not shown, located between the conductor 2 and the outer shield 3.
  • the line 1 has a first and a third line section 5 and 6, both of which have as characteristic data an impedance Z 0 and a loss factor tg ⁇ 0 , which in the present example is zero (less loss Line section).
  • a line section 7 is provided, the impedance of which is Z 1 and very different from Z, which has a relative dielectric constant ⁇ r and a loss factor tg ⁇ 1 , and whose length is equal to L.
  • a signal 8 which is shown in FIG. 1 for example as a unit voltage jump signal and which propagates in line section 5 of impedance Z 0 , reaches point A of line 1, namely the beginning of line section 7, at which whose impedance suddenly takes the value Z 1 , part of the signal is reflected, while the other part propagates in line section 7.
  • point B of line 1 namely the end of line section 7, at which the impedance suddenly takes on the value Z 0
  • the reflected part of the signal which preferably makes up almost all of the remaining signal, is sent back to point A, where again a nearly total reflection occurs.
  • a multiple Re thus takes place in the line section 7, which has a different impedance than the adjacent line sections 5 and 6 flexion of the signal components, as shown in Fig. 2 in more detail.
  • This low-pass effect is based on the fact that not only a small part of the unit step signal 8 entering the line section 7 with different impedance has to go back and forth several times over this line section before it can build up a noticeable voltage at the output of the line section 7, but that the effect of the dielectric losses in this line section can also be increased because the "equivalent length" of the line section is multiplied by a factor which is essentially inversely proportional to the very small deviation of the reflection factor from 1.
  • This equivalent length is defined than the mean path length that a pulse-shaped wave has to travel through on the same line section when it goes back and forth several times until half of it comes out of the line section in question.
  • FIG. 4 shows the calculated and experimentally confirmed course of the filter attenuation for a line according to FIG. 1, the attenuation A being plotted in dB and the frequency f with respect to the cutoff frequency f 3dB for a 3 dB attenuation on a logarithmic scale.
  • the delay T d L / v, the product of the length L of the line section 7 and the inverse reproductive speed 1 / v in this section.
  • the reflections caused by the different impedance in the conductor section 7 determine the filter steepness and, as will be explained below, the cut-off frequency of the low-pass filter, while the dielectric losses of the line section 7 increase the frequency with an extinction or at least a strong attenuation of the resonances caused by the reflections and then a stronger weakening in the direction of higher frequencies is effected.
  • the reflection factor ⁇ depends on the one hand on a change in the dielectric constant ⁇ r and on the other hand on a change in the geometry of the line at the ends of the line section 7. Since the dielectric constant can be changed only to a relatively small extent due to the material, it is advantageous to bring about a considerable increase in the ratio of the frequency f rn of the first resonance to the cut-off frequency f 3dB in that the length L of the line section two other dimensions, ie the transverse dimensions, are changed, for example the diameter in the case of a cable-shaped line.
  • the entire line 1, ie also in line sections 5 and 6, can have the same loss angle tg ⁇ .
  • Suitable insulating materials for the lossy line section 7 with different impedance Z 1 for example, polyethylene with tg ⁇ between 0.02 and 0.2 or polyvinylidene fluoride (PVDF) with tg 6 between 0.1 and 0.2 in the frequency range from 0.5 to 200 MHz.
  • PVDF polyvinylidene fluoride
  • the line 1 shown only schematically in FIG. 1 can have different embodiments, three examples of which are shown in FIGS. 5, 6 and 7. In the cut views, only one of the line sections 5, 6 and 7 of FIG. 1 is shown.
  • FIG. 5 shows a two-wire line with two conductors 15, each of which is surrounded by an insulating material 16 of a certain diameter and certain dielectric properties.
  • a separate metallic shield 17 envelops each insulating material 16.
  • a plastic protective jacket 18 is provided.
  • 6 shows a similar arrangement with three conductors 15, but in which a shield 19 for the three insulating materials 16 of all three conductors 15 is common.
  • the embodiment according to FIG. 5 is also suitable for applications as an anti-parasitic signal or data line, while the embodiment according to FIG. 6 is also particularly suitable for use as an anti-parasitic mains cable for building and house installations.
  • the present line can also have the embodiment of a current or distribution rail for the supply inside or outside electrical and electronic devices, as shown in FIG. 7.
  • Two busbars 20, which are provided with connecting lugs 21, are embedded in an insulating material 22 of certain dimensions and certain dielectric properties.
  • the insulating material 22 is enclosed by a shielding metal housing 23 which is open on the underside and which is provided with a larger number of connecting lugs 24 and is surrounded by a plastic protective jacket 25.
  • the lengths L I to L 4 can, however, differ from one another in order to avoid any cumbersome accumulation of minor interfering effects of the reflections.
  • the lengths L 1 to L 4 as well as the length L according to FIG. 1 can have values between approximately 1 cm and 500 cm, so that in the case of small lengths, the present line also has the form of a discrete interference filter component for electrical and electronic devices, eg for mounting on a circuit board.
  • the distributed low-pass filter is effective, i.e. at any frequency, has uniformly distributed impedances and loss elements along the line sections, but no discrete elements. If you look at the behavior of any electrical component towards very fast pulses or high frequencies, you can see that in the sense of the word "discrete" circuit elements such as inductors and capacitors no longer exist, but that it only has elements that are distributed in a regular or irregular manner .
  • the damping curve of this arrangement must be for the higher frequencies to be damped under the face be considered that the inductors are distributed elements, the impedance of which is a function of the coordinate between a starting point and the end of the inductor.
  • an approximation of such an impedance can be obtained by taking only the average value, which is called the equivalent wave impedance.
  • the arrangement mentioned thus represents a line which has a first line section with an equivalent wave impedance Z eq , a second line section with a wave impedance Z eq and a third line section with an equivalent wave impedance Z eq .
  • FIG. 9 shows an exemplary embodiment of the electrical line according to the invention, in which one line section has a discrete inductance 31, a second line section is formed by a coaxial cable 32 and a third line section has a further discrete inductance 33, the second line section having a wave impedance Z and the adjacent line sections have equivalent wave impedances Z eq and Z ' eq different from Z.
  • FIG. 10a shows a similar design of a line, but in which the corresponding third line section has a capacitor 34.
  • this configuration corresponds to the line shown in FIG. 10b, the line sections of which have the equivalent wave impedance Z eq (L), the wave impedance Z and the equivalent wave impedance Z a q (C).
  • the capacitor 34 plays the same role as an open stub.
  • the entire line can consist of several, alternately successive line sections of the type described.
  • the known skin effect which is effective at higher frequencies, can be used to generate losses in a simple manner, which strongly dampen the resonances occurring as a result of the signal reflections and also effect the desired filter attenuation of the present line for the maximum frequency range (FIG. 4).
  • the measure for generating frequency-dependent losses due to the skin effect is that the conductor of the line has an inner conductor part (or a core) with high electrical conductivity in order to transmit the relatively low frequencies up to a few thousand hertz including the direct current without loss.
  • the inner conductor part has a coating or a surface layer which has a lower electrical conductivity or is even semiconducting, in which the currents of higher frequency flow due to the skin effect. Since this coating is a poor conductor, the current-conducting layer or Skin at higher and very high frequencies is even thinner than with a conductor made entirely of a highly conductive material, so that the power line is further deteriorated, ie the losses that occur as a result of the skin effect are considerably greater.
  • Dielectric losses increase in proportion to the frequency, but losses due to the skin effect only increase with the square root of the frequency.
  • the aforementioned coating can have a significantly lower electrical conductivity than, for example, copper, the skin effect losses which can be achieved are sufficient to obtain the desired filter damping.
  • An inner conductor part 35 consists of an electrically highly conductive material, for example copper with a specific electrical resistance of 1.7 ⁇ .cm.
  • the inner conductor part 35 has a thin surface layer 36 made of a poorly conducting metal, for example
  • the surface layer can also consist of a semiconducting material, preferably of copper (I) oxide Cu 2 O.
  • a layer 37 of an insulating material adjoins the surface layer 36, which in turn is encased by an outer conductor provided as a shield with high electrical conductivity, for example also made of copper.
  • This simple design of the line maintains the properties of the central conductor, which conducts the signals of relatively low frequencies, while at the same time strongly attenuating the signals of higher and highest frequencies.
  • the inner conductor part 35 can also be provided with a plurality of outer, thin layers of a poorly conducting material lying on top of one another, the specific resistance of the layers increasing towards the outside. This ensures that the current penetrates into the poorly conducting outer conductor part at high frequencies.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Filters And Equalizers (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Burglar Alarm Systems (AREA)
  • Networks Using Active Elements (AREA)
EP83810289A 1982-07-01 1983-06-29 Ligne avec filtre passe-bas réparti Expired EP0098801B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT83810289T ATE24983T1 (de) 1982-07-01 1983-06-29 Leitung mit verteiltem tiefpassfilter.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CH4021/82A CH656738A5 (de) 1982-07-01 1982-07-01 Leitung mit verteiltem tiefpassfilter.
CH4021/82 1982-07-01

Publications (3)

Publication Number Publication Date
EP0098801A2 true EP0098801A2 (fr) 1984-01-18
EP0098801A3 EP0098801A3 (en) 1984-07-18
EP0098801B1 EP0098801B1 (fr) 1987-01-14

Family

ID=4268337

Family Applications (1)

Application Number Title Priority Date Filing Date
EP83810289A Expired EP0098801B1 (fr) 1982-07-01 1983-06-29 Ligne avec filtre passe-bas réparti

Country Status (5)

Country Link
US (1) US4683450A (fr)
EP (1) EP0098801B1 (fr)
AT (1) ATE24983T1 (fr)
CH (1) CH656738A5 (fr)
DE (1) DE3369228D1 (fr)

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US4813047A (en) * 1987-10-05 1989-03-14 General Electric Company High frequency signal driver for a laser diode and method of forming same
US4849981A (en) * 1987-10-05 1989-07-18 General Electric Company High frequency signal driver for a laser diode and method of forming same
DE3932846A1 (de) * 1989-10-02 1991-04-11 Holger Dipl Ing Altmaier Stoerschutzfilter
US5142252A (en) * 1990-10-24 1992-08-25 Brisson Bruce A Audio signal transmission line with a low pass filter
EP1236247B1 (fr) 1999-12-08 2006-09-06 Current Communications International Holding GmbH Dispositif de transmission d'informations par un reseau d'alimentation basse tension
US7176786B2 (en) * 2000-01-20 2007-02-13 Current Technologies, Llc Method of isolating data in a power line communications network
WO2001054297A1 (fr) 2000-01-20 2001-07-26 Current Technologies, Llc Procede d'isolation de donnees dans un reseau de communications a ligne electrique
US7103240B2 (en) 2001-02-14 2006-09-05 Current Technologies, Llc Method and apparatus for providing inductive coupling and decoupling of high-frequency, high-bandwidth data signals directly on and off of a high voltage power line
US6998962B2 (en) 2000-04-14 2006-02-14 Current Technologies, Llc Power line communication apparatus and method of using the same
US6965302B2 (en) 2000-04-14 2005-11-15 Current Technologies, Llc Power line communication system and method of using the same
BR0110299A (pt) 2000-04-14 2005-08-02 Current Tech Llc Comunicações digitais utilizando linhas de distribuição de energia de média voltagem
US6621373B1 (en) * 2000-05-26 2003-09-16 Rambus Inc. Apparatus and method for utilizing a lossy dielectric substrate in a high speed digital system
US6980089B1 (en) * 2000-08-09 2005-12-27 Current Technologies, Llc Non-intrusive coupling to shielded power cable
EP1371219A4 (fr) 2001-02-14 2006-06-21 Current Tech Llc Communication de donnees par ligne electrique
US7053756B2 (en) 2001-12-21 2006-05-30 Current Technologies, Llc Facilitating communication of data signals on electric power systems
US7199699B1 (en) 2002-02-19 2007-04-03 Current Technologies, Llc Facilitating communication with power line communication devices
JP3756129B2 (ja) * 2002-06-11 2006-03-15 Ｎｅｃトーキン株式会社 伝送線路型ノイズフィルタ
US7102478B2 (en) 2002-06-21 2006-09-05 Current Technologies, Llc Power line coupling device and method of using the same
US6982611B2 (en) 2002-06-24 2006-01-03 Current Technologies, Llc Power line coupling device and method of using the same
US7132819B1 (en) 2002-11-12 2006-11-07 Current Technologies, Llc Floating power supply and method of using the same
US7076378B1 (en) 2002-11-13 2006-07-11 Current Technologies, Llc Device and method for providing power line characteristics and diagnostics
US7064654B2 (en) 2002-12-10 2006-06-20 Current Technologies, Llc Power line communication system and method of operating the same
US6980090B2 (en) 2002-12-10 2005-12-27 Current Technologies, Llc Device and method for coupling with electrical distribution network infrastructure to provide communications
US6965303B2 (en) 2002-12-10 2005-11-15 Current Technologies, Llc Power line communication system and method
US6980091B2 (en) 2002-12-10 2005-12-27 Current Technologies, Llc Power line communication system and method of operating the same
US7075414B2 (en) 2003-05-13 2006-07-11 Current Technologies, Llc Device and method for communicating data signals through multiple power line conductors
US7046124B2 (en) 2003-01-21 2006-05-16 Current Technologies, Llc Power line coupling device and method of using the same
US7308103B2 (en) 2003-05-08 2007-12-11 Current Technologies, Llc Power line communication device and method of using the same
US7460467B1 (en) 2003-07-23 2008-12-02 Current Technologies, Llc Voice-over-IP network test device and method
US7113134B1 (en) 2004-03-12 2006-09-26 Current Technologies, Llc Transformer antenna device and method of using the same
JP2006279462A (ja) * 2005-03-29 2006-10-12 Hitachi Metals Ltd 電気的雑音フィルタ及び電気的雑音除去方法
US7714682B2 (en) * 2007-06-21 2010-05-11 Current Technologies, Llc Power line data signal attenuation device and method
TWI381575B (zh) * 2008-12-19 2013-01-01 Askey Computer Corp 用於傳輸高頻訊號之載體及載體佈線方法

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Also Published As

Publication number Publication date
ATE24983T1 (de) 1987-01-15
EP0098801B1 (fr) 1987-01-14
DE3369228D1 (en) 1987-02-19
CH656738A5 (de) 1986-07-15
EP0098801A3 (en) 1984-07-18
US4683450A (en) 1987-07-28

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