JPS5963976A - Controlling method for rectifier - Google Patents

Abstract

PURPOSE:To reduce the harmonic component of a polyphase AC input current and to obtain a constant DC output having small ripple by controlling the conducting time of switching elements by a specific method so that the polyphase AC input current flows in the sinusoidal waveform. CONSTITUTION:A 3-phase AC input is applied through inductors Lu-Lw, capacitors, Cu-Cw and rectifiers Rec1-Rec3 to converters G1-G3, and the outputs are applied through smoothing circuits to a load F. Switching transistors Q1, Q'1 in the converters G1-G3 are respectively switched in high conversion frequency by the frequency of 3-phase AC. The energy produced at the output side at every period of the conversion frequency is controlled to be proportional to the product of the square of the 3-phase AC and the control amount, and proportional in the total energy produced from the respective phases to the control amount.

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention provides multiple a5! AC-
Regarding DC conversion.

For example, if you want to obtain a desired DC voltage of I from a commercial three-phase AC input, a typical switching mode rectifier is the one shown in Figure 1. This conventional rectifier consists of an inductor Lu%Lv%LW connected in a box row to each 6-phase AC input terminal, and 6 rectifiers D to D6, and performs full-wave rectification of the 3-phase AC input. A 6-phase full-wave rectifier circuit 1ec1, a smoothing circuit t that smoothes the output of this 6-phase full-wave rectifier circuit, and an inductor Ll that constitutes the circuit.
and a switching transistor Ql connected in series with each other via a capacitor C1 and a primary winding Nlf of a transformer T.
s Ql % diodes D7 and D8 which flow the energy in the transformer to the capacitor C1, rectifier D9 which rectifies the voltage of the secondary winding N2 of the transformer T, and a flywheel diode DIO-. Output filter circuit 4:'
: Inductor L2 and capacitor C2, output statement 1:, 1 child 0.0' and output, :i, 1 child O10'
The switching transistors Ql and Q! are connected to keep the DC output surface and pressure constant between them. , a control circuit C that controls the pulse width of
It consists of on.

In such a conventional rectifier, the 6-phase main + jiu input is rectified by the 3-phase full-wave j straw flow circuit Ree1, and then converted into a flat-groove one-section flow by the flat rI1 circuit consisting of the inductor Ll and the capacitor C1. , is provided in the rectifier circuit Ree1, which contains many harmonic components, at the 1c point where each phase t pulse-like current flows through the diode of the phase with the highest voltage.
Even if the inductor ulLvlLwt is used, at least the low-order convex V,'] wave component cannot be removed. These harmonic components are extremely powerful and cause induction disturbances in the communication circuit, causing it to malfunction.
It also has a negative impact on the surrounding I pots, and the 11C power loss of the multi-phase current power supply is large, and in combination with a generator, the capacity Kl is large due to the increased power loss of the generator, etc. 'ic
4 (3 meters).Also, there is a drawback that a smoothing inductor L1 and a capacitor C1 are required.

Non-invention eliminates these conventional drawbacks,
Based on the knowledge that the instantaneous value of the energy flow is constant at the input side of the symmetrical multiphase current and the two-phase six-green type and its DC output side with a constant negative direction, the polyphase AC input current is sinusoidal. By controlling the interpolation period fr% of each switching element so that the current flows in a waveform of 11) It is characterized by being able to do things.

In a symmetric n-phase multi-flow device (n≧6) with symmetric loads, the input 1i1! The voltage vj of l at Ilt'j is Vj-
JFvmSin (ωL −2π(j, −1)/n)
・・・Represented by haze. However, j=1.2.6,...
. . . n1■ is the effective value of the input voltage vj.

Here, if the load connected between each phase is a resistive load having a resistance value R, then the electric power Pi supplied to the input section is as follows.

This equation 6) shows that the energy flowing in the symmetrical n4 ('AC device 4) is one foot. Therefore, from this, if a constant energy is drawn to the DC output side by 1%, the input f11) has a sine Since the wave-like poly(() AC input 12I and current flow i), it is possible to completely reduce the high hτ: wave component.

Also, a certain amount of energy is extracted from the DC output side.

From the above equation, it is sufficient to extract the energy proportional to the square of the instantaneous voltage value of each phase at each point in time of the multiphase or current input.

The present invention provides a concrete AC-DC conversion that applies J and Ij based on the above-mentioned fc-like knowledge.

DESCRIPTION OF THE PREFERRED EMBODIMENTS Each embodiment of A C-DC conversion according to the present invention will be described in detail below with reference to the drawings.

First, an embodiment of the present invention will be explained with reference to FIGS. 2 to 5. FIG.

The main circuit of the rectifier shown in Figure 2 consists of three-phase AC inputs, one
0 U%v1W inductor Lu% Lv%LW% connected in series to each line, capacitor M-phase full-wave rectifier R, capacitor C', Ree2, Itee3, a pair of switching transistors Ql and Ql that perform switching operations simultaneously, primary winding LAN and secondary winding N2
a transformer T and a switching transistor Q1 having
and a diode D for discharging the excitation energy etc. stored in the transformer T via the capacitor Cf when the transformer T is turned off. G2, G3.6 (connected to combine the outputs of 4 parts in parallel; 7C rectifier D9, D9, D9, flywheeling diode j-) 10-smoothing circuit mk
Root InP! l'L2, i, g and': 1777
Consisting of V2, L:2, and capacitor C3, its output) "j"21 is connected to negative <::j F? It is.

In the table for this fire h', Q +1, ゛・current value (;m is each (1) old voltage total ≦ current rectifier circuit and change L':S f;
It is not a bad idea to install a smoothing circuit for the input h' and 1 wave between the
The switching operation of each switching transistor Q1 and Q1' is adjusted to N using a completely new control method described later.
, i+, by switching the sinusoidal voltage applied to the input terminal, the high i and jlt wave components at the input terminal are significantly reduced, and the ripple (1) is stabilized at a low level and waits for a 7C DC output. be.

FIG. 6 shows an example of the block construction of the control 311 circuit that performs this control method, FIG. 4 shows the timing of each part's operation, and FIG. (a), 03
) are diagrams for explaining the output waveforms of the converting section, respectively. , in FIG. 3, a convex j%'4 (i'f oscillator oscillator generates a basic pulse signal sound with a frequency sufficiently higher than the J,'d wave number of the single-phase current input, for example, 201 Gfz.

This reference pulse signal is o;7. This can be seen by the ∆ No. a generated at time t. At the rising edge of this (j number a), the reset pulse forming circuit 2 generates a predetermined pulse '+'1M.
, for example, generates a reset pulse of 1 .mu.sec pulse Ii'+if. Kono reset pulse t! The voltage is applied to the gate of the reset FET 6 through the OR circuit 5, and this FET 6
The capacitor 7 is turned on by that pulse width to discharge the charge of the capacitor 7 to almost zero. The delay circuit 3 is connected to the switching transistor Q from the falling edge of the reset pulse.
The time t is delayed by a time equal to the carrier accumulation time of □', and the time t is delayed by a time τ from the carrier signal 4'ja''.
2, an on signal is given to the drive latch circuit 4. Accordingly, the drive latch circuit 4 performs switching of the first converter G1)>transistor. Drive signal s to the base of 11Q1'
1 and turns on as shown by signal d.

Capacitor 7 connected in parallel to FET 6 increases error by +1
The constant current value is controlled by the error signal from the injury device 8, and the constant current from the controllable constant current source 9 is used for charging. As the error increases, the error signal output by the S generator 8 depends on the difference between the detection signal Sd, which is proportional to the DC output voltage at the rectifier K iR', and the base value. Therefore, the charging pressure of the capacitor 7 is reduced to the reference signal a (by the reset pulse that is applied, li'+: is lowered to about 5D value, and then the Gii control cycle is performed.
In this real crab H1, 1: Output (j5 pressure detection number Sd
(increases in proportion to the difference from the standard value)

Is Ichigo Yapacita 7's charge:j each comparison? ,'ir
10, 10', 10'' positive) lil'' is applied to the 4 children. Compared to these, each fish boat of elephant "r:) has a total of 5 waves.
Irj flow side terminal of 11', 11'' and resistor 1
2.12' and 12'' are respectively J:'A <, ', ;include t1
2. A 1:L voltage proportional to the phase-to-phase voltage of the three-phase AC input between Q:t3 and terminals 13 and 14 of the full-wave rectifier 11 is applied to the AC-side terminal 16 of the full-wave rectifier 11'. ', 14' has a voltage proportional to the v-w interphase voltage trap, and a full-wave 8. >AC f!!L terminal 13" of flow vessel 11", W between 1-4"
Since a voltage proportional to the U phase-to-phase try and voltage is applied to each, the negative lX1li terminal of the comparator 10 has a U
- A sinusoidal voltage obtained by full-wave rectification of the alternating current voltage between the -W phases appears, and at the same time, the negative terminals of the comparators 10' and 10"+7) respectively have a 9 current voltage between V - W 411, and ~V- A sine wave shaped voltage is applied between the U phases with AC voltages b and \.The respective ratios 1o, 10', 10'' are positive and negative D.
The aforementioned voltages applied to the terminal are compared, and when the voltage at the positive terminal becomes equal to the voltage at the negative terminal, an off signal δ is output. The off signal C of the comparator 10 is at time t3.
The lff1 fiI signal is input to the latch circuit 4, and accordingly, the I-flip jitch circuit 4 stops supplying the base drive signal S1 to the switching transistors Q and Q' in the conversion section G1.

Therefore, transistor Q, Q0' is 13 in FIG.
As shown by number d, it turns off at time t4 after the accumulation time has passed 0'7C.

Next, the output signal 9 from the comparator 10 is the same as the circuit 2 at $1. '
The signal is inputted to the reset pulse forming circuit 2' of JS.

Accordingly, the circuit 2' applies a reset pulse similar to the reset pulse generated by the circuit 2 to the gate of the FET 6 via the OR circuit 5, turns it on, and discharges the charge in the capacitor 7. Also, a delay circuit 3' having the same FJ configuration as circuit 6
receives a reset pulse and sends carrier 47f from signal C.
At time t5, which is delayed by approximately the desired time τ, the ON signal et is applied to the attendance latch circuit 4'. Accordingly, the circuit 4' is connected to the switching transistor of the conversion section G2.
Give 1υ signal S2 to turn it on (information
keg). 1t) and the capacitor 7 are turned on when the variable part G2 is turned on.
・0 production) (old; 11 is charged by a redundant flow that depends on the magnitude of the output voltage detection signal Sd applied to j? is compared with a sinusoidal voltage obtained by full-wave rectification of the voltage having a ratio of 1:il to the v-W interphase voltage and voltage, and at time t6 when the voltage on the main side becomes quiet, the signal fWr [mechanical latch circuit 4 ' and also to the reset pulse forming circuit 2''. When the drive latch circuit 4' receives the signal f, it immediately stops sending out the base drive signal S2, and accordingly, the converter G2 is activated after the storage time of the switching transistor has elapsed. time 1
．． to turn off.

Next, the reset pulse forming circuit 2'' receives the signal f from the comparator circuit 10' and applies a reset pulse k to the gate of the FET 6 via the OR circuit 5, turning on all of them and changing the charge of the capacitor Z to the Let's release one generation.

The third delay circuit 6'' receives a reset pulse from the circuit 2'', and applies the on-line clutch No. 8 to the Iu dynamic clutch 101 and 4'' at a time t8, which is a time τ ≧ from the signal f.

Accordingly, the circuit 4'' converts the A motion signal 83 into the converter G6.
is applied to the switching transistor to turn it on (signal j). The capacitor 7 is discharged once when the FET 6 is turned on, and charged with a constant '1;L current proportional to rlj and the output voltage detection signal Sd. The charging pressure of the capacitor 70 is compared with a sinusoidal voltage obtained by full-wave rectification of a voltage proportional to the W-U phase voltage of the positive phase input by a comparator 10'', and the comparator 10'' compares both of these voltages. At time t9 when the values become equal, an off signal i is given to the drive latch circuit 4''.Accordingly, the circuit 4'' stops supplying the drive signal S3, and the converter G6 turns off after the volume time i14 of the switching transistor has elapsed. (Igbo No. J). Jif flow device 9. Both 9' and 9'' act as inductors in the non-uniform sections, and the energy stored in L2' is transferred to diode D.
Flows back through IO and load Ft. Each part operates in this way, and 1 prisoner 11 JIT is completed. In Figure 6, 15 is a 411 conventional diode for each full-wave rectifier 11. , the switching transistor in each conversion section performs ++A-order switching Q9 within each cycle sufficiently smaller than the multiphase AC input voltage IJ1', lill. (As the switching transistor turns on, the next switching transistor turns on.) The switching transistor in each conversion section immediately generates a sinusoidal voltage proportional to the output voltage detection signal and the voltage between each phase. and each switching element opens and closes the rectified sinusoidal voltage of each phase voltage.Therefore, the switching transistors of each conversion section are controlled by a pulse width proportional to 1. The energy extracted from each phase of the polyphase alternating current to the output side every 1υJ, which is sufficiently short in terms of period, is equal to the 144-hour voltage I1 (1
It can be seen that switching is controlled so as to be proportional to the product of a value proportional to 2m (Ksin"Ot: K is a constant) and control (2Y).

Furthermore, in order to make this control method easier to understand, Figure 5 shows the 6-phase input waveform and output 1i'1 waveform of the converter in a 180° interval centered on the U phase. In, vl is the UV phase 'I'ij pressure waveform, v2 is the V-W phase voltage waveform, and V3 is the W-U phase voltage wave II.
In the same figure (J3), Ul, U2, U3 are 6
The time to-t5 to G6 corresponding to 60° Ui1% &C of the phase AC input waveform operates at a conversion frequency of, for example, 201 (Hz), and the 6-variable j>↓ part G1 to G6 corresponds to the corresponding phase of the 6-phase AC input. 'rF'i+ pressure is opened and closed at a conversion frequency of 201utz.As shown by the chain line in Fig. 5, each output voltage waveform in one period starting from time to when UV phase interval 1fi: LE vl is zero value. is explained in detail in the above embodiment, and as shown in '1'c, the output voltage is detected (+'corresponds to the charging voltage of the capacitor 7 depending on the f signal Sd). The switching transistors of each conversion unit 01 to G6 are set to f with the pulse width determined by comparison with the value
ii control, and these switching transistors open and close a sinusoidal voltage that is a full-wave current of the city pressure during each period of 1 roaring.If we consider all the above, the input VIK at time toK, the corresponding output U1 Both pulse 11 and amplitude are very small, output U2 corresponding to human power v2.
The output U5 corresponding to the input V3 and the output U5 are equal to each other in all cases, and the pulses 11.
．． It is easy to understand that both i, +l; and % are sufficiently large.'':5).

Next, as shown in Figure 1, the reciprocal current input U; (i),
5 Time t when 1+1 hits CI' (Of course, ``3 time t.

To explain the cycle that starts with 20 KfIz change even between ~t and 5 mouths and 1 lil wave number, each converter produces jj and lj), the output U1 changes as the input ■, becomes a sinusoidal waveform. Both pulse width and amplitude are large,
The pulse width and amplitude of the output U2 become maximum as the human force v2 reaches the maximum amplitude. Further, the output U3 becomes approximately equal to the output U1 in terms of pulse width and bell as the input v3 becomes actually fp at time t. Does it start from time t2, t3...t5? The same period is also explained in the same manner.

In this 11th example, the frequency of the polyphase AC input is set to 50
1 (where z represents each station) is divided into 400 equal parts with a conversion frequency of 20 Klfz, and in each of these 400 equal parts, the conversion parts 01 to G6' (c--time division control using the control method as described above) are performed. There are 11 cases. 400 IJ stations that have been deceived.
Output U at I ~ Is the sum of U3 a limit? It is proportional to the error signal which is the difference between the i11 quantity, that is, the output '+IL pressure detection No. 11' Vd and the reference value, and if this detection No. 43 Vd is constant, the output in each period is U1
It can be seen that the sums of ~U3 are all equal.

Therefore, according to the above equation (ro), the instantaneous power Pi on the multi-input side is constant, so if the one-plane viewing power obtained on the output side is constant, it is natural that the input side will have a sinusoidal However, in this embodiment, the output U of each cycle is also versatile due to the conversion frequency of 20KfXz, which is sufficiently higher than the frequency of the AC input.
Since the sum of l to U3 is almost constant, high 1. '
It is easy to understand that a sinusoidal current with extremely low M-wave components flows! 71 I can do it.

Moreover, according to this A C-DC conversion, it is possible to obtain the entire 1α output voltage with small ripples, and as can be seen from the above, when the switching transistor of the converting section G1 is turned off, the switching transistor of the converting section G2 is turned on. However, since the switching transistor of the converter G6 can be controlled to turn on when it is turned off, it is easy to increase the frequency, and it is possible to use r:1 up to 1/2, which is the maximum duty of the converter used in the actual Fa1 example. τ can be considered.

Follow like this? 1iil 4・；■1 possible f! f': In order to eliminate the influence of the gear storage time of the switching transistor in the third part, the ON signal is delayed by approximately the same amount of time, and the pulse width is In order to improve the proportionality with respect to the power voltage, the capacitor 7 is charged before the start of this delay time t! r? q;J 'i (,
stomach.

Next, a specific example of the characteristics obtained by such AC-DC conversion will be described. However, the high 1114 waves range from the 2nd order to the 45th order.

Input is 3'A11 AC (50Hz) 200V, output power DC48V% 30A (D case: harmonic distribution of input voltage -UV: 1.67%, V-W: 1.4
1%, W-U: 2.22ch Input current harmonic distribution -U: 5.02ch, V: 4.07
%, W: 4.75, sophistication rate -0,982, efficiency -88.6.

FIG. 6 shows a rectifier for rectifying another embodiment of the present invention, in which the respective outputs of the flow bubbles D9, D9' and D9'' are connected to diodes D11, D1' and D,'', etc. The IR string is connected via the IR string. There are two ways to control the rectifier, and control method 21 is exactly the same as the method in the above embodiment, and the second control method converts without time division because the output is in series. It is possible to control the pulse widths of all the switching elements of sections 01 to G5 by turning them on or conducting them at the same time so that they partially overlap. This second control method also has the basic technical idea of the present invention, that is, the switching element'? ! r, switching at a conversion frequency that is sufficiently higher than the frequency of the 6-phase AC input, and for each cycle of this conversion frequency, the power taken out to the output side of each phase of the 6-phase AC input is 1ilti of the 6-phase AC input. It is proportional to the square of the temporal voltage value (proportional to the bond between fj and control 04In, and the total sum of power extracted from each phase of the multiphase alternating current is controlled to 4, which is proportional to is completely the same as the above embodiment.

Therefore, by simply translating this second (!iU method using 75 Fil), we get
Each switching capacitor of 2.G6 is turned on simultaneously at each time according to a predetermined frequency, and the output voltage output signal Sd is proportional to the fof of the multiphase father input Ii':411+', c value, respectively. Even the bus 1i54 is fb1. l i'il sat1-4 o Yotte mo b'
l 11) The output U of each phase at J, U2, U3 is the human power phase v1 .
■2. Amplitude of U3 and its period output voltage output signal Sd
and the difference between the voltage and the polyphase V1 and the input voltage at 1tt f
It is determined by the value proportional to the product of the target and the target. In this control method, the output U□ of the output side rectifiers D9, D9', D9''
, U2, and U3 are superimposed.

Next, the OFF diagram shows a case in which the converters 01 to G3 are bridge-crossed by switching elements, and the setter tap double-wave rectifier circuits are connected directly to each other.

The 215 control methods in this rectifying device 1'i are exactly the same as those in the example m described above, and therefore will not be described in detail.

Next, in the current device shown in Figure 8, the active circuit of the output τI11 is a full-wave rectifier bridge D9, D9', D9''.
One rectifier arm di, dl', dl is connected in parallel and connected in series with the first inductor L2, and the other rectifier arm d2, U2, d2 is connected in parallel and connected in series with another second inductor L iK. ing. The basic control method of this device is also the same as in the first embodiment, but since the maximum duty of the voltage waveform that each converter supplies to one inductor 2 or L12 is limited to 1, positive, The maximum duty of the output nz pressure waveform of each variable J9j section is divided into negative cycles.
Separate inductors L2, L12 can be used up to 2
The feature is that the current is extracted from the switching element, which improves the utilization of switching elements.

Next, FIG. 9 shows six bidirectional switching elements S1 to S.
6 is connected to a 6-phase full-wave rectifier 41, and the smoothing inductor L2 has an inductance large enough to maintain a constant current in the conversion period. .

The basic control technology is shown in Fig. 2 (Basic 9 Although it will not be explained in detail since it is the same as the control method described above, the table below shows An example of the switching sequence of the switching elements 81 to S6 made by IIIJ is shown.

To explain the above sequence, in the phase of 0 to π/6 of the UV phase voltage, first the switching elements S1 and 8
5, then 85 and 83, and then S6 and 84 sequentially repeat the switching operation at a frequency sufficiently higher than the frequency of the six-phase AC input and by the control method described above. π/6 to 2π/6 of U-V III voltage
During the period, switching elements S1 and 85, S5 and 33,
S6. SL responded to Doho and returned the jii primary switching action. Similarly, corresponding switching elements perform switching operations in other phases as well.

Next, Fig. J'10 shows an example of an on-off type six-phase rectifier, and the control method and switching sequence of the switching knobs 81 to s6 are the same as those of the device shown in Fig. 90, so a description thereof will be omitted. In this device, energy is stored in the inductor L3 when any pair of switching elements 81 to S6 is on, and energy is stored in the inductor L3 in the load F when all of the switching elements 81 to S6 are off. Energy is supplied.

In FIG. 11, each of the bidirectional switching elements $1 to S6 in FIG. The input/output 1!1 is DC-isolated by the transformer T (1q is formed and the rectifier is shown.The control method is to convert the positive output in the control in case of By adding the operation to obtain a negative output to the operation to obtain a negative output (operation with a 180° phase shift), in the table above, the sequences with a 180' phase shift are k Apply positive and negative outputs to the transformer.

As for a simple example of control, if the secondary side of the transformer is connected in series to 4.+1 of the rectifier shown in Figures 6 and 5, the central part of each transformer The pulse width of the switching element is controlled by using the center of the pulse width as a reference trap.The pulse width is controlled before and after the center of the pulse width. When the output sides are connected in parallel like in the case, if the pulse width of drive No. 44 is large or if all the switching elements are turned on for the cautious river 11, the symmetry of control will be improved, the power factor will be improved, and the input current will be reduced. It is possible to reduce harmonics in , and the characteristics can be significantly improved.

Furthermore, in the above-mentioned disaster example, the switching element of the first converter is turned on in response to the basic signal that is generated at a fixed period, and as it is turned off, the switching element of the next converter starts its switching operation. Each primary conversion unit performed a switching operation as shown in FIG.
In order to further reduce the distortion of the waveform of the input iL current, it is also possible to detect the input voltage of each phase and switch the converter in the order of the phase with the highest detected voltage or the phase with the lowest detection voltage. .

J'': J, In the above explanation, the input ゛ti IE was used as the pl, ', pregnant sine waveform applied to one input terminal of the ratio generator, but instead of this, a PLL circuit etc. can be used to adjust the input frequency. A sine wave generator that generates synchronized sine wave signals can also be used.

Also, in actual equipment, through switching elements.

The current flowing from the input to the output varies within the conversion period depending on the leakage inductance in each conversion section and the value of the output side inductor. As a control method for reducing this influence, there is a method of controlling in a ladder in which the total integrated value of the current flowing through all the switching elements is proportional to the absolute value i+t+ of the instantaneous value of the input voltage of the corresponding phase. However, since the integral value depends on the pulse width and the current value, the value fluctuates considerably, and control may become difficult. In this case, 'i' and 'j' correspond to the product of the current flowing from the input through the switching element and the control amount (by dividing it into 11
1J integral (Bit change!!: Since II can be made sufficiently small, fji'l gll becomes easy.

In this case, fill (:I' 1^ is the trace'
j', the father is a value proportional to the output 1a force, and iii! This is the opposite of the above-mentioned 1+, ) trill A]+15・X.

As stated above, according to the present invention, the switching element is switched at a conversion frequency i which is considerably higher than the frequency of the multiphase alternating current, and the outputs ip and lj are extracted from each phase at each cycle according to the odd frequency. Energy is polyphase −,
AC squared and controlled? The high d[8] wave is Because it is possible to flow an input current with a very small component;
It is possible to prevent the induced disturbance on the fl wave component, and also (F
It is possible to obtain a constant output torque with a small one-frequency ripple. Further, according to the present invention, there is a horizontal line between the input i1+11 rectifier circuit and the strange part. Since there is no need to provide an IT circuit, the device can be made smaller.

It goes without saying that in addition to transistors, other devices such as thyristors can also be used as switching elements, and although the above embodiments are based on symmetrical 6-phase crossed manual power, other multi-phase manual power or 2-phase 6V systems can also be used. Even if the input waveform is slightly deformed, the energy flow at the input is controlled to be constant using the return loop, thereby reducing the drop in the output.

4.1 Brief explanation of Inff Fig. 1 is a diagram for explaining a conventional method of controlling a rectifier, and Fig. 2 is a diagram showing an example of a 512 flow device for fully implementing an embodiment of the present invention. , Figure 6 shows that l[Hlj 1゜(
i! Figure 4 is a diagram showing the timing of the operation of each part; Figure 5 is a diagram showing the output waveform of the output side; 1
8 and 9 to 11 are diagrams showing different examples of the cram school 15 flow device for carrying out the fi+lJ control method of the full flow device according to the present invention, respectively.

Recl ~Rec5- Hard (IT, circuit 01~G6
...Variable JV4 part F...Load Con...Control circuit 1...Basic information generator 2.2', 2''-reset pulse type H, circuit 6.6',
3''...delay circuit 4.4', 4''...11 latch circuit 5...OR
Circuit 8... Error amplifier 9... Controllable regular flow source 10. 10', 10''... Comparator % U'l' output & li 4 people Origin Electric Co., Ltd. Figure 11 Procedure amendment document 1988 12 May 27th, Mr. Commissioner of the Japan Patent Office 1, Indication of the case Patent Application No. 173646 of 1982, 2 Title of the invention Control method of rectifier device 6, Relationship with the amendment person case Patent applicant address Takada, Toshima-ku, Tokyo 1-18-1 〒17
1 Telephone (983) 7111 (Main) 4. Date of amendment order Voluntary 5. Subject of amendment ``Detailed description of the invention'' column (1)
In the present specification, page 6, line 12, 1, direct current... is corrected as follows.

1) If the load on the AC input is linear and the DC output side is controlled so as to obtain a constant amount of energy, it will be released through the same book Off Negative Line 15 1...01' ” is corrected as follows.

"...Return to C1'..." (3+
) Same book, page 10, line 4 F...It rises in proportion to the size. ' shall be corrected as follows.

[...It rises at a rising rate proportional to its size. ] (4) Lines 14 to 16 of page 16 of the same book “...
. . . Inductor L2, . . . conducts current. ” shall be amended as follows.

l...The energy stored in the inductor L2 flows through the diode D1o'. (5) In the same book, No. 17, line 8 and line 9, “If it is fixed,...
"...Flows, but" is corrected as follows.

"If the above-mentioned pulse width control has a sufficiently high conversion frequency with respect to the input frequency, a sinusoidal current will naturally flow on the input side simply by removing the high frequency component." (6) Ibid., same page. The 11th line 1... is constant, so the input j is corrected as follows.

[...Since it is constant, it is possible to obtain a DC output voltage with small ripples, and the input voltage is constant.''
・・Ripple・・・・can be done, ``Delete all.''

(a, same book, same page, line 20 [...It can be controlled, so the frequency is increased...]) Correct as shown below.

"...Since it can be controlled, the output side can be connected in parallel using an on-off type converter, and high frequency can be achieved at low voltage and large current..." (9) Ibid.・From the 1st line on page 19 to the 16th line on page 20, “Figure 6 is...
...is superimposed. ” is corrected as follows.

Claims (1)

[Scope of Claims] (1) A method for controlling a rectifier which receives polyphase alternating current as input and obtains an output voltage by sending energy to an output through a switching element when a switching element is turned on, comprising: switching of each phase; The elements are operated at a conversion frequency higher than the frequency of the polyphase alternating current, and in each period determined by this conversion frequency, the switching elements of the other phases are turned on as the switching element of the phase that is turned on turns on. The switching elements are sequentially switched fjhn
control so that the power extracted from each phase of the polyphase alternating current to the output side in each period determined by the conversion frequency is proportional to the square of the instantaneous voltage of the polyphase alternating current and the detection signal. A method for controlling a rectifier, characterized in that the control is performed in a manner dependent on a predetermined relationship between the flow rate and the flow rate. (2) The method for controlling a rectifier according to claim (1), wherein the switching elements of each phase perform all switching operations in a predetermined sequence. (6) Claim (1) characterized in that the switching elements of each phase perform switching operations in the order of the phases with larger or smaller detected voltage values in each phase of the multiphase AC input. A method for controlling a hepatic flow device.