EP2012563B1 - Dispositif d'amorçage amélioré - Google Patents

Dispositif d'amorçage amélioré Download PDF

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Publication number
EP2012563B1
EP2012563B1 EP20080008476 EP08008476A EP2012563B1 EP 2012563 B1 EP2012563 B1 EP 2012563B1 EP 20080008476 EP20080008476 EP 20080008476 EP 08008476 A EP08008476 A EP 08008476A EP 2012563 B1 EP2012563 B1 EP 2012563B1
Authority
EP
European Patent Office
Prior art keywords
switching frequency
current
steps
control circuit
preheat
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Not-in-force
Application number
EP20080008476
Other languages
German (de)
English (en)
Other versions
EP2012563A2 (fr
EP2012563A3 (fr
Inventor
Markus Cernek
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Vossloh Schwabe Deutschland GmbH
Vossloh Schwabe GmbH
Original Assignee
Vossloh Schwabe Deutschland GmbH
Vossloh Schwabe GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Vossloh Schwabe Deutschland GmbH, Vossloh Schwabe GmbH filed Critical Vossloh Schwabe Deutschland GmbH
Publication of EP2012563A2 publication Critical patent/EP2012563A2/fr
Publication of EP2012563A3 publication Critical patent/EP2012563A3/fr
Application granted granted Critical
Publication of EP2012563B1 publication Critical patent/EP2012563B1/fr
Not-in-force legal-status Critical Current
Anticipated expiration legal-status Critical

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps

Definitions

  • the invention relates to a ballast for gas discharge lamps such as fluorescent lamps, in particular with preheatable electrodes.
  • Ballasts for gas discharge lamps in particular fluorescent lamps, currently usually contain externally controlled inverters, which are controlled by a control circuit in the form of an integrated circuit.
  • ballast is the data sheet "Smart Ballast Control IC for Fluorescent Lamp Ballasts" Datasheet Version 1.2, February 2006, for the integrated circuit ICB1FL02G.
  • the integrated circuit has outputs for the direct control of an inverter half-bridge to which a fluorescent lamp is connected with the interposition of further components in the form of, for example, capacitors and inductors.
  • the inverter half-bridge is grounded through a current sensing resistor to sense the current flowing therethrough. The voltage drop across the current sensing resistor is applied to a corresponding LSCS input of the integrated circuit.
  • the integrated circuit has a further control input RFRUN, which is connected via a resistor to ground.
  • the size of the resistor determines the switching frequency of the inverter half-bridge when the lamp is lit.
  • Another control input RFPH is connected to earth via another resistor.
  • the size of the resistor determines the switching frequency of the inverter half-bridge during preheating.
  • Another input RTPH is connected via a resistor to ground. This resistance determines the length of time of the preheat phase.
  • the inverter half-bridge In the preheat phase, the inverter half-bridge is operated at a switching frequency which is greater than during the operating phase. Resonance effects in the lamp branch thereby cause a preheating current in the heating coils.
  • the integrated circuit goes into an ignition phase.
  • the switching frequency of the inverter half bridge in steps, for example, 127 individual steps, gradually changed in the direction of the operating frequency. Occurs in this case on the current sensor resistance to a current increase, for example, as a result of the saturation of current-limiting inductances, the switching frequency is preferably by several Steps increased again. If the difference between the switching frequency during the preheat phase and the switching frequency during the operating phase is very large, the individual steps are also very large.
  • the ballast according to the invention has a control circuit which has an input at which the size of the steps of the frequency change during the ignition phase can be influenced.
  • the control circuit may be a discrete circuit, an integrated circuit or a mixture of discrete and integrated circuits.
  • the control circuit operates during the ignition phase at a preheat switching frequency and during operation of the fluorescent lamp at an operating switching frequency. Both are predetermined switching frequencies, wherein the Vorholicschaltfrequenz is significantly higher than the operating switching frequency.
  • the switching frequency goes to the operating switching frequency in steps from the preheat switching frequency down.
  • the possibility of influencing, in particular reducing, the size of the steps during the ignition phase ensures that the reduction in the ignition voltage applied to the lamp becomes too great after a current violation at the current sensor resistance of the inverter. It can be ensured that the frequency change of the switching frequency is lower and thus also the Zündnapsredulement is lower. This ultimately increases the (quadratic) mean value of the ignition voltage during the ignition phase. Without further increase of the ignition peak voltage thereby the ignition of the gas discharge lamp is facilitated. This also applies to difficult ignition conditions, for example due to low temperatures, applied moisture, aged lamps or the like.
  • the input for controlling the size of the steps during the ignition phase can directly control the size of the steps. But it may also be an input, which is provided for example to determine the preheating frequency.
  • the operating frequency can be specified otherwise.
  • the input for specifying the preheating frequency By influencing the input for specifying the preheating frequency, the difference between the operating frequency and the preheating frequency (temporary) is changed. This also changes the size of the steps (temporarily).
  • the input for specifying the Vorholicschaltfrequenz can be used as an input to influence the size of the steps.
  • control circuit may have an input whose wiring determines the operating switching frequency.
  • the temporary influence of this input by A switch during the ignition phase can also be used to reduce the difference between the operating switching frequency and the preheat switching frequency and thus the magnitude of the steps for the frequency change.
  • an input or output of the control circuit can be used, the wiring of which defines, for example with an ohmic resistance, the length of time of the preheating phase.
  • the voltage dropping across the resistor can serve as a control signal for the design of the length of the preheating phase.
  • the voltage drop across the resistor may be provided to control the switch.
  • the concept presented is particularly suitable for use in ballasts in which a particularly large difference between the Vorholicschaltfrequenz and the operating switching frequency is required or desired.
  • FIG. 1 is a ballast 1 illustrated in a simplified representation.
  • a not further illustrated power supply for generating a high DC voltage U, for example, 400 volts.
  • the circuit contains not further illustrated means for generating a lower DC voltage U b, for example, 15 V for supplying a control circuit 2.
  • This is used to control an inverter 3, for example, comprises two switching transistors T1, T2.
  • a lamp branch 4 is connected, which contains a gas discharge lamp, for example in the form of a fluorescent lamp 5.
  • the fluorescent lamp 5 has heatable electrodes 6, 7 which are designed, for example, as heating coils and are connected to a heating circuit 8.
  • the fluorescent lamp 5 is fed by the inverter 3 via a current limiting inductor 9.
  • a coupling capacitor 10 is provided in series with the throttle 9 or other suitable location to keep away from DC potentials of the fluorescent lamp 5.
  • the heating circuit 8 can, as shown, be provided by a simple capacitor 11 connecting the electrodes 6, 7 or else by more costly means, as described in the Datasheet Version 1.2, February 2006, of the ICB1FL02G "Smart Ballast Control IC for Fluorescent Lamp Ballast". the company Infineon emerge.
  • the two ends of a respective electrode 6, 7 may be connected via a series resonant circuit to corresponding windings, which are arranged on the inductor 9 and inductively couple with this.
  • the inverter 3 outputs a voltage which is not constant over time to the lamp circuit 8, which periodically changes between the operating voltage U (for example 400 V) and 0 V and is regarded as alternating voltage in this respect.
  • U for example 400 V
  • 0 V a voltage which is not constant over time to the lamp circuit 8
  • a current sensor resistor 12 is provided between the lower transistor T2 of the inverter 3 and Ground. This generates a voltage drop, which characterizes the current in the inverter 3 and in particular in the lamp circuit 8.
  • the control circuit 2 serving to control the inverter 3 is, for example, the integrated circuit ICB1FL02G from Infineon. This has a current monitoring input LSCS, which is connected directly or via a corresponding converter circuit 13 to the current sensor resistor 12.
  • the control circuit 2 specifies the switching frequency of the inverter 3. It distinguishes between a heating phase V (Preheat), an ignition phase Z (Ignition) and an operating phase B (Run).
  • the switching frequencies of the inverter 3 are set differently by the control circuit 2 in the phases V, Z and B.
  • To set the respective desired switching frequencies are corresponding inputs RFRUN and RFPH the control circuit 2. At the input RFRUN the operating switching frequency for the operating phase B by the size of a corresponding grounded resistor R1 is set.
  • the preheat switching frequency RFPH is determined by the ohmic resistance to be measured from the input RFPH to ground. This resistance is determined by the series connection of two resistors R2, R4.
  • Another input RTPH defines the duration of the preheat phase V.
  • the resistor R3 is acted upon via the terminal RTPH of the control circuit 2 to a current.
  • the magnitude of the voltage drop across resistor R3 controls the length of the preheat time interval. After the same time, the current flowing through resistor R3 to ground is cut off. The voltage drop across the resistor R3 then collapses.
  • the resistor R4 is bridged by a switch, which is formed in the present embodiment by a transistor T3, for example, a bipolar npn transistor. Its emitter is grounded while its collector is connected to the junction of resistors R2 and R4. Its base is connected via a resistor R5 to the input RTPH.
  • a switch which is formed in the present embodiment by a transistor T3, for example, a bipolar npn transistor. Its emitter is grounded while its collector is connected to the junction of resistors R2 and R4. Its base is connected via a resistor R5 to the input RTPH.
  • the ballast 1 described so far operates as follows:
  • the control circuit 2 When switching on, the control circuit 2 begins to operate the inverter 3 initially with a high switching frequency of 125 kHz, for example. Within a very short time, this frequency drops to a preheat frequency of, for example, 65 kHz. For a preheat period, which is determined by the size of the resistor R3, the control circuit 2, and thus the inverter 3, now operates at a constant preheat switching frequency.
  • the preheat switching frequency is significantly above the operating switching frequency of, for example, only 45 kHz.
  • the preheating phase V serves to preheat the electrodes 6, 7 of the fluorescent lamp 5.
  • the heating circuit 8 is designed to conduct a large part of the current output by the inverter 3 through the electrodes 6, 7 to heat them.
  • the ballast 1 goes into ignition mode.
  • the switching frequency of the inverter 3 is lowered. This is done, for example, in a fixed number of steps.
  • the specified number can be 127.
  • the lamp circuit 8 preferably operates with resonance. It can have a resonant frequency at the operating frequency FRUN, ie near 45 kHz. The current in the lamp branch and thus the inverter current increases when the switching frequency is lowered. If the still unlit fluorescent lamp 5 does not yet dampen the resonance phenomena in the lamp circuit 8, excessive current increases can occur, for example as a consequence of saturation phenomena of the reactor 9.
  • Such current increases are detected at the current sensor resistor 12 and passed through the conversion circuit 13 or directly to the LSCS input of the control circuit 2. It responds by increasing the switching frequency by ten steps, for example.
  • the voltage curve resulting without T3 and R5 is in FIG. 3 as curve 14 illustrates. If the frequency reaches its respective minimum, the voltage U at the fluorescent lamp 5 has its maximum, which may be above 900 volts, for example. At the same time, however, the current detected at the current sensor resistor 12 exceeds the set limit, so that the control circuit 2 greatly reduces the frequency. It comes immediately to a sharp drop in voltage 15, then how FIG. 3 shows again a gradual increase in voltage 16 follows.
  • a virtual preheat switching frequency FPH ' is formed which is between the operating switching frequency FRUN and the preheating switching frequency VPH and can be significantly lower than this.
  • FPH ' is formed which is between the operating switching frequency FRUN and the preheating switching frequency VPH and can be significantly lower than this.
  • At least one circuit branch is present which determines the switching frequency of the inverter 3 during the preheating phase V and the ignition phase Z of the fluorescent lamp 5.
  • the circuit branch at least one switch or a similar electronic component is present, that of the control circuit 2 for driving the inverter 3 during the ignition Z predetermines a different Vorholicschaltfrequenz than during the actual preheat V. This reduces the step size or step size of the frequency change during the ignition Z and subsequently the time average of the ignition voltage and the number of ignition in the phase Z occurring voltage maxima increases.

Landscapes

  • Circuit Arrangements For Discharge Lamps (AREA)

Claims (10)

  1. Ballast (1) destiné à des lampes à décharge gazeuse, en particulier des lampes à décharge gazeuse basse pression, notamment des lampes fluorescentes (5),
    comprenant un onduleur (3) qui transforme une tension continue en tension alternative, à partir de laquelle la lampe à décharge gazeuse (5) est alimentée en courant,
    comprenant un circuit de commande (ICB1FL02G) qui prédéfinit une fréquence de commutation (F) pour l'onduleur (3) pendant une phase de préchauffage (V), une phase d'amorçage (Z) et une phase de service (B), sachant que
    le circuit de commande (ICB1FL02G) présente au moins une première et une deuxième entrée (RFPH, RFRUN) pour prédéfinir une fréquence de commutation de préchauffage et de service, et sachant que
    le circuit de commande (ICB1PL02G contient un composant qui est conçu pour faire passer la fréquence de commutation (F), pendant la phase d'amorçage, par pas (S) d'une fréquence de commutation de préchauffage (FPH) à la fréquence de commutation de service (RUN), les pas (S) présentant une grandeur qui dépend de la différence entre la fréquence de commutation de préchauffage et la fréquence de commutation de service,
    et sachant que le circuit de commande (ICB1FL02G) présente une entrée de surveillance de courant (LSCS),
    et sachant que le circuit de commande (ICB IFL02G) est conçu pour augmenter la fréquence de commutation (F) d'un ou plusieurs pas (S), en cas d'augmentation du courant de l'onduleur jusqu'à un courant maximal pendant la phase d'amorçage,
    caractérisé en ce que
    est connectée à la première entrée du circuit de commande (RFPH), une première résistance (124) qui agit sur la fréquence de commutation de préchauffage et/ou de service, et en ce que
    est connecté à la première entrée (RFPH) du circuit de commande (ICB1FL02G), un interrupteur (T3) en parallèle avec la première résistance (R4), l'interrupteur (T3) étant agencé de telle manière que l'interrupteur mette la première résistance (R4) en dérivation pendant la phase d'amorçage, en vue d'agir sur la grandeur des pas (S) au cours de la phase d'amorçage,
  2. Ballast selon la revendication 1, caractérisé en ce qu'au moins une inductance de limitation de courant (9) est disposée entre l'onduleur (3) et la lampe à décharge gazeuse (5), la lampe à décharge gazeuse (5) étant alimentée par l'onduleur (3), par l'intermédiaire de l'inductance de limitation de courant (9).
  3. Ballast selon la revendication 1, caractérisé en ce que la première entrée (RFPH) est prévue pour la prédéfinition de la fréquence de commutation de préchauffage (FPH).
  4. Ballast selon la revendication 1, caractérisé en ce que la deuxième entrée (RFRUN) est prévue pour la prédéfinition de la fréquence de commutation de suervice (FUN).
  5. Ballast selon la revendication 1, caractérisé en ce que les pas (S) présentent un nombre prédéfini.
  6. Ballast selon la revendication 5, caractérisé en ce que la grandeur des pas correspond à la différence entre la fréquence de commutation de préchauffage (FPH') et la fréquence de commutation de service (FRUN), divisée par le nombre de pas (S).
  7. Ballast selon la revendication 1, caractérisé en ce qu'un dispositif de surveillance de courant (12) est prévu pour surveiller le courant de l'onduleur.
  8. Ballast selon la revendication 7, caractérisé en ce que le dispositif de surveillance de courant est connecté à l'entrée de surveillance de courant du circuit de commande (ICB1FL02G), afin d'augmenter d'un ou plusieurs pas la fréquence de commutation pendant la phase d'amorçage (Z), si le courant de l'onduleur dépasse le courant maximal.
  9. Ballast selon la revendication 1, caractérisé en ce que l'interrupteur (T3) est connecté à une borne (RTPH) du circuit de commande (ICB1FL02G), dont la connexion à une deuxième résistance (R3) sert à commander la durée de la phase d'amorçage (Z), la tension qui chute sur la deuxième résistance (R3) servant à commander l'interrupteur, de sorte que l'interrupteur (T3) est activé pour la durée de la phase d'amorçage.
  10. Ballast selon la revendication 1, caractérisé en ce que, pendant la phase d'amorçage (Z), l'interrupteur (T3) diminue la valeur prédéfinie pour la fréquence de commutation de préchauffage, afin de réduire ainsi la grandeur des pas (S).
EP20080008476 2007-07-04 2008-05-06 Dispositif d'amorçage amélioré Not-in-force EP2012563B1 (fr)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
DE200710031099 DE102007031099A1 (de) 2007-07-04 2007-07-04 Vorschaltgerät mit verbessertem Zündspannungsmittelwert

Publications (3)

Publication Number Publication Date
EP2012563A2 EP2012563A2 (fr) 2009-01-07
EP2012563A3 EP2012563A3 (fr) 2010-02-03
EP2012563B1 true EP2012563B1 (fr) 2014-07-09

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ID=39884546

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Application Number Title Priority Date Filing Date
EP20080008476 Not-in-force EP2012563B1 (fr) 2007-07-04 2008-05-06 Dispositif d'amorçage amélioré

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EP (1) EP2012563B1 (fr)
DE (1) DE102007031099A1 (fr)

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6414449B1 (en) * 2000-11-22 2002-07-02 City University Of Hong Kong Universal electronic ballast
US6628091B2 (en) * 2001-05-29 2003-09-30 Koninklijke Philips Electronics N.V. Electronic switch for a bi-level fluorescent lamp fixture

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EP2012563A2 (fr) 2009-01-07
DE102007031099A1 (de) 2009-01-22
EP2012563A3 (fr) 2010-02-03

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